TNY255P

TNY255PN POWERINT | Alldatasheet

Document overview

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Technical content

Figure 1. Typical Standby Application.

230 VAC or

115 VAC

• Lower cost than RCC, discrete PWM and other integrat- ed/hybrid solutions
• Cost effective replacement for bulky linear adapters
• Lowest component count
• Simple ON/OFF control – no loop compensation devices
• No bias winding – simpler, lower cost transformer
• Allows simple RC type EMI filter for up to 2 W from universal input or 4 W from 115 VAC input Extremely Energy Efficient
• Consumes only 30/60 mW at 115/230 VAC with no load
• Meets Blue Angel, Energy Star, Energy 2000 and 200 mW European cell phone requirements for standby
• Saves $1 to $4 per year in energy costs (at $0.12/kWHr) compared to bulky linear adapters
• Ideal for cellular phone chargers, standby power supplies for PC, TV and VCR, utility meters, and cordless phones. High Performance at Low Cost
• High-voltage powered – ideal for charger applications
• Very high loop bandwidth provides excellent transient response and fast turn on with practically no overshoot
• Current limit operation rejects line frequency ripple
• Glitch free output when input is removed
• Built-in current limit and thermal protection
• 44 kHz operation (TNY253/4) with snubber clamp reduces EMI and video noise in TVs and VCRs
• Operates with optocoupler or bias winding feedback

Description

The TinySwitch family uses a breakthrough design to provide the lowest cost, high efficiency, off-line switcher solution in the 0 to 10 W range. These devices integrate a 700 V power MOSFET, oscillator, high-voltage switched current source, current limit and thermal shutdown circuitry. They start-up and run on power derived from the DRAIN voltage, eliminat- ing the need for a transformer bias winding and the associated circuitry. And yet, they consume only about 80 mW at no load, from 265 VAC input. A simple ON/OFF control scheme also eliminates the need for loop compensation. TNY253P TNY254P TinySwitch Selection Guide PACKAGE DIP-8 DIP-8 SMD-8 SMD-8 TNY253G TNY255P 0-2 W 1-4 W 0-4 W 2-5 W TNY255G DIP-8 TNY254G SMD-8 3.5-6.5 W4-10 W The TNY253 and TNY254 switch at 44 kHz to minimize EMI and to allow a simple snubber clamp to limit DRAIN spike voltage. At the same time, they allow use of low cost EE16 core transformers to deliver up to 5 W. The TNY253 is identical to TNY254 except for its lower current limit, which reduces output short-circuit current for applications under 2.5 W. TNY255 uses higher switching rate of 130 kHz to deliver up to 10 W from the same low cost EE16 core for applications such as PC standby supply. An EE13 or EF13 core with safety spaced bobbin can be used for applications under 2.5 W. Absence of a bias winding eliminates the need for taping/margins in most applications, when triple insulated wire is used for the secondary. This simplifies the transformer construction and reduces cost. PI-2178-022699 Wide-Range High-Voltage DC Input TinySwitch D S EN BP DC Output **Table 1. *Please refer to the Key Application Considerations section**

Figure 2. Functional Block Diagram. Figure 3. Pin Configuration. current for both start-up and steady-state operation. sourcing supply current to external circuitry. Power MOSFET source connection. Primary return. simple ON/OFF control to regulate the output voltage. pin for faster loop response.

1.5 V + VTH

circuit is sampled at the rising edge of the oscillator Clock signal (at the beginning of each cycle). If it is high, then the power MOSFET is turned on (enabled) for that cycle, otherwise the power MOSFET remains in the off state (cycle skipped). Since the sampling is done only once at the beginning of each cycle, any subsequent changes at the ENABLE pin during the cycle are ignored.

5.8 V Regulator

The 5.8 V regulator charges the bypass capacitor connected to the BYPASS pin to 5.8 V by drawing a current from the voltage on the DRAIN, whenever the MOSFET is off. The BYPASS pin is the internal supply voltage node for the TinySwitch. When the MOSFET is on, the TinySwitch runs off of the energy stored in the bypass capacitor. Extremely low power consumption of the internal circuitry allows the TinySwitch to operate continu- ously from the current drawn from the DRAIN pin. A bypass capacitor value of 0.1 µF is sufficient for both high frequency de-coupling and energy storage. Undervoltage The undervoltage circuitry disables the power MOSFET when the BYPASS pin voltage drops below 5.1 V. Once the BYPASS pin voltage drops below 5.1 V, it has to rise back to 5.8 V to enable (turn-on) the power MOSFET. Hysteretic Over Temperature Protection The thermal shutdown circuitry senses the die junction tem- perature. The threshold is set at 135 °C with 70 °C hysteresis. When the junction temperature rises above this threshold (135 °C) the power MOSFET is disabled and remains disabled until the die junction temperature falls by 70 °C, at which point it is re-enabled. Current Limit The current limit circuit senses the current in the power MOSFET. When this current exceeds the internal threshold (ILIMIT), the power MOSFET is turned off for the remainder of that cycle. The leading edge blanking circuit inhibits the current limit comparator for a short time (tLEB) after the power MOSFET is turned on. This leading edge blanking time has been set so that current spikes caused by primary-side capacitance and secondary-side rectifier reverse recovery time will not cause premature termination of the switching pulse. TinySwitch Operation TinySwitch is intended to operate in the current limit mode. When enabled, the oscillator turns the power MOSFET on at the beginning of each cycle. The MOSFET is turned off when the current ramps up to the current limit. The maximum on-time of the MOSFET is limited to DCMAX by the oscillator. Since the current limit and frequency of a given TinySwitch device are constant, the power delivered is proportional to the primary inductance of the transformer and is relatively independent of the input voltage. Therefore, the design of the power supply involves calculating the primary inductance of the transformer for the maximum power required. As long as the TinySwitch device chosen is rated for the power level at the lowest input voltage, the calculated inductance will ramp up the current to the current limit before the DCMAX limit is reached. Enable Function The TinySwitch senses the ENABLE pin to determine whether or not to proceed with the next switch cycle as described earlier. Once a cycle is started TinySwitch always completes the cycle (even when the ENABLE pin changes state half way through the cycle). This operation results in a power supply whose output voltage ripple is determined by the output capacitor, amount of energy per switch cycle and the delay of the ENABLE feedback. The ENABLE signal is generated on the secondary by comparing the power supply output voltage with a reference voltage. The ENABLE signal is high when the power supply output voltage is less than the reference voltage. In a typical implementation, the ENABLE pin is driven by an optocoupler. The collector of the optocoupler transistor is connected to the ENABLE pin and the emitter is connected to the SOURCE pin. The optocoupler LED is connected in series with a Zener across the DC output voltage to be regulated. When the output voltage exceeds the target regulation voltage level (optocoupler diode voltage drop plus Zener voltage), the optocoupler diode will start to conduct, pulling the ENABLE pin low. The Zener could be replaced by a TL431 device for improved accuracy. The ENABLE pin pull-down current threshold is nominally 50 µA, but is set to 40 µA the instant the threshold is exceeded. This is reset to 50 µA when the ENABLE pull-down current drops below the current threshold of 40 µA. ON/OFF Control The internal clock of the TinySwitch runs all the time. At the beginning of each clock cycle the TinySwitch samples the ENABLE pin to decide whether or not to implement a switch cycle. If the ENABLE pin is high (< 40 µA), then a switching cycle takes place. If the ENABLE pin is low (greater than 50 µA) then no switching cycle occurs, and the ENABLE pin status is sampled again at the start of the subsequent clock cycle. At full load TinySwitch will conduct during the majority of its clock cycles (Figure 4). At loads less than full load, the TinySwitch will “skip” more cycles in order to maintain volt- age regulation at the secondary output (Figure 5). At light load or no load, almost all cycles will be skipped (Figure 6). A small percentage of cycles will conduct to support the power consumption of the power supply.

Figure 4. TinySwitch Operation at Heavy Load. Figure 5. TinySwitch Operation at Medium Load. line ripple rejection and excellent transient response. remain off without any glitches (Figure 8). the cost of an extra bias winding and associated components. ated components, none of which are necessary with TinySwitch. Switching frequency (with no cycle skipping) is set at 44 kHz. the preferred snubbing schemes are RCD or diode-Zener clamps. tor alone in 115 VAC applications at powers levels below 4 W). impacting the efficiency of the supply. the TNY253/254 for lower power applications.

Figure 6. TinySwitch Operation at Light Load. Figure 7. TinySwitch Power-Up Timing Diagram. Figure 8. TinySwitch Power Down Timing Diagram. decoupling the internal power supply of the TinySwitch.

375 VDC depending on the input AC voltage range that the TV

source of the DC supply to the inputs of the TV standby circuit. create the 7.5 V output. L1 and C5 provide additional filtering. U2 LED forward drop (~ 1 V) and Zener diode VR1 voltage. improve its voltage tolerance.

10 W Standby

Figure 11. 3.6 W Constant Voltage-Constant Current Cellular Phone Charger Circuit. current output over an universal input (85 to 265 VAC) range. bias current through the Zener to improve its voltage tolerance. Figure 12. 0.5 W Open Loop AC Adapter Circuit.

achieve the appropriate value. R3 is a base current limiting resistor. When the drop across R4 exceeds the VBE of transistor Q1, it turns on and takes over the control of the loop by driving the optocoupler LED. R6 drops an additional voltage to keep the control loop in operation down to zero volts on the output. With the output shorted, the drop across R4 and R6 (~ 1.5 V) is sufficient to keep the Q1 and LED circuit active. Resistors R7 and R9 limit the forward current that could be drawn through VR1 by Q1 under output short-circuit conditions, due to the voltage drop across R6 and R4. AC Adapter Many consumer electronic products utilize low power 50/60 Hz transformer based AC adapters. The TinySwitch can cost ef- fectively replace these linear adapters with a solution that is lighter, smaller and more energy efficient . Figure 12 shows a 9 V, 0.5 W AC adapter circuit using the TNY253. This circuit operates from a 115 VAC input. To save cost, this circuit runs without any feedback, in discontinuous conduction mode to deliver constant power output relatively independent of in- put voltage. The output voltage is determined by the voltage drop across Zener diode VR1. The primary inductance of the transformer is chosen to deliver a power that is in excess of the required output power by at least 50% to allow for component tolerances and to maintain some current through the Zener VR1 at full load. At no load, all of the power is delivered to the Zener which should be rated and heat sinked accordingly. In spite of a constant power consumption from the mains input, this solu- tion is still significantly more efficient than linear adapters up to output power levels of approximately 1 W. The AC input is rectified by diodes D1 and D2. D2 is used to reduce conducted EMI by only allowing noise onto the neutral line during diode conduction. The rectified AC is then filtered by capacitors C1 and C2 to generate a high-voltage DC bus, which is applied to the series combination of the primary wind- ing of T1 and the high-voltage MOSFET inside the TNY253. The resistor R2 along with capacitors C1 and C2 form a π-filter which is sufficient for meeting EMI conducted emissions at these power levels. C5 is a Y capacitor which is used to reduce common mode EMI. Due to the 700 V rating of the TinySwitch MOSFET, a simple capacitive snubber (C4) is adequate to limit the leakage inductance spike in 115 VAC applications, at low power levels. The secondary winding is rectified and filtered by D3 and C6. Key Application Considerations For the most up to date information visit our Web site at: www.powerint.com Design Output Power Range The power levels shown in the TinySwitch Selection Guide (Table 1) are approximate, recommended output power ranges that will provide a cost optimum design and are based on following assumptions: 1. The minimum DC input voltage is 90 V or higher for 85 VAC input or 240 V or higher for 230 VAC input or 115 VAC input with a voltage doubler. 2. The TinySwitch is not thermally limited - the source pins are soldered to sufficient copper area to keep the die temperature at or below 100 °C. This limitation does not usually apply to TNY253 and TNY254. The maximum power capability of a TinySwitch depends on the thermal environment, transformer core size and design (continuous or discontinuous), efficiency required, minimum specified input voltage, input storage capacitance, output volt- age, output diode forward drop, etc., and can be different from the values shown in the selection guide. Audible Noise At loads other than maximum load, the cycle skipping mode operation used in TinySwitch can generate audio frequency components in the transformer. This can cause the transformer to produce audio noise. Transformer audible noise can be reduced by utilizing appropriate transformer construction techniques and decreasing the peak flux density. For more information on audio suppression techniques, please check the Application Notes section on our Web site at www.powerint.com. Ceramic capacitors that use dielectrics such as Z5U, when used in clamp and snubber circuits, can also generate audio noise due to electrostriction and piezo-electric effects. If this is the case, replacing them with a capacitor having a different type of dielectric is the simplest solution. Polyester film capacitor is a good alternative. Short-Circuit Current The TinySwitch does not have an auto-restart feature. As a result, TinySwitch will continue to deliver power to the load during output short-circuit conditions. In the worst case, peak short-circuit current is equal to the primary current limit (ILIMIT) multiplied by the turns ratio of the transformer (Np/Ns). In a typical design the average current is 25 to 50% lower than this peak value. At the power levels of TinySwitch this is

1. Soldered to 1 sq. inch (645 mm2), 2 oz. (610 gm/m2) copper clad. 6. The higher peak drain current is allowed while the drain voltage is simultaneously less than 400 V. ABSOLUTE MAXIMUM RATINGS(1) 1. All voltages referenced to SOURCE, TA = 25 °C. 2. Normally limited by internal circuitry. 3. 1/16" from case for 5 seconds. 40 44 48 66 68 71 -68 -50 -30 -15 -10 -5 1.10 1.45 1.80 -58 -42 -25 160 200 140 180 -2.5 5.8 0.72 CONTROL FUNCTIONS Output Frequency Maximum Duty Cycle ENABLE Pin Turnoff Threshold Current ENABLE Pin Hysteresis Current ENABLE Pin Voltage ENABLE Short- Circuit Current DRAIN Supply Current BYPASS Pin Charge Current BYPASS Pin Voltage BYPASS Hysteresis kHz µA µA V µA µA µA mA mA V V Min Typ Max fOSC DCMAX IDIS IHYS VEN IENSC IS1 IS2 ICH1 ICH2 VBP VBPH Parameter Symbol (Unless Otherwise Specified) See Figure 14 Conditions TNY253 TNY255 TNY253 TNY254 TNY255 TNY253 TNY254 TNY255 TNY253 TNY254 TNY255 130 215 -4.5 -3.3 TNY254 ENABLE Open (MOSFET Switching) See Note B, C TJ = 25 °C 115 140 265 -2.0 -5.0 -3.5 -4.0 -1.0 5.6 6.1 0.60 0.85 UnitsSOURCE = 0 V; TJ = -40 to 125 °C TNY253 TNY255 67 TNY254 TJ = -40 °C to 125 °C TJ = 125 °C -68 -52 -45 VEN = 0 V, TJ = -40 °C to 125 °C VEN = 0 V, TJ = 125 °C -58 -45 -38 VBP = 0 V, TJ = 25 °C See Note D, E VBP = 4 V, TJ = 25 °C See Note D, E 64 69 -4.8 -1.8 -6.0 -3.0 170 215 TNY253 TNY254 TNY255 S1 Open See Note A IEN = -25 µA VEN = 0 V (MOSFET Not Switching) See Note B See Note D

Parameter Symbol SOURCE = 0 V; TJ = -40 to 125 °C See Figure 14 (Unless Otherwise Specified) di/dt = 12.5 mA/µs TJ = 25 °C di/dt = 25 mA/µs TJ = 25 °C di/dt = 80 mA/µs TJ = 25 °C 135 150 165 230 255 280 255 280 310 170 240 170 215 200 250 100 150 125 135 145 31 36 50 60 23 27 37 45 700 ILIMIT Note F IINIT tLEB tILD RDS(ON) IDSS BVDSS tR tF mA mA ns ns Ω µA V ns ns Current Limit Initial Current Limit Leading Edge Blanking Time Current Limit Delay Thermal Shutdown Temperature Thermal Shutdown Hysteresis ON-State Resistance OFF-State Drain Leakage Current Breakdown Voltage Rise Time Fall Time Min Typ Max Units CIRCUIT PROTECTION OUTPUT VBP = 6.2 V, VEN = 0 V, V DS = 560 V, TJ = 125 °C TJ = 25 °C TJ = 100 °C TJ = 25 °C TJ = 100 °C TNY253/TNY254 ID = 25 mA Measured with Figure 10 Schematic. TNY253 TNY254 TNY255 VBP = 6.2 V, VEN = 0 V, IDS = 100 µA, TJ = 25 °C TNY253 TNY254 TNY255 TNY253 TNY254 TNY255 TJ = 25 °C See Note G TNY255 ID = 33 mA See Figure 17 TJ = 25 °C TJ = 25 °C 0.65 x ILIMIT(MIN)

A. For a threshold with a negative value, negative hysteresis is a decrease in magnitude of the corresponding threshold. and the sum of IS2 and IDSS when ENABLE pin is open (MOSFET switching). DRAIN. An alternative is to measure the BYPASS pin current at 6.2 V. D. BYPASS pin is not intended for sourcing supply current to external circuitry. E. See typical performance characteristics section for BYPASS pin start-up charging waveform. F. For current limit at other di/dt values, refer to current limit vs. di/dt curve under typical performance characteristics. Figure 14. TinySwitch General Test Circuit.

5 W S2

NOTE: This test circuit is not applicable for current limit or output characteristic measurements.

Typical Performance Characteristics (Continued) 1.2 1.0 0.8 0.6 0.4 0.2 0.0 0 12.5 25 37.5 50 62.5 75 87.5 100 di/dt in mA/s TNY253 CURRENT LIMIT vs. di/dt PI-2230-082798 Current Limit (Normalized to 12.5 mA/s) 1.4 1.2 1.0 0.8 0.6 0.4 0.2 0.0 0 50 100 150 200 250 di/dt in mA/s TNY254 CURRENT LIMIT vs. di/dt PI-2232-082798 Current Limit (Normalized to 25 mA/s) 1.4 1.2 1.0 0.8 0.6 0.4 0.2 0.0 0 160 320 480 640 800 di/dt in mA/s TNY255 CURRENT LIMIT vs. di/dt PI-2234-082798 Current Limit (Normalized to 80 mA/s) 1.4 1.2 1.0 0.8 0.6 0.4 0.2 0.0 -50 -250 25 50 75 100 125 CURRENT LIMIT vs. TEMPERATURE PI-2236-033001 1.4 Time (ms) BYPASS PIN START-UP WAVEFORM PI-2240-082898 BYPASS Pin Voltage (V) DRAIN Voltage (V) Drain Current (mA) OUTPUT CHARACTERISTIC 300 250 200 100 150 02 46 81 0 PI-2221-033001 TNY253 1.00 TNY254 1.00 TNY255 1.33 Scaling Factors:

A K L G 8 5 C N PDIP-8 (P Package) D S .004 (.10) -E- -D- B -F- DIM A B C G H K L M N P Q Inches 0.367-0.387 0.240-0.260 0.125-0.145 0.015-0.040 0.120-0.140 0.057-0.068 0.014-0.022 0.008-0.015

0.100 BSC

0.030 (MIN) 0.300-0.320 0.300-0.390

0.300 BSC

9.32-9.83 6.10-6.60 3.18-3.68 0.38-1.02 3.05-3.56 1.45-1.73 0.36-0.56 0.20-0.38

2.54 BSC

0.76 (MIN) 7.62-8.13 7.62-9.91

7.62 BSC

Notes: 1. Package dimensions conform to JEDEC specification MS-001-AB for standard dual in-line (DIP) package .300 inch row spacing (PLASTIC) 8 leads (issue B, 7/85). 2. Controlling dimensions are inches. 3. Dimensions shown do not include mold flash or other protrusions. Mold flash or protrusions shall not exceed .006 (.15) on any side. 4. D, E and F are reference datums on the molded body. H M P Q P08A Typical Performance Characteristics (Continued) 100 0 600 DRAIN Voltage (V) DRAIN Capacitance (pF) COSS vs. DRAIN VOLTAGE PI-2223-033001 200 400 TNY253 1.00 TNY254 1.00 TNY255 1.33 Scaling Factors: 0 200 400 600 DRAIN Voltage (V) Power (mW) DRAIN CAPACITANCE POWER PI-2225-033001 TNY253 1.00 TNY254 1.00 TNY255 1.33 Scaling Factors:

A L C G08A SMD-8 (G Package) D S .004 (.10) E S .010 (.25) -E- -D- B -F- M DIM A B C G H K L M P α Inches 0.367-0.387 0.240-0.260 0.125-0.145 0.004-0.012 0.036-0.044 0.057-0.068 0.048-0.053 0.032-0.037 0.007-0.011 0.010-0.012 0.030 (MIN) 0.372-0.388 0-8° mm 9.32-9.83 6.10-6.60 3.18-3.68 0.10-0.30 0.91-1.12 1.45-1.73 1.22-1.35 0.81-0.94 0.18-0.28 0.25-0.30 0.76 (MIN) 9.45-9.86 0-8° Notes: 1. Package dimensions conform to JEDEC specification MS-001-AB (issue B, 7/85) except for lead shape and size. 2. Controlling dimensions are inches. 3. Dimensions shown do not include mold flash or other protrusions. Mold flash or protrusions shall not exceed .006 (.15) on any side. 4. D, E and F are reference datums on the molded body. K Gα H .004 (.10) P .010 (.25) M A S .420 .046 .060 .060 .046 .080Pin 1 .086 .186 .286 Solder Pad Dimensions Revision Notes Date A - 02/99 B 1. Leading edge blanking time (tLEB) typical and minimum values increased to improve design flexibility. 2. Minimum DRAIN supply current (IS1, IS2) eliminated as it has no design revelance. 07/01 C 1. Updated package reference. 2. Corrected VR1 in Figure 12. 3. Corrected storage temperature, θJA and θJC and updated nomenclature in parameter table. 4. Corrected spacing and font sizes in figures. D 1. Corrected θJA for P/G package. 2. Updated DIP-8 and SMD-8 Package Drawings. 3. Figure 10 caption and text description modified. E 1. Changed SOA limit. 02/12

For the latest updates, visit our website: www.powerint.com Power Integrations reserves the right to make changes to its products at any time to improve reliability or manufacturability. Power Integrations does not assume any liability arising from the use of any device or circuit described herein. POWER INTEGRATIONS MAKES NO WARRANTY HEREIN AND SPECIFICALLY DISCLAIMS ALL WARRANTIES INCLUDING, WITHOUT LIMITATION, THE IMPLIED WARRANTIES OF MERCHANTABILITY, FITNESS FOR A PARTICULAR PURPOSE, AND NON-INFRINGEMENT OF THIRD PARTY RIGHTS. Patent Information The products and applications illustrated herein (including transformer construction and circuits external to the products) may be covered complete list of Power Integrations patents may be found at www.powerint.com. Power Integrations grants its customers a license under certain patent rights as set forth at http://www.powerint.com/ip.htm. Life Support Policy POWER INTEGRATIONS PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT DEVICES OR SYSTEMS WITHOUT THE EXPRESS WRITTEN APPROVAL OF THE PRESIDENT OF POWER INTEGRATIONS. As used herein: 1. A Life support device or system is one which, (i) is intended for surgical implant into the body, or (ii) supports or sustains life, and (iii) whose failure to perform, when properly used in accordance with instructions for use, can be reasonably expected to result in significant injury or death to the user. 2. A critical component is any component of a life support device or system whose failure to perform can be reasonably expected to cause the failure of the life support device or system, or to affect its safety or effectiveness. The PI logo, TOPSwitch, TinySwitch, LinkSwitch, DPA-Switch, PeakSwitch, CAPZero, SENZero, LinkZero, HiperPFS, HiperTFS, HiperLCS, Qspeed, EcoSmart, Clampless, E-Shield, Filterfuse, StakFET, PI Expert and PI FACTS are trademarks of Power Integrations, Inc. Other trademarks are property of their respective companies. ©2012, Power Integrations, Inc. Power Integrations Worldwide Sales Support Locations World Headquarters

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