AV2030

AV2030 AVICTEK | Alldatasheet

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@vic AV2030 LINEAR INTEGRATED CIRCUIT QW-R107-004,B 14W HI-FI AUDIO AMPLIFIER

DESCRIPTION

The AVIC AV2030 is a monolithic audio power amplifier integrated circuit.

FEATURES

*Very low external component required. *High current output and high operating voltage. *Low harmonic and crossover distortion. *Built-in Over temperature protection. *Short circuit protection between all pins. *Safety Operating Area for output transistors. TO-220B TO-220-5 PIN CONFIGURATIONS

1 Non inverting input

2 Inverting input

4 Output

ABSOLUTE MAXIMUM RATINGS(Ta=25°C) PARAMETER SYMBOL VALUE UNIT Supply Voltage Vs +-18 V Input Voltage Vi Vs V Differential Input Voltage Vdi +-15 V Peak Output Current(internally limited) Io 3.5 A Total Power Dissipation at Tcase=90°C Ptot 20 W Storage Temperature Tstg -40~+150 °C Junction Temperature Tj -40~+150 °C

ELECTRICAL CHARACTERISTICS

(Refer to the test circuit, Vs =+-16V,Ta=25°C) PARAMETER SYMBOL TEST CONDITIONS MIN TYP MAX UNIT Supply Voltage Vs +-6 +-18 V Quiescent Drain Current Id 40 60 mA Input Bias Current Ib 0.2 2 µA Input Offset Voltage Vos Vs=+-18v +-2 +-20 MV Input Offset Current Ios +-20 +-200 NA

QW-R107-004,B (Continued) d=0.5%,Gv=30dB f=40 to 15,000Hz O u t p u t P o w e r P o R L = 4 Ω 12 14 W R L = 8 Ω 8 9 W d=10%,Gv=30dB f = 1 K H z R L = 4 Ω 18 W R L = 8 Ω 11 W Power Bandwidth B Po=12W,RL=4 Ω, Gv=30dB 10~140,000 Hz Open Loop Voltage Gain Gvo 90 dB Closed Loop Voltage Gain Gvc f=1kHz 29.5 30 30 .5 dB Distortion d Po=0.1 to 12W,RL=4 Ω f=40 to 15,000Hz, Gv=30dB 0.2 0.5 % Po=0.1 to 8W,RL=8 Ω f=40 to 15,000Hz, Gv=30dB 0.1 0.5 % Input Noise Voltage e N B= 22Hz to 22kHz 3 10 µV Input Noise Current i N B= 22Hz to 22kHz 80 200 pA Input Resistance(pin 1) Ri 0.5 5 M Ω Supply Voltage Rejection SVR RL=4 Ω,Gv=30dB Rg=22kΩ,f ripple=100Hz, Vripple=0.5Veff 40 50 dB Thermal Shut-Down Junction Temperature Tj 145 °C @vic AV2030 LINEAR INTEGRATED CIRCUIT

QW-R107-004,B TEST CIRCUIT APPLICATION CIRCUIT UTC TDA2030 2 3 Vi +Vs -Vs 1 µF 22 µF 100 µF 100nF 220nF 100nF 100 µF 1N4001 1N4001 22kΩ 22kΩ R5 C8 R4 RLR3 680Ω UTC TDA2030 2 3 Vi +Vs -Vs 1 µF 22 µF 100 µF 100nF 220nF 100nF 220 µF 1N4001 1N4001 22kΩ 13kΩ RLR3 680Ω @vic AV2030 LINEAR INTEGRATED CIRCUIT

QW-R107-004,B TYPICAL PERFORMANCE CHARACTERISTICS 102 103 104 105 106 107101-60 -20 100 140 Phase Gain Gv (dB) 180 Phase Fig.2 Open loop frequency response 24 28 32 36 40 44 RL=4Ω RL=8Ω Gv=26dB d=0.5% f=40 to 15kHz Fig.3 Output power vs. Supply voltage Fig.4 Total harmonic distortion vs. output power Fig.5 Two tone CCIF intermodulation distortion 10-1 100 101 10210-2 10-2 10-1 100 101 102 Vs=38V RL=8Ω Vs=32V RL=4Ω f=15kHz f=1kHz Gv=26dB 101 102 10-2 10-1 100 101 102 103 104 105 Order (2f1-f2) Order (2f2-f1) Vs=32V Po=4W RL=4 Ω Gv=26dB Fig.6 Large signal frequency response Fig.7 Maximum allowable power dissipation vs. ambient temperture 101 102 103 104 Vs=+-15V RL=4 Ω Vs=+-15V RL=8Ω -50 0 50 100 150 200 infinite heatsink heatsink having Rty=25°C/W heatsink having Rth=4°C/Wheatsink having Rth=8°C/W Tamb (°C) Ptot (W) Frequency (kHz) Vo (Vp-p) Po (W) Frequency (Hz) Po (W) Vs (V)Frequency (Hz) Po (W) d ( % ) d ( % ) @vic AV2030 LINEAR INTEGRATED CIRCUIT

QW-R107-004,B UTC TDA2030 2 3 Vi +Vs 0.22 µF 56kΩ RL=4Ω 3.3kΩ 1N4001 10 µF 56kΩC1 2.2 µF 56kΩ 22 µF 220 µF /40V 2200 µF 1.5Ω 0.22 µF 30kΩ 1.5Ω 1N4001 0.22 µF BD908 BD907 Fig. 8 Single supply high power amplifier(UTC TDA2030+BD908/BD907) TYPICAL PERFORMANCE OF THE CIRCUIT OF FIG. 8 PARAMETER SYMBOL TEST CONDITIONS MIN TYP MAX UNIT Supply Voltage Vs 36 44 V Quiescent Drain Current Id Vs=36V 50 mA d=0.5%,RL=4 Ω f=40Hz to 15kHz,Vs=39V Output Power Po d=0.5%,RL=4Ω f=40Hz to 15kHz,Vs=36V W d=0.5%,f=1kHz, RL=4Ω,Vs=39V d=0.5%,RL=4 Ω f=1kHz,Vs=36V Voltage Gain Gv f=1kHz 19.5 20 20.5 dB Slew Rate SR 8 V/ µsec Total Harmonic d Po=20W,f=1kHz 0.02 % Distortion Po=20W,f=40Hz to 15kHz 0.05 % Input Sensitivity Vi Gv=20dB,Po=20W, f=1kHz,RL=4Ω 890 mV Signal to Noise S/N RL=4Ω,Rg=10kΩ B=curve A,Po=25W 108 dB Ratio RL=4 Ω,Rg=10kΩ B=curve A,Po=25W 100 @vic AV2030 LINEAR INTEGRATED CIRCUIT

QW-R107-004,B TYPICAL PERFORMANCE CHARACTERISTICS 24 28 32 34 36 40 Fig. 10 Output power vs. supply voltage Po (W) Vs (V) 10-1 100 101 10-2 10-1 100 f=15kHz f=1kHz Vs=36V RL=4Ω Gv=20dB d (%) Po (W) Fig. 11 Total harmonic distortion vs. output power 100 250 400 550 700 Gv=26dB Gv=20dB Vi (mV) Po (W) Fig. 12 Output power vs. Input level 0 8 16 24 32 Po (W) Ptot (W) Complete Amplifier BD908/ BD907 UTC TDA2030 Fig. 13 Power dissipation vs. output power @vic AV2030 LINEAR INTEGRATED CIRCUIT

QW-R107-004,B Fig. 14 Typical amplifier with split power supply Fig. 16 Bridge amplifier with split power supply(Po=34W,Vs+=16V,Vs-=16V) UTC TDA2030 2 3 Vi +Vs -Vs 1 µF 22 µF 100 µF 100nF 220nF 100nF 100 µF 1N4001 1N4001 22kΩ 22kΩ R5 C8 R4 RLR3 680Ω UTC TDA2030 UTC TDA2030 220 µF 100 µF 100nF 2 3 2 3 0.22 µF 22 µF 0.22 µF 22 µF 100nF 100 µF 22kΩ 22kΩ 680Ω 680Ω 22kΩ 22kΩ 22kΩ Vs+ Vs- IN RL @vic AV2030 LINEAR INTEGRATED CIRCUIT

QW-R107-004,B MULTIWAY SPEAKER SYSTEMS AND ACTIVE BOXES Multiway loudspeaker systems provide the best possible acoustic performance since each loudspeaker is specially designed and optimized to handle a limited range of frequencies. Commonly, these loudspeaker systems divide the audio spectrum two or three bands. To maintain a flat frequency response over the Hi-Fi audio range the bands cobered by each loudspeaker must overlap slightly. Imbalance between the loudspeakers produces unacceptable results therefore it is important to ensure that each unit generates the correct amount of acoustic energy for its segments of the audio spectrum. In this respect it is also important to know the energy distribution of the music spectrum to determine the cutoff frequencies of the crossover filters(see Fig. 18).As an example,1 100W three-way system with crossover frequencies of 400Hz and 3khz would require 50W for the woofer,35W for the midrange unit and 15W for the tweeter. Both active and passive filters can be used for crossovers but active filters cost significantly less than a good passive filter using aircored inductors and non-electrolytic capacitors. In addition active filters do not suffer from the typical defects of passive filters: --Power less; --Increased impedance seen by the loudspeaker(lower damping) --Difficulty of precise design due to variable loudspeaker impedance. Obviously, active crossovers can only be used if a power amplifier is provide for each drive unit. This makes it particularly interesting and economically sound to use monolithic power amplifiers. In some applications complex filters are not relay necessary and simple RC low-pass and high-pass networks(6dB/octave) can be recommended. The result obtained are excellent because this is the best type of audio filter and the only one free from phase and transient distortion. The rather poor out of band attenuation of single RC filters means that the loudspeaker must operate linearly well beyond the crossover frequency to avoid distortion. A more effective solution, named "Active power Filter" by SGS is shown in Fig. 19. The proposed circuit can realize combined power amplifiers and 12dB/octave or 18dB octave high-pass or low-pass filters. In proactive, at the input pins amplifier two equal and in-phase voltages are available, as required for the active filter operations. The impedance at the Pin(-) is of the order of 100 Ω,while that of the Pin (+) is very high, which is also what was wanted. 102 103 104 105101 100

80 Morden

Fig. 18 Power distribution vs. frequency Vs+ Vs- 3.3kΩ 100Ω R2R1 C1 C2 C3 RL Fig. 19 Active power filter @vic AV2030 LINEAR INTEGRATED CIRCUIT

QW-R107-004,B The components values calculated for fc=900Hz using a Bessel 3rd Sallen and Key structure are: C1=C2=C3=22nF,R1=8.2K Ω,R2=5.6KΩ,R3=33KΩ. Using this type of crossover filter, a complete 3-way 60W active loudspeaker system is shown in Fig. 20. It employs 2nd order Buttherworth filter with the crossover frequencies equal to 300Hz and 3kHz. The midrange section consistors of two filters a high pass circuit followed by a low pass network. With Vs=36V the output power delivered to the woofer is 25W at d=0.06%( 30W at d=0.5%).The power delivered to the midrange and the tweeter can be optimized in the design phase taking in account the loudspeaker efficiency and impedance(RL=4Ω to 8Ω). It is quite common that midrange and tweeter speakers have an efficiency 3dB higher than woofers. UTC TDA2030 UTC TDA2030 UTC TDA2030 0.22 µF 2200 µF18nF 33nF 100 µF 0.22 µF 1N4001 1 µF 0.1 µF0.1 µF 0.22 µF Vs+ 18nF 3.3nF 100 µF 0.22 µF 0.1 µF0.1 µF 47 µF 0.22 µF 100 µF 0.22 µF 220 µF 0.22 µF 2200 µF 1N4001 BD908 BD907 22kΩ 1.5Ω1.5Ω 3.3kΩ 22kΩ 22kΩ 680Ω 100Ω 22kΩ22kΩ 6.8kΩ 3.3kΩ 100Ω 2.2kΩ Vs+ 1N4001 1N4001 1N4001 2.2kΩ 12kΩ100Ω 22kΩ 22kΩ 22kΩ Vs+ 100 µF Vs+ IN Woofer Midrange TweeterHigh-pass 3kHz High-pass 3kHz Band-pass 300Hz to 3kHz Low-pass 300Hz 1N4001 @vic AV2030 LINEAR INTEGRATED CIRCUIT

QW-R107-004,B MUSICAL INSTRUMENTS AMPLIFIERS Another important field of application for active system is music. In this area the use of several medium power amplifiers is more convenient than a single high power amplifier, and it is also more reliable. A typical example(see Fig. 21) consist of four amplifiers each driving a low-cost, 12 inch loudspeaker. This application can supply 80 to 160W rms. TRANSIENT INTER-MODULATION DISTORTION(TIM) Transient inter-modulation distortion is an unfortunate phenomena associated with negative-feedback amplifiers. When a feedback amplifier receives an input signal which rises very steeply, i.e. contains high-frequency components, the feedback can arrive too late so that the amplifiers overloads and a burst of inter-modulation distortion will be produced as in Fig.22.Since transients occur frequently in music this obviously a problem for the designed of audio amplifiers. Unfortunately, heavy negative feedback is frequency used to reduce the total harmonic distortion of an amplifier, which tends to aggravate the transient inter-modulation(TIM situation.)The best known 20 to 40W Amplifier 20 to 40W Amplifier 20 to 40W Amplifier 20 to 40W Amplifier PRE AMPLIFIER POWER AMPLIFIER FEEDBACK PATH INPUT V1 V2 V3 V4 V4汕 OUTPUT Fig.21 High power active box for musical instrument Fig.22 Overshoot phenomenon in feedback amplifiers method for the measurement of TIM consists of feeding sine waves superimposed onto square wavers, into the amplifier under test. The output spectrum is then examined using a spectrum analyzer and compared to the input. This method suffers from serious disadvantages: the accuracy is limited, the measurement is a tatter delicate operation and an expensive spectrum analyzer is essential. A new approach (see Technical Note 143(Applied by SGS to monolithic amplifiers measurement is fast cheap, it requires nothing more sophisticated than an oscilloscope-and sensitive-and it can be used down to the values as low as 0.002% in high power amplifiers. The "inverting-sawtooth" method of measurement is based on the response of an amplifier to a 20KHz saw-tooth wave-form. The amplifier has no difficulty following the slow ramp but it cannot follow the fast edge. The output will follow the upper line in Fig.23 cutting of the shade area and thus increasing the mean level. If this output signal is filtered to remove the saw-tooth, direct voltage remains which indicates the amount of TIM distortion, although it is difficult to measure because it is indistinguishable from the DC offset of the amplifier. This problem is neatly avoided in the IS-TIM method by periodically inverting the saw-tooth wave-form at a low audio frequency as shown in Fig.24.Inthe case of the saw-tooth in Fig. 25 the means level was increased by the TIM distortion, for a saw-tooth in the other direction the opposite is true. @vic AV2030 LINEAR INTEGRATED CIRCUIT

QW-R107-004,B SR(V/µs) Input Signal Filtered Output Siganal F i g . 2 3 2 0 k H z s a w t o o t h w a v e f o r m F i g . 2 4 I n v e r t i n g s a w t o o t h w a v e f o r m The result is an AC signal at the output whole peak-to-peak value is the TIM voltage, which can be measured easily with an oscilloscope. If the peak-topeak value of the signal and the peak-to-peak of the inverting sawtooth are measured, the TIM can be found very simply from: TIM VOUT Vsawtooth * 100= 10-1 100 101 102 10-2 10-1 100 101 UTC2030A BD908/907 Gv=26dB Vs=36V RL=4 Ω RC Filter fc=30kHz Fig. 25 TIM distortion Vs. Output Power Po(W) TIM(%) 10-1 100 101 102 Vo(Vp-p) 10-1 100 101 102 RC Filter fc=30kHz Fig. 26 TIM design diagram(fc=30kHz) TIM =0.1 TIM =0.01 TIM SR(V/ s)米 In Fig.25 The experimental results are shown for the 30W amplifier using the UTC2030A as a driver and a low-cost complementary pair. A simple RC filter on the input of the amplifier to limit the maximum signal slope(SS) is an effective way to reduce TIM. The Diagram of Fig.26 originated by SGS can be used to find the Slew-Rate(SR) required for a given output power or voltage and a TIM design target. For example if an anti-TIM filter with a cutoff at 30kHz is used and the max. Peak to peak output voltage is 20V then, referring to the diagram, a Slew-Rate of 6V/µs is necessary for 0.1% TIM. As shown Slew-Rates of above 10V/µs do not contribute to a further reduction in TIM. Slew-Rates of 100V/ µs are not only useless but also a disadvantage in hi-fi audio amplifiers because they tend to turn the amplifier into a radio receiver. POWER SUPPLY Using monolithic audio amplifier with non regulated supply correctly. In any working case it must provide a supply voltage less than the maximum value fixed by the IC breakdown voltage. @vic AV2030 LINEAR INTEGRATED CIRCUIT

QW-R107-004,B It is essential to take into account all the working conditions, in particular mains fluctuations and supply voltage variations with and without load. The UTC2030(Vsmax=44V) is particularly suitable for substitution of the standard IC power amplifiers(with Vsmax=36V) for more reliable applications. An example, using a simple full-wave rectifier followed by a capacitor filter, is shown in the table and in the diagram of Fig.27. A regulated supply is not usually used for the power output stages because of its dimensioning must be done taking into account the power to supply in signal peaks. They are not only a small percentage of the total music signal, with consequently large overdimensioning of the circuit. Even if with a regulated supply higher output power can be obtained(Vs is constant in all working conditions),the additional cost and power dissipation do not usually justify its use. using non-regulated supplies, there are fewer designee restriction. In fact, when signal peaks are present, the capacitor filter acts as a flywheel supplying the required energy. In average conditions, the continuous power supplied is lower. The music power/continuous power ratio is greater in case than for the case of regulated supplied, with space saving and cost reduction. Vo(V) Io(A) Fig.27 DC characteristics of 50W non-regulated supply Vo 3300 µF 220V Ripple (Vp-p) Ripple Vout Mains(220V) Secondary Voltage DC Output Voltage(Vo) Io=0 Io=0.1A Io=1A +20% 28.8V 43.2V 42V 37.5V +15% 27.6V 41.4V 40.3V 35.8V +10% 26.4V 39.6V 38.5V 34.2V — 24V 36.2V 35V 31V -10% 21.6V 32.4V 31.5V 27.8V -15% 20.4V 30.6V 29.8V 26V -20% 19.2V 28.8V 28V 24.3 @vic AV2030 LINEAR INTEGRATED CIRCUIT

QW-R107-004,B SHORT CIRCUIT PROTECTION The UTC TDA2030 has an original circuit which limits the current of the output transistors. This function can be considered as being peak power limiting rather than simple current limiting. It reduces the possibility that the device gets damaged during an accidental short circuit from AC output to Ground. THERMAL SHUT-DOWN The presence of a thermal limiting circuit offers the following advantages: 1).An overload on the output (even if it is permanent),or an above limit ambient temperature can be easily supported since the Tj can not be higher than 150°C 2).The heatsink can have a smaller factor of safety compared with that of a congenital circuit, There is no possibility of device damage due to high junction temperature increase up to 150, the thermal shut-down simply reduces the power dissipation and the current consumption. APPLICATION SUGGESTION The recommended values of the components are those shown on application circuit of Fig.14. Different values can be used. The following table can help the designer. COMPONENT RECOMMENDED VALUE PURPOSE LARGE THAN RECOMMENDED VALUE LARGE THAN RECOMMENDED VALUE R1 22K Ω Closed loop gaon setting. Increase of Gain Decrease of Gain R2 680 Ω Closed loop gaon setting. Decrease of Gain Increase of Gain R3 22K Ω Non inverting input biasing Increase of input impedance Decrease of input impedance R4 1 Ω Frequency stacility Danger of oscillation at high frequencies with inductive loads. R5 ≈3R2 Upper frequency cutoff Poor high frequencies attenuation Dange of oscillation C1 1 µF Input DC decoupling Increase of low frequencies cutoff C2 22 µF Inverting DC decoupling Increase of low frequencies cutoff C3,C4 0.1 µF Supply voltage bypass Dange of oscillation C5,C6 100 µF Supply voltage bypass Dange of oscillation C7 0.22 µF Frequency stability Larger bandwidth C8 ≈1/(2π*B*R1) Upper frequency cutoff smaller bandwidth Larger bandwidth D1,D2 1N4001 To protect the device against output voltage spikes. @vic AV2030 LINEAR INTEGRATED CIRCUIT