U4221B

U4221B TEMIC | Alldatasheet

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Technical content

Features

/C0068Low power consumption /C0068Very high sensitivity /C0068High selectivity by quartz resonator /C0068Stop-function available /C0068Only a few external components necessary /C0068Digitized serial output signal Block Diagram Demodulator ComparatorPower supply Amplifier 1 Amplifier 2 AGC CCAV GND PON CCDV 13 10 914 CAGC CDEMINA2OUTA1 765 GND (digital) GND (analog) IN2 IN1 Driver 93 7506 e TCO FSI NC FSS Figure 1.

Rev. A1, 15-May-96 Preliminary Information 2 (12) Pin Description Pin Symbol Function

1 IN2 Amplifier 1 - Input 2

2 IN1 Amplifier 1 - Input 1

3 GND Analog ground

4 CAGC Time constant of AGC

5 CDEM Low pass filter

6 INA2 Amplifier 2 input

7 GND Digital ground

8 OUTA1 Amplifier 1 output

9 V CCD Supply voltage (digital)

10 NC Not connected

11 FSS Field strength select

12 FSI Field strength indication

13 TCO Time code output

14 PON Power ON/OFF control

15 GND Ground (substrate)

16 V CCA Supply voltage (analog)

IN1, IN2 IN2 is connected to Pin 16 (VCCA ). A ferrite antenna is connected between IN1 and IN2. Q of antenna circuit should be as high as possible, but the temperature influence must be compensated. The resonant resistance should be 200 k/C0087 to 300 k/C0087 for optimal sensitivity. OUTA1, INA2 To achieve a high selectivity, a quartz resonator is connected between the pins OUTA1 and INA2. It is used with the serial resonance frequency of the time code transmitter (e.g. 60 kHz WWVB, 77.5 kHz DCF). The parasitic parallel capacitance C 0 of the quartz resonator should be 0.5 pF to 1 pF. CAGC A control voltage derived from the field strength is generated to control the amplifiers. The time constant of this automatic gain control (AGC) is influenced by the capacitor CAGC. CDEM After demodulation the signal is low pass filtered by the capacitor CDEM. PON If PON is connected to VCCD, the U4221B receiver IC will be activated. The set-up time is typical 2.5 s after ap- plying V CCD at this pin. If PON is connected to GND, the receiver will go into stop mode. FSS This pin is connected to GND, otherwise the field strength indication FSI is disabled. FSI If the voltage at the input of amplifier 1 is higher than about 5 /C0109V , FSI will be high.

Rev. A1, 15-May-96 3 (12) TCO The digitized serial signal of the time code transmitter can be directly decoded by a microcomputer. Details about the time code format of several transmitters are described separately. The output consists of a PNP current source and a NPN switching transistor T S. The guaranteed source output current is 0.2 µA (TCO = high) and the sink current is 1 µA (TCO = low). Considering these output currents, the supply voltage and the switching levels of the following µC, the lowest load resistance is defined. The maximum load capacitance is 100 pF. In order to improve the driving capability an external pull-up resistor can be used. The value of the resistor should be 4.7 M/C0087. To prevent an undefined output vol- tage in the power-down state of the U4221B, the use of this pull-up resistor is recommended. An additional improvement of the driving capability may be achieved by using a CMOS driver circuit or a NPN transistor with pull-up resistor connected to the collector (see figure 2). Using a CMOS driver this circuit must be connected to V CCD . 100 k/C0087 V CCD pin13 TCO

4.7 M/C0087

0.2 /C0109A ISINK 1 /C0109A pin 9 93 7689 e Figure 2. Functional Description The following description gives you some additional information and hints in order to facilitate your design, in particular the problems of the antenna. Figure 3 shows the principal function of the receiver (simplified consideration). resR Demodulator Comparator CF 93 7521 e A 2 and Figure 3. R res: resonant resistance, A1: preamplifier, A2: amplifier 2, CF: crystal filter Condition for signal reception: S/N ≈ 4 at comparator input. Important parameters are: V NA = (4 k T Rres)1/2 BW A = fres/QA input noise voltage density of preamplifier: V NA1 : 40 nV/Hz1/2 (typ) bandwidth of preamplifier: BW A1 : 60 kHz (typ) bandwidth of crystal filter: BW CF : 16 Hz (typ) ultimate attenuation of crystal filter: D CF : –35 dB (typ) whereas: V NA antenna noise voltage density k 1.38 /C006410–23 Ws/K (Boltzmann constant) T absolute temperature BW A bandwidth of antenna fres resonant frequency Q A Q antenna The equivalent input noise voltage at the preamplifier in- put is: V N /C0043/C0466V NA /C0064BW CF/C0504/C0467 /C0041/C0466V NA /C0064BW A/C0504 D CF /C0467 /C0041/C0064 /C0064/C0504 /C0064/C0064/C0064 /C0041/C0466V NA1 /C0064BW CF/C0504/C0467 /C0041/C0466V NA1 /C0064BW A1/C0504 D CF /C0467 whereas: R res = 300 k/C0087, BWA = 1 kHz then VN ≈ 0.4 /C0109V The condition for signal reception is: S/N ≈ 4 ⇒ sensitivity ≈ 1.6 /C0109V That means that the noise voltage of antenna within the bandwidth of the crystal filter dominates and the bandwidth of antenna is uncritical for the sensitivity aspect.

Rev. A1, 15-May-96 Preliminary Information 4 (12) There is some consideration concerning the calculation of R res: in order to achieve high signal voltage: R res should be high in order to achieve low antenna noise voltage: R res should be low R res < 200 k/C0087: the input noise voltage of A 1 dominates R res > 300 k/C0087: the antenna noise voltage dominates That means the resonant resistance should be between 200 k/C0087 and 300 k/C0087/C0046 Q of antenna must be high for attenuation of interfering signals. But the temperature must not influence the resonance frequency. Design Hints for the Ferrite Antenna The bar antenna is the most critical device of the complete clock receiver. But by observing some basic rf design knowledge, no problem should arise with this part. The IC requires a resonance resistance of 200 k/C0087 to 300 k/C0087. This can be achieved by a variation of the L/C-relation in the antenna circuit. But it is not easy to measure such high resistances in the RF region. It is much more convenient to distinguish the bandwidth of the antenna circuit and afterwards to calculate the resonance resistance. Thus the first step in designing the antenna circuit is to measure the bandwidth. Figure 4 shows an example for the test circuit. The RF signal is coupled into the bar antenna by inductive means, e.g. a wire loop. It can be measured by a simple oscilloscope using the 10:1 probe. The input capacitance of the probe, typically about 10 pF, should be taken into consideration. By varying the frequency of the signal generator, the resonance frequency can be determined. ScopeRF - Signal generator 77.5 kHz C res Probe 10 : 1 wire loop 94 7907 e /C011910 M /C0087 Afterwards, the two frequencies where the voltage of the rf signal at the probe drops 3 dB down can be measured. The difference between these two frequencies is called the bandwidth BWA of the antenna circuit. As the value of the capacitor Cres in the antenna circuit is well known, it is easy to compute the resonance resistance according to the following formula: R res /C00431 2 /C0064/C0112/C0064BW A /C0064C res whereas R res is the resonance resistance, BW A is the measured bandwidth (in Hz) C res is the value of the capacitor in the antenna circuit (in Farad) If high inductance values and low capacitor values are used, the additional parasitic capacitances of the coil must be considered. It may reach up to about 20 pF. The Q-value of the capacitor should be no problem if a high Q-type is used. The Q-value of the coil is more or less dis- tinguished by the simple DC-resistance of the wire. Skin effects can be observed but do not dominate. Therefore it should be no problem to achieve the recommended values of resonance resistance. The use of thicker wire increases Q and accordingly reduces bandwidth. This is advantageous in order to improve reception in noisy areas. On the other hand, temperature compensation of the resonance frequency might become a problem if the bandwidth of the antenna circuit is low compared to the temperature variation of the resonance frequency. Of course, Q can also be reduced by a parallel resistor. Temperature compensation of the resonance frequency is a must if the clock is used at different temperatures. Please ask your dealer of bar antenna material and of capacitors for specified values of temperature coefficient. Furthermore some critical parasitics have to be considered. These are shortened loops (e.g. in the ground line of the PCB board) close to the antenna and undesired loops in the antenna circuit. Shortened loops decrease Q of the circuit. They have the same effect like conducting plates close to the antenna. To avoid undesired loops in the antenna circuit it is recommended to mount the capac- itor C res as close as possible to the antenna coil or to use a twisted wire for the antenna coil connection. This twisted line is also necessary to reduce feedback of noise from the microprocessor to the IC input. Long connection lines must be shielded. For the adjustment of the resonance frequency the capacitance of the probe and the input capacitance of the IC are to be taken into account. The alignment should be done in the final environment. The bandwidth is so low that metal parts close to the antenna influence the resonance frequency. The adjustment can be done by pushing the coil along the bar antenna.

Rev. A1, 15-May-96 5 (12) Absolute Maximum Ratings Parameters Symbol Value Unit Supply voltage V CC 5.5 V Ambient temperature range Tamb –20 to +70 /C0095C Storage temperature range R stg –30 to +85 /C0095C Junction temperature Tj 125 /C0095C Electrostatic handling (MIL Standard 883°C) ± V ESD 2000 V Thermal Resistance Parameters Symbol Value Unit Thermal resistance R thJA 70 K/W

Electrical Characteristics

V CCA , VCCD = 3.0 V , reference point Pins 3, 7, 15, input signal according to DCF 77 transmitter, Tamb = 25/C0095C, unless otherwise specified Parameters Test Conditions / Pins Symbol Min. Typ. Max. Unit Supply voltage range Pins 9, 16V CCA V CCD 2.4 5.5 V Supply current I CC = ICCA + ICCD Pins 9, 16 without reception signal with reception signal > 20 /C0109V OFF-mode ICC 0.2 /C0109A /C0109A /C0109A Reception frequency range fin 60 80 kHz Minimum input voltage R gen = 50 /C0087 Pins 1,2 R res /C0118 300 k/C0087, Qres > 30 V in 1.5 1.75 /C0109V Maximum input voltage R gen = 50 /C0087 Pins 1,2 R res /C0118 300 k/C0087, Qres > 30 V in 40 mV Input capacitances to ground Pins 1, 2C in 1 C in 2 pF Set-up time after POWER ON tpon 2.5 5 s TIMING CODE OUTPUT; TCO Pin 13 Output voltage HIGH LOW R LOAD = 13 M/C0087 to GND R LOAD = 2.6 M/C0087 to VCCD V OH V OL V CCD -0.4 0.4 V V Output current HIGH LOW V TCO = VCCD/2 V TCO = VCCD/2 ISOURCE ISINK 0.2 0.4 /C0109/C0065 /C0109/C0065 Decoding characteristics input carrier reduction 100 ms input carrier reduction 200 ms t100 t200 150 110 230 ms ms POWER ON/OFF CONTROL; PON Pin 14 Input voltage HIGH LOW Generator output resistance /C0118 200 k/C0087 V CCD –0.4 0.4 V V

Rev. A1, 15-May-96 Preliminary Information 6 (12) Parameters Test Conditions / Pins Symbol Min. Typ. Max. Unit FIELD STRENGTH INDICATION; FSI Pin 12 Output voltage HIGH LOW R LOAD = 13 M/C0087 to GND R LOAD = 2.6 M/C0087 to VCCD V CC –0.4 0.4 V Output current HIGH LOW V TCO = VCCD/2 V TCO = VCCD/2 0.2 1.0 0.4 4.0 /C0109/C0065 /C0109/C0065 FIELD STRENGTH SELECT; FSS Pin 11 Input voltage HIGH LOW Generator output resistance /C0118 200 k/C0087 V CC –0.4 0.4 V V Test Circuit for DCF U 4221 B Measurement point 100 n 50 k /C0053/C0048 /C0053/C0048 77,5 kHz Generator 220 n 47 n 77.5 kHz (with variable output level) Electronic switch (Time Code) T 1 s Measuring device: Oscilloscope with high impedance /C0119 V CCD –0.8 V Receiver input signal calibration: Example: 2 /C0109 V eff input signal ⇒ 2 /C0001 2 /C0001 2 /C0001 103 = 5.65 mVpp at measurement point +V CC PON TCO It must be noted: Input is shortened by 50 /C0087/C0044 that means, the antenna noise is not taken into consideration. Modulation depth adjustment by potentiometer (carrier reduced to 25%) 100 /C0087 93 7719 e T = 100 ms (binary “0”) or 200 ms (binary “1”) probe(/C0119 20 M/C0087)

Rev. A1, 15-May-96 7 (12) Application Circuit for DCF 77.5 kHz CC+V CONTROL LINES DISPLAY KEYBOARD MICROCOMPUTER 47 nF PON Ferrite Antenna 220 nF 77.5 kHz U 4221 B 93 7504 e TCO Application Circuit for WWVB 60 kHz CC+V CONTROL LINES DISPLAY KEYBOARD MICROCOMPUTER 47 nF PON Ferrite Antenna 220 nF 60 kHz U 4221 B 94 7906 e TCO

Rev. A1, 15-May-96 Preliminary Information 8 (12) Information Regarding German Transmitter Station: DCF 77, Frequency 77.5 kHz, Transmitting power 50 kW Location: Mainflingen/Germany, Geographical coordinates: 50/C0095 0.1’N, 09/C0095 00’E Time of transmission: permanent 0 5 10 15 20 25 30 40 50 55 0 5 10 coding when required minutes hours day of the week month year 35 45 21 22 23 24 25 26 27 28 30 29 31 32 33 34 35 1248 10 20 40 P1 1 2 4 81 0 2 0 P2 Z1Z2 S R P11 2040 Time Frame 1 Minute ( index count 1 second ) Time Frame calendar day minutes hours 20sec. s Start Bit Parity Bit P1 Parity Bit P2 Example:19.35 h 93 7527 Modulation: The carrier amplitude is reduced to 25% at the beginning of each second for 100 ms (binary zero) or 200 ms (binary one) duration, excepting the 59th second. Time Code Format: (based on information of Deutsche Bundespost) It consists of 1 minute time frames. No modulation at the beginning of the 59th second to recognize the switch over to the next 1 minute time frame. A time frame contains BCD-coded information of minutes, hours, calendar day, day of the week, month and year between the 20th second and 58th second of the time frame, including the start bit S (200 ms) and parity bits P1, P2 and P3. Further there are 4 additional bits R (transmission by reserve antenna), A1 (announcement of change-over to the summer time), Z1 (during the summer time 200 ms, otherwise 100 ms), Z2 (during standard time 200 ms otherwise 100 ms) and A2 (announcement of leap second) transmitted between the 15th second and 19th second of the time frame.

Rev. A1, 15-May-96 9 (12) Information Regarding British Transmitter Station: MSF Frequency 60 kHz Transmitting power 50 kW Location: Teddington, Middlesex Geographical coordinates: 52/C0095 22’N, 01/C0095 11’W Time of transmission: permanent, excepting the first Tuesday of each month from 10.00 h to 14.00 h. 05 10 15 20 25 30 40 50 55 05 1 035 45 year day of month month day of week hour minute minute identifier hour + minute day of week day + month year TIME FRAME 1 MINUTE TIME FRAME( index count 1 second) Parity check bits BST BST 7 GMT change impending 500 ms500 ms switch over to the next time frame 80 40 20 10 42 1 108 8 4 2 1 18 19 20 21 22 23 24 25 26 27 28 29 30 year month 17seconds 93 7528 0 1 Example: March 1993 Modulation: The carrier amplitude is reduced at the beginning of each second for the time of 100 ms (binary zero) or 200 ms (binary one). Time Code Format: It consists of 1 minute time frames. A time frame contains BCD-coded information of year, month, calendar day, day of the week, hours and minutes. At the switch-over to the next time frame, the carrier amplitude is reduced for 500 ms duration.

Rev. A1, 15-May-96 Preliminary Information 10 (12) Information Regarding US Transmitter Station: WWVB Frequency 60 kHz Transmitting power 10 kW Location: Fort Collins Geographical coordinates: 40/C0095 40’N, 105/C0095 03’W Time of transmission: permanent. 0 51 0 2 0 2 5 30 40 50 55 0 51 0 TIME FRAME 35 45 P0 40 20 10 8421 P 1 0 1 2 35 4 6 7 89 10 11 12 13 14 15 16 17 18 19 20 P220 10 8 4 2 1 hours hours minutes minutes days FRM 100 200 2010 ADD SUBADD P4800 400 200 100 4020 UTI UTIsign correctionyear daylight savings time bits leap second warning bit leap year indicator bit ”0” = non leap year ”1” = leap year TIME FRAME 1 MINUTE ( index count 1 second) TIME FRAME Frame reference marker seconds 93 7529 e Example: UTC 18.42 h Modulation: The carrier amplitude is reduced at the beginning of each second and is restored in 500 ms (binary one) or in 200 ms (binary zero). Time Code Format: It consists of 1 minute time frames. A time frame contains BCD-coded information of minutes, hours, days and year. In addition there are 6 position identifier markers (P0 thru P5) and 1 frame reference marker with reduced carrier amplitude of 800 ms duration.

Rev. A1, 15-May-96 11 (12) Ordering and Package Information Extended Type Number Package Remarks U4221B-BFP SO16 plastic U4221B-BFPG1 SO16 plastic Taping according to IEC-286-3

Rev. A1, 15-May-96 Preliminary Information 12 (12) Ozone Depleting Substances Policy Statement It is the policy of TEMIC TELEFUNKEN microelectronic GmbH to 1. Meet all present and future national and international statutory requirements. 2. Regularly and continuously improve the performance of our products, processes, distribution and operating systems with respect to their impact on the health and safety of our employees and the public, as well as their impact on the environment. It is particular concern to control or eliminate releases of those substances into the atmosphere which are known as ozone depleting substances (ODSs). The Montreal Protocol (1987) and its London Amendments (1990) intend to severely restrict the use of ODSs and forbid their use within the next ten years. Various national and international initiatives are pressing for an earlier ban on these substances. TEMIC TELEFUNKEN microelectronic GmbH semiconductor division has been able to use its policy of continuous improvements to eliminate the use of ODSs listed in the following documents. 1. Annex A, B and list of transitional substances of the Montreal Protocol and the London Amendments respectively 2. Class I and II ozone depleting substances in the Clean Air Act Amendments of 1990 by the Environmental Protection Agency (EPA) in the USA 3. Council Decision 88/540/EEC and 91/690/EEC Annex A, B and C (transitional substances) respectively. TEMIC can certify that our semiconductors are not manufactured with ozone depleting substances and do not contain such substances. We reserve the right to make changes to improve technical design and may do so without further notice. Parameters can vary in different applications. All operating parameters must be validated for each customer application by the customer. Should the buyer use TEMIC products for any unintended or unauthorized application, the buyer shall indemnify TEMIC against all claims, costs, damages, and expenses, arising out of, directly or indirectly, any claim of personal damage, injury or death associated with such unintended or unauthorized use. TEMIC TELEFUNKEN microelectronic GmbH, P.O.B. 3535, D-74025 Heilbronn, Germany Telephone: 49 (0)7131 67 2831, Fax number: 49 (0)7131 67 2423