U211B-XFPG3Y

U211B ATMEL | Alldatasheet

Document overview

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Technical content

Features

• Internal Frequency-to-voltage Converter  Externally Controlled Integrated Amplifier  Overload Limitation with “Fold Back” Characteristic  Optimized Soft-start Function  Tacho Monitoring for Shorted and Open Loop  Automatic Retriggering Switchable  Triggering Pulse Typically 155 mA  Voltage and Current Synchronization  Internal Supply-voltage Monitoring  Temperature Reference Source  Current Requirement ≤ 3 mA 1. Description The integrated circuit U211B is designed as a phase-control circuit in bipolar technol- ogy with an internal frequency-to-voltage converter. The device includes an internal control amplifier which means it can be used for speed-regulated motor applications. Amongst others, the device features integrated load limitation, tacho monitoring and soft-start functions, to realize sophisticated motor control systems. Figure 1-1. Block Diagram Control amplifier Load limitation speed/time controlled Voltage monitoring Supply voltage limitation Reference voltage Output pulse Pulse-blocking tacho monitoring Frequency- to-voltage converter ϕ = f (V12) Phase- control unit Soft start 11(10) 18* Voltage/current detector Automatic retriggering 17(16) 1(1) 4(4) -VS GND -VRef 6(5) 7(6) 3(3) 2(2) 16(15) 10(9) 14(13) 15(14) Controlled current sink Pin numbers in brackets refer to SO16 * Pins 5 and 18 connected internally Phase Control IC with Overload Limitation for Tacho

Applications

Rev. 4752B–INDCO–09/05

4752B–INDCO–09/05 U211B 2. Pin Configuration Figure 2-1. Pinning DIP18 109 VS Output Retr VRP CP F/V Isync GND VRef OVL Isense Csoft CTR/OPO OP+ PB/TM Vsync CRV OP- U211B Table 2-1. Pin Description Pin Symbol Function 1I sync Current synchronization

2 GND Ground

4 Output Trigger pulse output

5 Retr Retrigger programming

8 F/V Frequency-to-voltage converter

10 OP- OP inverting input

11 OP+ OP non-inverting input

12 CTR/OPO Control input/OP output

14 I sense Load-current sensing

15 OVL Overload adjust

17 V sync Voltage synchronization

18 PB/TM Pulse blocking/tacho monitoring

4752B–INDCO–09/05 U211B Figure 2-2. Pinning SO16 VS Output VRP CP F/V CRV Isync GND OVL I sense Csoft OP+ OP- Vsync VRef U211B CTR/OPO Table 2-2. Pin Description Pin Symbol Function 1I sync Current synchronization

7 F/V Frequency-to-voltage converter

9 OP- OP inverting input

10 OP+ OP non-inverting input

11 CTR/OPO Control input/OP output

13 I sense Load-current sensing

14 OVL Overload adjust

16 V sync Voltage synchronization

4752B–INDCO–09/05 U211B 3. Mains Supply The U211B is equipped with voltage limiting and can therefore be supplied directly from the mains. The supply voltage between pin 2 (+ pol/_|_) and pin 3 builds up across D1 and R1 and is smoothed by C1. The value of the series resistance can be approximated using: Further information regarding the design of the mains supply can be found in the section “Design Hints” on page 9. The reference voltage source on pin 16 of typically -8.9 V is derived from the supply voltage and is used for regulation. Operation using an externally stabilized DC voltage is not recommended. If the supply cannot be taken directly from the mains because the power dissipation in R 1 would be too large, the circuit as shown in Figure 3-1 should be used. Figure 3-1. Supply Voltage for High Current Requirements 4. Phase Control The phase angle of the trigger pulse is derived by comparing the ramp voltage (which is mains synchronized by the voltage detector) with the set value on the control input pin 12. The slope of the ramp is determined by C2 and its charging current. The charging current can be varied using R2 on pin 6. The maximum phase angle αmax can also be adjusted by using R2. When the potential on pin 7 reaches the nominal value predetermined at pin 12, a trigger pulse is generated whose width t p is determined by the value of C 2 (the value of C 2 and hence the pulse width can be evaluated by assuming 8 µs/nF) . At the same time, a latch is set, so that as long as the automatic retriggering has not been activated, no more pulses can be generated in that half cycle. The current sensor on pin 1 ensures that, for operations with inductive loads, no pulse will be generated in a new half cycle as long as a current from the previous half cycle is still flowing in the opposite direction to the supply voltage at that instant. This makes sure that “gaps” in the load current are prevented. The control signal on pin 12 can be in the range of 0 V to -7 V (reference point pin 2). If V12 = -7 V, the phase angle is at maximum ( αmax), i.e., the current flow angle, is at minimum. The phase angle is minimum (αmin) when V12 = V2. VM VS– 2 IS 123 4 5 24 V~

4752B–INDCO–09/05 U211B 5. Voltage Monitoring As the voltage is built up, uncontrolled output pulses are avoided by internal voltage surveil- lance. At the same time, all latches in the circui t (phase control, load limit regulation, soft start) are reset and the soft-start capacitor is short ci rcuited. Used with a switching hysteresis of 300 mV, this system guarantees defined start-up behavior each time the supply voltage is switched on or after short interruptions of the mains supply. 6. Soft Start As soon as the supply voltage builds up (t 1), the integrated soft start is initiated. Figure 6-1 shows the behavior of the voltage across the soft-start capacitor, which is identical with the volt- age on the phase-control input on pin 12. This behavior guarantees a gentle start-up for the motor and automatically ensures the optimum run-up time. Figure 6-1. Soft Start C 3 is first charged up to the starting voltage V 0 with a current of typically 45 µA (t 2). By reducing the charging current to approximately 4 µA, the slope of the charging function is also substan- tially reduced, so that the rotational speed of the motor only slowly increases. The charging current then increases as the voltage across C 3 increases, resulting in a progressively rising charging function which accelerates the motor mo re and more with increasing rotational speed. The charging function determines the acceleration up to the set point. The charging current can have a maximum value of 55 µA. VC3 t V12 ttot t1 = Build-up of supply voltage t2 = Charging of C3 to starting voltage t1 + t2 = Dead time t3 = Run-up time ttot = Total start-up time to required speed

4752B–INDCO–09/05 U211B 7. Frequency-to-voltage Converter The internal frequency-to-voltage converter (f/V converter) generates a DC signal on pin 10 which is proportional to the rotational speed, using an AC signal from a tacho generator or a light beam whose frequency is in turn dependent on the rotational speed. The high-impedance input pin 8 compares the tacho voltage to a switch-on threshold of typically -100 mV. The switch-off threshold is -50 mV. The hysteresis guarantees very reliable operation even when relatively sim- ple tacho generators are used. The tacho frequency is given by: where: n = Revolutions per minute p = Number of pulses per revolution The converter is based on the charge pumping principle. With each negative half-wave of the input signal, a quantity of charge determined by C 5 is internally amplified and then integrated by C6 at the converter output on pin 10. The conversion constant is determined by C 5, its charge transfer voltage of Vch, R6 (pin 10) and the internally adjusted charge transfer gain. k = Gi × C5 × R6 × Vch The analog output voltage is given by VO = k × f The values of C 5 and C6 must be such that for the highest possible input frequency, the maxi- mum output voltage V O does not exceed 6 V. While C 5 is charging up, the R i on pin 9 is approximately 6.7 k Ω. To obtain good linearity of the f/V converter, the time constant resulting from Ri and C5 should be considerably less (1/5) than the time span of the negative half-cycle for the highest possible input frequency. The amount of remaining ripple on the output voltage on pin 10 is dependent on C5, C6 and the internal charge amplification. The ripple ∆VO can be reduced by using larger values of C 6. However, the increasing speed will then also be reduced. The value of this capacitor should be chosen to fi t the particular control loop where it is going to be used. f n Gi I10 ∆VO Gi Vch× C5×

4752B–INDCO–09/05 U211B

7.1 Pulse Blocking

The output of pulses can be blocked by using pi n 18 (standby operatio n) and the system reset via the voltage monitor if V 18 ≥ -1.25 V. After cycling through the switching point hysteresis, the output is released when V18 ≤ -1.5 V, followed by a soft start such as after turn-on. Monitoring of the rotation can be carried out by connecting an RC network to pin 18. In the event of a short or open circuit, the triac triggering pul ses are cut off by the time delay which is deter- mined by R and C. The capacitor C is discharged via an internal resistance R i = 2 kΩ with each charge transfer process of the f/V converter. If there are no more charge transfer processes, C is charged up via R until the switch-off threshold is exceeded and the triac triggering pulses are cut off. For operation without trigger pulse blocking or monitoring of the rotation, pin 18 and pin 16 must be connected together. Figure 7-1. Operation Delay

7.2 Control Amplifier

The integrated control amplifier (see Figure 10-17 on page 21 ) with differential input compares the set value (pin 11) with the instantaneous value on pin 10, and generates a regulating voltage on the output pin 12 (together with the external circuitry on pin 12). This pin always tries to keep the actual voltage at the value of the set voltages. The amplifier has a transmittance of typically 1000 µA/V and a bipolar current source output on pin 12 which operates with typically ±110 µA. The amplification and frequency response are determined by R 7, C7, C8 and R 11 (can be left out). For open-loop operation, C 4, C5, R6, R7, C7, C8 and R11 can be omitted. Pin 10 should be connected with pin 12 and pin 8 with pin 2. T he phase angle of the triggering pulse can be adjusted by using the voltage on pin 11. An internal limitation circuit prevents the voltage on pin 12 from becoming more negative than V16 + 1 V.

7.3 Load Limitation

The load limitation, with standard circuitry, prov ides full protection against overloading of the motor. The function of load limiting takes account of the fact that motors operating at higher speeds can safely withstand larger power dissipations than at lower speeds due to the increased action of the cooling fan. Similarly, considerations have been made for short-term overloads for the motor which are, in practice, often required. These behaviors are not damaging and can be tolerated. C = 1 µF 10 V 18 17 16 15 123 4 R = 1 MΩ

4752B–INDCO–09/05 U211B In each positive half-cycle, the circuit measures, via R10, the load current on pin 14 as a potential drop across R 8 and produces a current proportional to the voltage on pin 14. This current is available on pin 15 and is integrated by C9. If, following high-current amplitudes or a large phase angle for current flow, the voltage on C 9 exceeds an internally set threshold of approximately 7.3 V (reference voltage pin 16), a latch is set and load limiting is turned on. A current source (sink) controlled by the control voltage on pin 15 now draws current from pin 12 and lowers the control voltage on pin 12 so that the phase angle α is increased to α max. The simultaneous reduction of the phase angle during which current flows causes firstly a reduc- tion of the rotational speed of the motor which can even drop to zero if the angular momentum of the motor is excessively large, and secondly a reduction of the potential on C 9 which in turn reduces the influence of the current sink on pin 12. The control voltage can then increase again and bring down the phase angle. This cycle of action sets up a “balanced condition” between the “current integral” on pin 15 and the control voltage on pin 12. Apart from the amplitude of the load current and the time during which current flows, the poten- tial on pin 12 and hence the rotational speed also affects the function of load limiting. A current proportional to the potential on pin 10 gives rise to a voltage drop across R 10, via pin 14, so that the current measured on pin 14 is smaller than the actual current through R8. This means that higher rotational speeds and higher current amplitudes lead to the same current integral. Therefore, at higher speeds, the power dissipation must be greater than that at lower speeds before the internal threshold voltage on pin 15 is exceeded. The effect of speed on the maximum power is determined by the resistor R 10 and can therefore be adjusted to suit each individual application. If, after load limiting has been turned on, the momentum of the load sinks below the “o-momen- tum” set using R10, V15 will be reduced. V 12 can then increase again so that the phase angle is reduced. A smaller phase angel corresponds to a larger momentum of the motor and hence the motor runs up, as long as this is allowed by the load momentum. For an already rotating machine, the effect of rotation on the measured “current integral” ensures that the power dissi- pation is able to increase with the rotational speed. The result is a current-controlled acceleration run-up which ends in a small peak of acceleration when the set point is reached. The load limiting latch is simultaneously reset. Then the speed of the motor is under control again and is capable of carrying its full load. The above mentioned peak of acceleration depends upon the ripple of actual speed voltage. A large amount of ripple also leads to a large peak of acceleration. The measuring resistor R 8 should have a value which ensures that the amplitude of the voltage across it does not exceed 600 mV.

4752B–INDCO–09/05 U211B

7.4 Design Hints

Practical trials are normally needed for the exact determination of the values of the relevant components for load limiting. To make this evaluation easier, the following table shows the effect of the circuitry on the important parameters for load limiting and summarizes the general tendencies. Table 7-1. Load Limiting Parameters Pmax - Maximum continuous power dissipationP1 = f(n) n ≠ 0 Pmin - Power dissipation with no rotation P 1 = f(n) n = 0 td - Operation delay time tr - Recovery time n.e. - No effect

7.5 Pulse-output Stage

The pulse-output stage is short-circuit protected and can typically deliver currents of 125 mA. For the design of smaller triggering currents, the function I GT = f(RGT) can be taken from Figure 10-12 on page 18.

7.6 Automatic Retriggering

The variable automatic retriggering prevents half cycles without current flow, even if the triac has been turned off earlier, e.g., due to a collector which is not exactly centered (brush lifter) or in the event of unsuccessful triggering. If necessary, another triggering pulse is generated after a time lapse which is determined by the repetition rate set by resistance between pin 5 and pin 3 (R 5-3). With the maximum repetition rate (pin 5 directly connected to pin 3), the next attempt to trigger comes after a pause of 4.5 t p and this is repeated until either the triac fires or the half cycle fin- ishes. If pin 5 is not connected, only one trigger pulse per half cycle is generated. Since the value of R5-3 determines the charging current of C2, any repetition rate set using R5-3 is only valid for a fixed value of C2. Parameters Component Component Component R10 Increasing R 9 Increasing C 9 Increasing Pmax Increases Decreases n.e. Pmin Increases Decreases n.e. Pmax/min Increases n.e. n.e. td n.e. Increases Increases tr n.e. Increases Increases

4752B–INDCO–09/05 U211B

7.7 General Hints and Explanation of Terms

To ensure safe and trouble-free operation, the following points should be taken into consider- ation when circuits are being constructed or in the design of printed circuit boards.  The connecting lines from C2 to pin 7 and pin 2 should be as short as possible. The connection to pin 2 should not carry any additional high current such as the load current. When selecting C2, a low temperature coefficient is desirable.  The common (earth) connections of the set-point generator, the tacho generator and the final interference suppression capacitor C4 of the f/V converter should not carry load current.  The tacho generator should be mounted without influence by strong stray fields from the motor.  The connections from R10 and C5 should be as short as possible. To achieve a high noise immunity, a maximum ramp voltage of 6 V should be used. The typical resistance Rϕ can be calculated from Iϕ as follows: T = Period duration for mains frequency (10 ms at 50 Hz) Cϕ = Ramp capacitor, maximum ramp voltage 6 V and constant voltage drop at Rϕ = 1.13 V A 10% lower value of Rϕ (under worst case conditions) is recommended. Figure 7-2. Explanation of Terms in Phase Relationship Rϕ kΩ() Tm s() 1.13 V()× 103× V VGT VL IL π/2 π 3/2π 2π tp tpp = 4.5 tp Mains Supply Trigger Pulse Load Voltage Load Current ϕ Φ

4752B–INDCO–09/05 U211B

7.8 Design Calculati ons for Main Supply

The following equations can be used for t he evaluation of the series resistor R 1 for worst case conditions: where: VM = Mains voltage VS = Supply voltage on pin 3 Itot = Total DC current requirement of the circuit = IS + Ip + Ix ISmax = Current requirement of the IC in mA Ip = Average current requirement of the triggering pulse Ix = Current requirement of other peripheral components R1 can be easily evaluated from the Figure 10-14 on page 19, Figure 10-15 on page 19 and Figure 10-16 on page 20. R1max 0.85 VMmin VSmax–

2 Itot

VM VSmin–

2 ISmax

P R1max() VMmax VSmin–() 2 2 R1

4752B–INDCO–09/05 U211B 8. Absolute Maximum Ratings Reference point pin 2, unless otherwise specified Stresses beyond those listed under “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress rating only and functional operation of the device at these or any other conditions beyond those indicated in the operational sections of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. Parameters Pins Symbol Value Unit Current requirement 3 -I S 30 mA t ≤ 10 µs 3 -i s 100 mA Synchronization current 1 I syncI 5m A

17 I syncV 5m A

t < 10 µs 1 ±i I 35 mA t < 10 µs 17 ±i I 35 mA f/V Converter Input current 8 I I 3m A t < 10 µs 8 ±i I 13 mA Load Limiting Limiting current, negative half wave 14 I I 5m A t < 10 µs 14 I I 35 mA Input voltage 14 ±V i 1V 15 -V I |V16| to 0 V Phase Control Input voltage 12 -V I 0 to 7 V Input current 12 ±I I 500 µA 6- I I 1m A Soft Start Input voltage 13 -V I |V16| to 0 V Pulse Output Reverse voltage 4 V R VS to 5 V Pulse Blocking Input voltage 18 -V I |V16| to 0 V Amplifier Input voltage 11 V I 0 to VS V Pin 9 open 10 -V I |V16| to 0 V Reference Voltage Source Output current 16 I o 7.5 mA Storage temperature range T stg -40 to +125 ° C Junction temperature T j 125 ° C Ambient temperature range T amb -10 to +100 ° C

4752B–INDCO–09/05 U211B 9. Thermal Resistance Parameters Symbol Value Unit Junction ambient DIP18 SO16 on p.c. SO16 on ceramic RthJA RthJA RthJA 120 180 100 K/W K/W K/W 10. Electrical Characteristics -VS = 13.0 V, Tamb = 25° C, reference point pin 2, unless otherwise specified Parameters Test Conditions Pins Symbol Min. Typ. Max. Unit Supply voltage for mains operation 3 -V S 13.0 V Limit V Supply voltage limitation -IS = 4 mA -IS = 30 mA 3- V S 14.6 14.7 16.6 16.8 V V DC current requirement -V S = 13.0 V 3 I S 1.2 2.5 3.0 mA Reference voltage source -IL = 10 µA -IL = 5 mA 16 -V Ref 8.6 8.3 8.9 9.2 9.1 V V Temperature coefficient 16 -TC VRef 0.5 mV/K Voltage Monitoring Turn-on threshold 3 -V SON 11.2 13.0 V Turn-off threshold 3 -V SOFF 9.9 10.9 V Phase-control Currents Synchronization current 1 ±IsyncI ±IsyncV 0.35 2.0 mA Voltage limitation ±I L = 5 mA 1, 17 ±V I 1.4 1.6 1.8 V Reference Ramp (see Figure 10-1 on page 15) Charge current I7 = f(R6) R6 = 50 kΩ to 1 MΩ 7I 7 12 0 µ A Rϕ-reference voltage α ≥ 180° 6, 3 V ϕRef 1.06 1.13 1.18 V Temperature coefficient 6 TC VϕRef 0.5 mV/K Pulse Output (see Figure 10-12 on page 18, Pin 4) Output pulse current R GT = 0, VGT = 1.2 V I o 100 155 190 mA Reverse current I or 0.01 3.0 µA Output pulse width C ϕ = 10 nF t p 80 µs Amplifier Common-mode signal range 10, 11 V 10, V11 V16 -1 V Input bias current 11 I IO 0.01 1 µA Input offset voltage 10, 11 V 10 10 mV Output current 12 -IO +IO 110 120 145 165 µA µA Short circuit forward, transmittance I12 = f(V10-11), (see Figure 10-7 on page 17) 12 Y f 1000 µA/V

4752B–INDCO–09/05 U211B Pulse Blocking, Tacho Monitoring Logic-on 18 -V TON 3.7 1.5 V Logic-off 18 -V TOFF 1.25 1.0 V Input current V18 = VTOFF = 1.25 V V18 = V16 18 I I 14.5 0.3 1 µA µA Output resistance 18 R O 1.5 6 10 k Ω Frequency-to-voltage Converter Input bias current 8 I IB 0.6 2 µA Input voltage limitation II = -1 mA II = +1 mA (see Figure 10-7 on page 17) -VI +VI 660 7.25 750 8.05 mV V Turn-on threshold 8 -V TON 100 150 mV Turn-off threshold 8 -V TOFF 20 50 mV Charge Amplifier Discharge current C5 = 1 nF, (see Figure 10-17 on page 21) 9I dis 0.5 mA Charge transfer voltage 9 to 16 V ch 6.50 6.70 6.90 V Charge transfer gain I 10/I9 9, 10 G i 7.5 8.3 9.0 Conversion factor C5 = 1 nF, R6 = 100 kΩ (see Figure 10-17 on page 21) K 5.5 mV/Hz Output operating range 10 to 16 V O 0-6 V Linearity ±1 % Soft Start, f/V Converter Non-active (see Figure 10-2 on page 15 and Figure 10-4 on page 16) Starting current V 13 = V16, V8 = V2 13 I O 20 45 55 µA Final current V 13 = 0.5 13 I O 50 85 130 µA f/V Converter Active (see Figure 10-3 on page 15, Figure 10-5 on page 16 and Figure 10-6 on page 16) Starting current V 13 = V16 13 I O 247 µ A Final current V 13 = 0.5 I O 30 55 80 µA Discharge current Restart pulse 13 I O 0.5 3 10 mA Automatic Retriggering (see Figure 10-13 on page 19, Pin 5) Repetition rate R 5-3 = 0 t pp 34 . 56 t p R5-3 = 15 kΩ tpp 20 t p Load Limiting (see Figure 10-9 on page 17, Figure 10-10 on page 18 and Figure 10-11 on page 18) Operating voltage range 14 V I -1.0 +1.0 V Offset current V10 = V16 V14 = V2 via 1 kΩ 15-16 IO IO 0.1 1.0 µA µA Input current V 10 = 4.5 V 14 I I 60 90 120 µA Output current V 14 = 300 mV 15-16 I O 110 140 µA Overload ON 15-16 V TON 7.05 7.4 7.7 V 10. Electrical Characteristics (Continued) -VS = 13.0 V, Tamb = 25° C, reference point pin 2, unless otherwise specified Parameters Test Conditions Pins Symbol Min. Typ. Max. Unit

4752B–INDCO–09/05 U211B Figure 10-16. Power Dissipation of R1 According to Current Consumption 03 6 91 2 P (R1) (W Itot (mA) Mains Supply 230 V

4752B–INDCO–09/05 U211B Figure 10-17. Speed Control, Automatic Retriggering, Load Limiting, Soft Start 220 kΩ 470 k Ω -V S 3.3 nF 1 MΩ GND 22 µF/ 25 V C 11 2.2 µF R 12 180Ω M R 1 18 kΩ 1N4007 D 1 2 W TIC 226 33 mΩ 1 W R11 2 MΩ 100 kΩ R6C6 100 nF 10 µF/16V C7 C8 220 nF 22 kΩ R7 C 3 2.2 µF/ 16 V C 5 1 nF R 5 1 kΩ Speed sensor 220 nF L N 1 kΩ R10 1 MΩ 4.7 µF/16V R19 100 kΩ C10 2.2 µF/16V R31 100 kΩ R14 56 kΩ R13 47 kΩ VM =

230 V ~

ϕ = f (V12) Soft start 12 13 9 8 Voltage/current detector Automatic retriggering 17 1 - C2 Set speed voltage Actual speed voltage Controlled current sink -VRef

4752B–INDCO–09/05 U211B Figure 10-18. Speed Control, Automatic Retriggering, Load Switch-off, Soft Start The switch-off level at maximum load shows in principle the same speed dependency as the original version (see Figure 10-17 on page 21), but when reaching the maximum load, the motor is switched off completely. This function is effected by the thyristor (formed by T 1 and T2) which ignites when the voltage at pin 15 reaches typica lly 7.4 V (reference point pin 16). The circuit is thereby switched to standby mode over the release Pin 18. 11 8 10 9 R M R 18 kΩ 220 kΩ 470 kΩ R 1.5 W 1N4004 180Ω R 22µF 25 V C R 8= 3 x 11 m Ω R 2.2 kΩ 230 V~ 680 pF C R 1 M Ω C 2.2 nF 1 kΩ R 220 nF C Speed sensor R 15 kΩ C R 47 kΩ 1 M Ω R C 100 nF R 100 kΩ 220 nF C 2.2µF 10 V C 2.2 µF 10 V C 250 kΩ R 4.7µF 10 V C 470 kΩ R

9 GND

S 1 W R 47 kΩ R 47 kΩ 10 kΩ R BZX55 Set speed voltage L N 2.2 /10 V Rϕ C /tϕ µF C 2.2µ F U211B

4752B–INDCO–09/05 U211B Figure 10-19. Speed Control, Automatic Retriggering, Load Switch-down, Soft Start The maximum load regulation shows in principle the same speed dependency as the original version (see Figure 10-17 on page 21 ). When reaching the maximum load, the control unit is turned to αmax, adjustable with R 2. Then, only IO flows. This function is effected by the thyristor, formed by T1 and T2 which ignites as soon as the voltage at pin 15 reaches approximately 6.8 V (reference point pin 16). The potential at pin 15 is lifted and kept by R 14 over the internal operat- ing threshold whereby the maximum load regulation starts and adjusts the control unit constantly to α max (IO), inspite of a reduced load current. The motor shows that the circuit is still in operation by produceing a buzzing sound. 11 8 10 9 R M R 18 kΩ D 220 kΩ 470 kΩ R 1.5 W 1N4004 180Ω R 22 µF 25 V C R 8= 3 x 11 m Ω R 2.2 kΩ 230 V~ 680 pF C R 1 M Ω C 2.2 nF 1 kΩ R 220 nF C Speed sensor R 15 kΩ 2.2 µF/ 10 V C R 47 kΩ 1 M Ω R C 100 nF R 100 kΩ 220 nF C 2.2µ F 10 V C 2.2µF 10 V C 250 kΩR 4.7µF 10 V 470 kΩ GND S 1 WR 47 kΩ R 33 kΩ 10 kΩ R BZX55 Set speed voltage L R C /tϕ ϕ N C C 2.2 µF U211B

4752B–INDCO–09/05 U211B Figure 10-20. Speed Control, Automatic Retriggering, Load Limiting, Soft Start, Tacho Control 11 8 10 9 R M R 18 kΩ D 220 kW C 470 kW R 1.5 W 1N4004 220Ω R 22 µF 25 V C R = 3 x 11 m Ω R 1 kΩ 230 V~ 1 nF C R 1 M Ω C 2.2 nF 1 kΩ R 220 nF C Speed sensor R 22 kΩ C R 47 kΩ 1.5 M Ω R C 100 nF R 68 kΩ 220 nF C 2.2 µF 10 V C 2.2 µF 10 V C 250 kΩR 4.7µF C 1 M Ω R GND S 1 W Set speed voltage L N 1 / mF 10 V 1 M W 2.2 /µF 10 V R C ϕ ϕ 22 nF U211B

4752B–INDCO–09/05 U211B Figure 10-21. Speed Control with Reflective Opto Coupler CNY70 as Emitter 11 8 10 9 22 nF R M R 18 kΩ D 220 kΩ C 470 kΩ R 1.5 W 1N4004 100W R 47 25 V C 230 V~ 680 pF C R 1 M Ω C 3.3 nF C R 470 kΩ 220 nF C 2.2 10 V C 4.7 10 V C 13 100 kΩ R GND S 10 V R C R C 16 kΩ 470 nF Set speed m in. R Set speed m ax. R 47 kΩ R 4.7 kΩR R 220 kΩ R 1.5 kΩ 100 10 V C C 470 nF CNY 70 R R 100 Ω 470Ω Z BZX55 C9V1 3.5 kΩ / 8 W R 1N4004 D IGT = 50 m A L L R 100Ω 150 nF 250 V~ C ca. 220 Pulses/Revolution all diodes BYW ϕ ϕ µF µF µ F µF µF U211B

4752B–INDCO–09/05 U211B Figure 10-22. Speed Control, Maximum Load Control with Reflective Opto Coupler CNY70 as Emitter 11 8 10 9 22 nF R M R 10 kΩ D 110 kΩ C 220 kΩ R 1.1 W 1N4004 100 Ω R 22 25 V C 230 V~ C R 1 M Ω C 3.3 nF C R 820 kΩ 470 nF C 2.2 10 V C 47 10 V C 10 220 kΩR GND S R C R C 16 kΩ 470 nF Set speed m in. R Set speed m ax. R 82 kΩ R 6 R 2.2 kΩ CNY 70 R R 33 kΩ 470Ω IGT = 50 m A 100Ω 150 nF 250 V~ C 680 pF R 10 kΩ C 1 nF 9 V 4.7 10 V C R 220 kΩ R 8= 3 x 0.1 Ω R 1.1 kΩ C ϕ ϕ µF µFµF µF µF µF U211B

4752B–INDCO–09/05 U211B The schematic diagram (see Figure 10-22 on page 26) is designed as a speed control IC based on the reflection-coupled principle with 4 per iods per revolution and a maximum speed of 30000 rpm. The separation of the coupler from the rotating aperture should be about approxi- mately 1 mm. In the schematic diagram, the power supply for the coupler was provided externally because of the relatively high current consumption. Instructions for adjusting: 1. In the initial adjustment of the phase-control circuit, R 2 should be adjusted so that when R14 = 0 and R31 are in minimum position, the motor just turns. 2. The speed can now be adjusted as desired by means of R 31 between the limits deter- mined by R13 and R14. 3. The switch-off power of the limiting-load control can be set by R 9. The lower R9, the higher the switch-off power.

4752B–INDCO–09/05 U211B 12. Package Information 11. Ordering Information Extended Type Number Package Remarks U211B-xY DIP18 Tube U211B-xFPY SO16 Tube U211B-xFPG3Y SO16 Taped and reeled Dimensions in mm 0.5 min technical drawings according to DIN specifications 7.77 7.4723.3 max 4.8 max 3.3 6.4 max 0.36 max 9.8 8.2 1.64 1.44 0.58 0.48 2.54 20.32 18 10 technical drawings according to DIN specifications Dimensions in mm 10.0 9.85 8.89 0.4 1.27 1.4 0.25 0.10 5.2 4.8 3.7 3.8 6.15 5.85 0.2 16 9

4752B–INDCO–09/05 U211B 13. Revision History Please note that the following page numbers referred to in this section refer to the specific revision mentioned, not to this document. Revision No. History 4752B-INDCO-08/05

• Put datasheet in a new template
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