MC1563

MC1563 MOTOROLA | Alldatasheet

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MC1463, MC1563 MAXIMUM RATINGS (Tc = +25°C unless otherwise noted.) Tq = 25°C Po | oss 24 | watts Derate above Ta = 259C wRosa| Sad 16 | mvc ‘Thermal Resistance, Junction to Air Rosia 184 62 CI Te = 25°C Po 18 90 | wats Derate above Tc = 25°C Rese | 14.8 61 | mie Operating and Storage Junction Temperature |Tj, Tstg | -€5t0 “160 °C ee OPERATING TEMPERATURE RANGE Operating Ambient Temperature Range Ta bo ELECTRICAL CHARACTERISTICS 1, = 100 made, Tc ~ #28°C, Vin = 15 V, Vg = 10 V unless otherwise noted) tance [en now [me ine Teas fe Ta] uw | TTA Tow to Thgn 2 1p =10may Gutout Vohge Range, = TO mal Ve [36 1-9 3a ee Minimum Input-Output Voltage Differential Nin Voll — Tos | 27 1s 30 Vde TempwatreCoetiian of Outut Vaioe 3 avolat | owe | re) J (Ree = 0.3 ohm) R Package to) = | s00 10] — | s00 (Ty = Constant (1.0 mA <1, <20 mal) | | oa | 16 or | 24] mv Te = #25°C (1.0 mA <1, <50 mA) R Package - | 0.005 | 0.05 0.005 | 005) Dion = 0°C ter merase @tyign = 70°C tor morass eat sink raquced for Tigh tenting of "G package = 88°C for MC1563 © +125°C for MC1563 MOTOROLA LINEAR/INTERFACE DEVICES 4-78

GENERAL DESIGN INFORMATION 1. Output Voltage. Vo FIGURE 9 - TYPICAL CIRCUIT CONNECTION 2) Output Voltages wt by resistors Ry and Rg (see Figure 8) Set Mg BB ohms and determine Fa hom the graph of Figuee11 or from the equation oo Ra ® (2|Vo|-7)ka = {1 Output voltage can be varied by making Ria adustable as its b shown in Figures 93nd 10, 1 ° ni €) Outout voltage, Vo,isdetermined by the ratio of Ra and Rig ‘ therefore optimum temperature performance can be achieved 4 « If Ra and Rg have the same temperature cotticient oJ wee | n Miche 4) Vo = Veet (1 + RA); therefore the tolerance on e Re 0008 uF ° cutput voltage is determined by the tolerance of Viet andy, g d_te re Ra and Rg D edi] ct Rito Ge Dear vg RA UD Vp -Daes YOO“3SINY get 2. Short-Cireuit Current, Isc Seer Bat Go Doe Vo 2 v0 . Shore-Cieuit Current isc is determined By Aye. Rye mov be choten with the aid of Figure 11 when using the type! Ereut connection of Figure 8. See Figure. 27 for current finvting during NPN current boost 3. Compensation, Co "A 0001 LF ‘capacitor (Ce, see Figure 9). will provide FIGURE 10 ~ Ra versus Vo txiequate cormpentation in moat sppliations, with or without 0 Curtent boost. Smaller value of Ce wil reduce stability and impedance versus frequency. The physical location of Ce Py (ay = 63 4 should be close to the MC1S63/MC1463 with short lead | 7 lengths a y ‘RO uF capacitor, Cy, trom Pin wo ground wit typically 3 reduce the output noise voltage to 120 uVirms). The value —™ of Cy can be increased or decreased, depending an the noise 2 LY ‘oltage requirements of aperticular appheaton. A minimum ng | value of 0.001 uF 1s recommended! 2 a aa 8. Oviput Capacitor, Co 0 4 The value of Co should be at least 10 uF in order to provide LVL i] jo stab 000 stabity a, 6. Shutdown Contrat a a (ne method of turning “OFF” the regulator is to draw 1 mA | from Pin 2 (See Figure 8). This contro! can be used to ‘Vo. OUTPUT VOLTAGE (VOLTS) Aliminate power consumption by circuit leds which can be put in "standby" mode. Examples include, an ac OF de rqueich” contol for communications cireut, end a ith pation contro! to protect the regulator under sustained out FIGURE 11 ~ tye verte Rye Butshorteireuiting As the magnitude of the aput threshold «en Voltage at Pin 2 depen directly upon the junctwon temper, Mureo! the integratederreitchip,afixeade voltage at Pin? Tyetasee wall cause automatic shutdown for high junetion tempers Eg tures see Figure 25). This will protect the chip, incepend = 1 nt of the heat sinking used, the ambient temperature, or the input or outout vortage levels Stancard foc tevelsof 8 MECL, MATL, MOTL or MTTL can als0 be used to 3 — {urn the regulator "ON" or “OFF” (see Figures 30 and 31) 2 Rw | 1. Remote Sensing 5 ae “Fae connection t0 Pin 8 can be made with 9 separate ind \\ direct 10 the load. Thus, “remote sensing” can be achieved 3 trod the effect of undesired impedances Tnclading ma ot gg N the miliammeter used to measure ly) on Zq.can begremtly — reduced {sce Figure 39) 3 Fo a MECL, MOTL, MATL, and MTTL are Trademarks of Motorota Ine ° 19 EJ 30 0 Ey fa EXTERNAL CURRENT LIMITING AESISTOR (OHS) MOTOROLA LINEAR/INTERFACE DEVICES 4-80

MC1463, MC1563 TYPICAL CHARACTERISTICS Cp=O.1HF, Ce = 0.001 uF, Co = 10uF, Te = +269C, Unless otherwise noted q Vi(nom) = -15 Vde, Vo{nom) = -10 Vde, 1, = 100 mAde FIGURE 12 ~ TEMPERATURE DEPENDENCE FIGURE 13 ~ FREQUENCY DEPENDENCE OF SHORT-CIACUIT LOAD CURRENT OF OUTPUT IMPEDANCE ‘al Coo CO 3g mol} — oro jb app tet BaD al = cool ae rt td 4 | ESS Eato~ 2 a aa CI 5 A 8 sal, <a 3 ano PH AE i 3 woofs _ on 2 co ni 7 Lb eR ES oe EY) S — pat =), oss os bess 2°) SESS eS (Se fo a 3 gH ee a a ee 2 abet Bie ; io — oa ere a eC ie "T 7 vot

1 JUNCTION TEMPERATURE OD eneauency mot

FIGURE 14 ~ DEPENDENCE OF OUTPUT MPEDANCE ON OUTPUT VOLTAGE FIGURE 15 — OUTPUT IMPEDANCE versus Rye ° % — foes ee ee | a (My Vols 3.0¥, Ty = #28°C = = 50m ~ tH Par Meaty = 1D mats S00 mA 3” Vane FA ida oi | Bo _|— 50 | sf fT poe 5 eT Tt se ~~ LL | 5 10 7% 3 a0 D En a 3 7 7s vy OUTPUT VOLTAGE WOLTS fu CURRENT LIMITING RESISTOR OHS) FIGURE 16 ~ CURRENT LIMITING CHARACTERISTICS Fa a eo S ose Fie eee ee Zon asp TT An ee _ a a eC nC

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MOTOROLA LINEAR/INTERFACE DEVICES 4-81

MC1463, MC1563 TYPICAL CHARACTERISTICS (continued) FIGURE 17 — BIAS CURRENT versus INPUT VOLTAGE ON INPUT-OUTPUT VOLTAGE DIFFERENTIAL . [fo je-tue_f be "CTT TTTT TTT, , GS eee COE i Creer Be BpA4e 4 5 a a ea eZee a ee eee see Pe a ee = : Pee coo: Beer Pe A wT TT ETT? tT YCLELLLLL) eo 3 | ie] Eg} fj pee ft A ce A = a i se Fo SO OO 2 PNY) aw Lt ees A A Petre SET) bs | A Lory — ors Se o iT 0 6 Ey B x» Ey 40 bal oes a | (Ee 32 nf -—-f—| fren -eX| — Ee EE 32 | I a eee 5 | bad eT TZ hn —— Pie OR | a i a a a | ae ee Pd = ee = anal — | | 7-1 oe FEE Ee ‘ae wb EE a 8 sana on 01 al Cor TH i 30 40 58 70 0 nw w 40 50 WOysi01v Vamwoiv Vj Vq.. INPUT-OUTPUT VOLTAGE OIF FERENTIAL (VOLTS) MOTOROLA LINEAR/INTERFACE DEVICES 4-82

MC1463, MC1563 OPERATION AND APPLICATIONS This section describes the operation and design of the MC1S63 (MC1463) negative voltage regulator and also Provides information on useful applications. SUBJECT SEQUENCE INDEX Specification Pg. No ‘Specification Pg. No. Theory of Operation 7 Remote Sensing 12 NPN Current Boosting 9 An Adjustable Zero-Temperature-Coetfivient 13 PNP Current Boosting 10 Voltage Source Positive and Negative Power Supphes iW Therma! Shutdown 13 Shutdown Techniques in ‘Thermal Considerations 13 Voltage Boosting 12 PC Board Layout and Information 15 ‘THEORY OF OPERATION is exactly the same approach used in the first option. That The usual series voltage regulator shown in Figure 23, is, the output is being resistively divided to match the consists of a reference voltage, an error amplifier, and a reference voltage. There is however, one big difference in series control element. ‘The error amplifier compares the that the output of this “regulator” is driving the input of output voltage with the reference voltage and adjusts the another regulator (the error amplifier). The output of the output accordingly until the error is essentially zero. For reference amplifier has a relatively low impedance as com- applications requiring output voltages larger than the refer- Pared to the input impedance of the error amplifier. ence, there are two options. The first is to use a resistive Changes in the load of the output of the error amplifier divider across the output and compare only a fraction of are buffered to the extent that they have virtually no effect the output voltage to the reference. This approach suffers ‘on the reference amplifier. If the feedback resistors are from reduced feedback to the error amplifier due to the external (as they are on the MC1563) a wide range of attenuation of the resistive divider. This degrades load reference voltages can be established. regulation especially at high voltage levels. The error amplifier can now be operated at unity gain The alternative is to eliminate the resistive divider and to provide excellent regulation. In fact, this “regulator- to shift the reference voltage instead. To accomplish this, within-a-regulator” concept permits the load regulation to another amplifier is employed to amplify (or level shift) be specified in terms of output impedance rather than as the reference voltage using an operational amplifier as some percentage change of the output voltage. This ap- shown in Figure 24. The gain-determining resistors may Proach was used in the design of the MC1S63 negative be external, enabling a wide # age of output voltages. This voltage regulator. FIGURE 23 — SERIES VOLTAGE REGULATOR FIGURE 24 — THE “REGULATOR-WITHIN-A-REGULATOR” APPROACH vy Seren — vol fy 5 vo Amplifier Fribheileal Fe Yo= Veet te 24) ao Fe oss MOTOROLA LINEAR/INTERFACE DEVICES 4-83

MC1463, MC1563 FIGURE 25 (Recommended External Circuitry is Depicted With Dotted Lines.) 2 (MC1563/MC1463 Block Diagram ce suartUp Veet - ps wna pes ° ey 2 shotDown ret i 8 Teor 7 YO vi i :° eB eay Ra } H + Controt ies Fey OC Lovet Shite Unity Gain Regulator 4 | Simi Circuit Schematic cnw/9

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38 vae + ie : Rpfoi! : : ‘nr bn, rar | i 2 ii 60k Votrett, 7 Co 4, t . » OM OTTO) oO} oobi! a ai “i Complete Circuit Schematic a Ree 5 6 Yo ‘Shut Down Contot DC Shift Outout cosa mown S OG Shitt Sense ry G4 SY Noten Fiter Groune (Fy T a - 2 zk gtk 510 1.5 100: | - | Ourout oN a, | Senta Pot °7 IY [J ram area | fo 2 sores | ‘3 “2 vr Curvent cima bo MC1563 (MC1463) Operation - 46 3 (C1463) New input voltage. It makes use of two zener diodes having Figure 25 shows the MC1563 (MC1463 ) Negative Reg- the same breakdown voltage. A first or auxiliary zener is ulator block diagram, simplified schematic, and complete driven directly from the input voltage line through a schematic. The four basic sections of the regulator are: resistor (60 k&2) and permits the regulator to initially Control, Bias, DC Level Shift, and Output (unity gain) achieve the desired bias conditions. This permits the Regulator, Each section is detailed in the following para sevond, or reference zener to be driven from a current graphs. source. When the reference zener enters breakdown, the Control auxiliary Zener is isolated from the rest of the regulator The control section involves two basic functions, start circuitry by a diode disconnect technique This is necessary up and shutdown. A startup function is required since to keep the added noise and ripple of the auxiliary zener the biasing is essentially independent of the unregulated from degrading the performance of the regulator. MOTOROLA LINEAR/INTERFACE DEVICES 4-84

MC1463, MC1563 ‘The shutdown control, in effect, consists of a PNP tran- inverting input to this amplifier is the Output Sense con- sistor across the reference zener diode. When this transistor nection (Pin 8) of the regulator. A Darlington connected is turned “ON”, via Pin 2, the reference voltage is reduced to NPN power transistor is used to handle the load current. ‘essentially zero volts and the regulator is forced to shut- The short-circuit current limiting resistor, Rsc, is con down. During shutdown the current drain of the com- nected in the emitter of this transistor to sample the full plete IC regulator drops to Vin/60 k& or 500 HA for a load current. This connection enables a four-diode string -30 V input to limit the drive current to the power transistors in a . conventional manner. Bias Stability and Compensation A zener diode i the main eference element and forms 'As has been seen, the MC1563 employs two amplifiers, the heart of the bias citeuitry lis positive temperature each using negative feedback. This implies the possibility coctfeae is balanced by a negative temperature oe of frequency instability due to excessive phase shift at high 4 efficients of forward biased diodes in & ratio determine frequencies. Since the error amplifier is normally used at by the resistors in the diode sting: Tye result is a refer unity gain (the worst ease for stability) a high impedance ence voltage of approximately “3.5 Vde with 2 typical node is brought out for compensation. For normal oper- temperature coefficient of 0.002%/9C. In addition, this ition a eapacitor is connected between this poiat (Pin 7) circuit also provides a reference current which is used to and PinS. The recommended value of 0.001 uF will insure bias all current sources in the remaining regulator circuitry Stability and stl provide acceptable transient response DC Level Shift (see Figure 21). It is also necessary to use an output ca- pacitor. Co. (typically 10 uF) directly from the output (Pin 4 am reference voltae isused as the inpot 13 ann 6) to ground. When an external transistor is used to boost ifferential amplifier he gain of this amplifier is quite the current, Co = 100 wF is recommended (see Figure 26). hhigh and it therefore may be considered to function as @ conventional operational amplifier. Consequently, negative NPN CURRENT BOOSTING feedback can be employed using two external resistors (RA For applications requiring more than $00 mA of load and Rp) to set the closed-loop gain and to boost the refer current. or for minimizing voltage variations due to tem ence voltage to the desired output voltage, A capacitor. perature changes in the IC regulator arising from changes Cas is introduced externally into the level shift network ‘of the internal power dissipation, the NPN current-boost (via Pin 3) to stabilize the amplifier and to filter the zener circuits of Figure 2 or 26. are recommended. The circuit noise. The recommended value for this capacitor is 0.1 BF shown in Figure 26 can supply up to approximately 4.0 and should have a voltage rating in excess of the desired amperes (subject to safe area limitations). At higher cur- output voltage. Smaller capacitors (0.001 uF minimum) rents the VBE of the pass transistor may itself exceed the may be used but will cause @ slight increase in output threshold of the current limit even for Rsc = 0. Figure 2 noise. Larger values of Cy will reduce the noise as well as illustrates the use of an additional external diode from Pin delay the start-up of the regulator 4 for higher current operation or for pass transistors ex: hibiting higher VBe"s. It will probably be necessary to Output Regulator determine Ree experimentally for each case where a pass The output of the shift amplifier is fed internally to the transistor is used because VBE varies from device to device, noninverting input of the output error amplifier. The ‘The eireit of Figure 26 when set up for a -10 V output FIGURE 26 — TYPICAL NPN CURRENT BOOST CONNECTION FIGURE 27 — Isc versus Rgc (REFERENCE FIGURE 26) a 3 89 44q- Try 3 | i GNO pall TT iy Tt }.4-t- a rr) oo peg bd aeeen rol || Fossil. fo | bop eb bz ba } t i i | i I = ° ! Eso Veo fob yy bob and i é i 1 mersean fo cols F™ & T jill t S| Mereesn | 8 100 Z Pop pep to bor poba ime re" 8 ys}— + -~ i toa 4d ot 3 Pi tS = 10/4 ~ f : rd an ‘ ra Fa vi 2 0 i ones ° oO? 04 06 08 1012 14 16 18 20 es jg: Current Limiting Resistor (Ohm) MOTOROLA LINEAR/INTERFACE DEVICES 4-85

MC1463, MC1563 GN L nue $3 cased oar ‘. b Co 4 [3 33k 100 uF 7 | mcrsesr [© 0.001 o-] mcra6an o FIGURE 28 — PNP CURRENT or 10K BOOST CONNECTION vin eS ° “BO WEs Fsct an706 or bau a & peas Srequy vi2 vo ¥5.2] ~6.B Vde ‘Oo2nsW vac (Ra = 13 kQ) supply and operating with a - 15 V input, 28 this represents a savings of 22 watts when compared with a Ree of 0.1 92, will yield a change in output voltage with operating the regulator from the single -9 V supply. of only 26 mV over a load current range of from 1 mA It can supply current to 10 amperes while requiring an to 3.5 A. This corresponds to a de output impedance input voltage to the collector of the pass transistor of -6.8 of only 7.5 milliohms or a percentage load regulation of volts minimum. The pass transistor is limited to 10 amperes 0.26% for a full 3.S-ampere load current change. Figure 27 by the added short-circuit current network in its emitter indicates how the short circuit current varies with the value (Rse2) and the IC regulator is limited to 500 mA in the of Rse for this circuit conventional manner (Rgc|). The MJ450 exhibits a min- imum hpE of 20 at 10 amperes, thus requiring only 500 PNP CURRENT BOOSTING mA from the MC1S63R. Regulation of this circuit is com- A PNP power transistor can also be used to boost the parable to that of the NPN boost configuration Joad current capabilities. To improve the efficiency of the For higher output voltages the additional unregulated PNP boost configuration, particularly for small output power supply is not required. The collector of the PNP voltages, the circuit of Figure 28. is recommended. An boost transistor can tie directly to Pin $ and the internal auxiliary -9 volt supply is used to power the IC regulator current limit circuit will provide short-circuit protection and the heavy load current is obtained froma second supply using Rsc (see Figure 11). Transistor Q2 and Rc will ‘of lower voltage. For the 10-ampere regulator of Figure not be required and Pin 2 should be returned to ground. ig "400 mA mand

1 Re“ 18 Vo ~ 15 Vee

1. vae — = > area (} chy merassn LN tour Vor tv A) 5 or Equiv 3k F 4 8 Positive Regulator 008 uF 12 > i é ° $ 4 *vo-|-vol = oan ? Cas 1 Rake +7 = one ao ~~ 7 mzasas = = oreo, = Re- 68k 39 92 dcae nares : | “se i ° mcis6aR 45 MC1a63R . Ce 0.001 uF 7 ba 10 uF ° Negetive Reguiator ° i" = D Vo = -15 vee peer Gon 400 matmax) FIGURE 29 — A +15 Vde COMPLEMENTARY TRACKING REGULATOR WITH AUXILIARY +5.0 V SUPPLY SSSSSSSSSSsSSSSSSSSSsSSSSSSSSSSSSSSSSS MOTOROLA LINEAR/INTERFACE DEVICES 4-86

MC1463, MC1563 Gno = on we Ag~ 68% 26 39 6 | ‘ Ran tk Vy = =10 vse @—— “51 rciseac Wz = -4 Vide ncra6ac ° Iz = mA (max) of 06 sot vz =-asaePA) Fe FIGURE 34 — AN ADJUSTABLE “ZERO-TC” VOLTAGE SOURCE AN ADJUSTABLE ZERO-TEMPERATURE- 103V/°C). By setting -0.61 Vde externally, at Pin 2, the COEFFICIENT (0-TC) VOLTAGE REFERENCE regulator will shutdown when the chip temperature reaches SOURCE approximately 140°C. Figure 35 shows circuit that uses The MC1563, when used in conjunction with tow-TC a zero-TC zener diode and a resistive divider to obtain resistors, makes an excellent reference-voltage generator this voltage If the -3.5 volt reference voltage of the IC regulator is a In the case where an external pass transistor is employed: satisfactory value, then Pins I and 9 can be tied together its temperature, rather than that of the IC regulator, re- and no resistors are needed. This will provide a voltage quires control. A technique similar to the one just dis- reference having a typical temperature coefficient of cussed can be used by directly monitoring the ease tem- 0.002%/°C. By adding two resistors. Ra and Rp. any perature of the pass transistor as is indicated in Figure 36 voltage hetwoen -3.5 Vde and ~37 Vde can be obtained ‘The case of the normally “OFF” thermal monitoring with the same low TC (see Figure 34) transistor, Q2, should be in thermal contact with, but electrically isolated from, the case of the boost tran- THERMAL SHUTDOWN sistor, QL By setting a fixed voltage at Pin 2. the MC1S63 chip can be protected against excessive junction temperatures THERMAL CONSIDERATIONS caused by power dissipation in the IC regulator. This is Monolithic voltage regulators are subjected to internal based om the negative temperature coefficient of the heating similar to a power transistor. Since the degree of base-emitter junction of the shutdown transistor (-1.9 x internal heating is a function of the specific application, — Gno ~ 270 rue -061 vae oak

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° morse 56k ° mciasa | ° ‘ oma | 0.001 uF ° Fee ® e FIGURE 35 — JUNCTION TEMPERATURE LIMITING SHUTDOWN CIRCUIT eee MOTOROLA LINEAR/INTERFACE DEVICES 4-89

MC1463, MC1563 assume Rgcs = 0.2°C/W and Rgga=2°C/W 3. OVQ due to gradient coefficient, AVO/AG [8 Vol = (AV0/4GXVOXAPp) 11 is desired to find the 4 Vo which results from this 41 Each of the three previously stated effects on Vo can now la Vol = (+3 x 10-4/W\\(5 volts)(5 x 107!) be separately considered Iavol=+08 mv 1. AVo due to a Ty Therefore the total A Vo is given by 4 oR Vo = (Vo) (Pp )(AVo/AT) (RasctRacstResa) 4 Vo=(5 VXSVx0.1 AX+0.002%/°C)(19.2°C/W) on 2VO toull=£1.0-20408 mv AVo* t 1.0mW -2.2mV <|Vo total] <-0.2 mv 2. AVQ due oz Other operating conditions may be substituted and com- laVol=(zoXlL) puted in a similar manner to evaluate the relative effects a vor™ 70K IL) of the parameters. laVol=-(2x 10-2107!) =-2 mv To SSSSsSSSSSSSSSSSSSSSSSSSSSSSSSSSSee TYPICAL PRINTED CIRCUIT BOARD LAYOUT 7 + —+ Te ° —~ f ii) im ie ° a SSSSSSSSSSsSSSSSsSssshFsese MOTOROLA LINEAR/INTERFACE DEVICES 491

MC1463, MC1563 FIGURE 37 — LOCATION OF COMPONENTS Co bs Hs Be ote 1 wets es hen Fag it sed it nec to remove he compe ve . + a [Note 2: GNo. a t i t im resistors to be paralleled to obtain the desired Cy @ii i value of Rige Bt eat i 5 [Note 3: a — aoe tal, \\y If Pin 2 is used to shut down the regulator, remove the Rie . Re i: jrPmer whihherts in 2 groune co 2 peek Now 4 a. wee i . |rRemote sensing can be achieved by removing the copper Bier * A to the “minus” load terminal. The circuit board ground 4 ce ar Rod Iground at the “plus” load terminal. La TYPICAL CIRCUIT CONNECTION FOR OUTPUT VOLTAGES BETWEEN ~3.5 AND ~37 VOLTS = ° oo 6 Ae Pathe, Se, ar 10 uF ae ©. 0001 nF > mcre6an Vos-3.8(1+ 8th ° 3° Re Wer s| [ee vi ° © Yo Select Ria + Agg; 10 Give Desired Vo: Rat Rag) (21 Vo |-7) kit with Rg =68 Ki PARTS LIST ma SOE bo amare caon Fae Select IAC Mode! X-203, allory Model MTC: or ecuivlent Rc select tava carbon Ri Select For minimum current of 1 made Co | TOF Sprague 1500 Series, Dickson 0 10C series or ecuivatert Gm out Ceramic Dist” Centrale ODAIO4, or equivalent ce 0.001 uF Sprague TO-P10, or equivalent . iimoer a MCTS63R or MC146R "HS Heatsink Thermalioy #61688 or equivalent “Socket (Not Shown) Robinson Nugent #0001306 or equivalent Eleewontc Molding Corp. #6241-210., 16348-188-1, 6349-188-1 or equivalent Pc Boars Circuit DOT, Ine. 4°C1119 oF equivalent 1158 W. 23rd St Tempe, Aritone 8528? “Optional a MOTOROLA LINEAR/INTERFACE DEVICES 4-92