CLF10060NIT-100M-D

R1270S-Y NISSHINBO | Alldatasheet

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34V, 3A PWM/VFM Step Down DC/DC Converter with PLL Synchronization for Industrial Applications NO.EY-299-200624 OUTLINE The R1270S is CMOS-based Step -down DC /DC converter with internal N -channel high side Tr. The ON resistance of the built -in high-side transistor is 0.10 and the R1270S can provide the maximum 3A output current. Each of t he ICs consists of an oscillator, a PWM control circuit, a voltage reference unit, an error amplifier, a phase compensation circuit, a slope compensation circuit, a soft-start circuit, protection circuits, an internal voltage regulator, a nd a switch for bootstrap circuit. The ICs can make up a s tep-down DC/DC converter with adding an inductor, resistors, a diode, and capacitors externally. The R1270S is current mode operating type DC/DC converters without an external current sense resistor, and realizes fast response and high efficiency. As an output capacitor, a ceramic type capacitor is usable. The internal oscillator frequency is adjustable over a range of 300kHz to 2400kHz by an external resistor, and also can be synchronized externally by PLL. The phase compensation is adjustable by using external resistor and capacitor. Thereby optimizations for the inductor and the capacitor can be done. To improve performance under light load conditions, the R1270S can select automatically between two modes: the VFM mo de when the inductor current is discontinuous and the PWM mode when the inductor current is continuous. The ripple voltage at VFM mode is 40mV (Typ.). As for protection, the R1270S has a current limit function to control an inductor peak current every cycle, a fold-back function to reduce the oscillator frequency under the short circuit, a thermal shutdown function, an under voltage lockout (UVLO) function, and an over voltage lockout (OVLO) function. Furthermore, the R1270S can include a latch protection function to cut off the output when the output current reaches the set current limit for a certain time. That is, the R1270S supports two types of the presence (R1270S001A) or the absence (R1270S001B) of the latch protection function. The current limit, which is fixed adjustable by an external resistor. And, the R1270S has the FLG pin to monitor the overvoltage of the FB pin voltage and the 6V rated pin. When detecting an abnormal voltage, the R1270S outputs a flag. The R1270S is available in HSOP-18 package.

FEATURES

(Max. step down ratio 160ns  fosc) (1) The output current depends on external components and conditions.

NO.EY-299-200624 Externally-adjustable by using capacitor Externally-adjustable by using resistor

• VFB Voltage Temperature Tolerance (ΔVFB/ΔTa)· ·· Typ. ±100ppm/°C (−40°C ≤ Ta ≤ 125°C)

APPLICATIONS

• FA Equipment, Smart Meters
• Surveillance Cameras and Vending Machines that are used outside or under high-temperature conditions
• Motors and Lightings that are accompanied by self-heating SELECTION GUIDE The latch type protection function is user-selectable. Product Name Package Quantity per Reel Pb Free Halogen Free R1270S001-E2-YE HSOP-18 1,000 pcs Yes Yes : Select the presence or absence of the latch type protection function. A: with Latch type protection function B: without Latch type protection function

NO.EY-299-200624 BLOCK DIAGRAMS Regulator S FLG BST LX D R VIN 5.0V VCO Limit Latch Circuit (2 msec) *1 Current Slope Circuit Peak Current Limit Circuit Set Pulse Maxduty Pulse Reset Shutdown Reset Set Current Sense Circuit EC LMT FB RT ER SS Soft Start Circuit Reference Filter PLLFLTR PLLREF Cmp φ Over/Under Voltage Detection OVP UVD OVP Thermal Shutdown UVLO OVLO Reset Shutdown CE 1.0V VIN VIN Shutdown UVD LMTOVP Limit Latch LMT OVP INT Shutdown +3.0V3.0V 2.9V Pin OVD Softstart GND Pin OVD PLLFLTR SS ER 3.3V 0.8V delay Low:PWM/VFM auto High:Fixed PWM R1270S001A/B Block Diagram1 (1) R1270S001A equips the limit latch circuit.

NO.EY-299-200624 PIN DESCRIPTIONS Pin No. Symbol Description 1, 2 LX Lx Switching Pin

3 NC No connection

4 GND Ground Pin

5 INT Internal Bias Pin

6 FB Feedback Pin

7 ER Phase Compensation Pin for External Resistor

8 EC Phase Compensation Pin for External Capacitor

9 LMT Current Limit adjustment Pin

10 PLLREF PLL Synchronization Pin

11 PLLFLTR PLL Filter Pin

12 RT Oscillation adjustment Pin

13 FLG Flag Output Pin

14 CE Chip Enable Pin (Active “H”)

15 SS Soft-start Pin

16 BST Bootstrap Pin

17, 18 VIN Power Supply Pin *The tab on the bottom of the package must be electrically connected to GND (substrate level) when mounted on the board. TOP VIEW LX FLG VIN BST SS CE FB ER EC RT LMT LX NC PLLFLTR VIN INT PLLREF 15GND PAD* R1270S (HSOP-18) Pin Configuration

NO.EY-299-200624 INTERNAL EQUIVALENT CIRCUIT FOR EACH PIN <LX Pin> <INT Pin> <FB Pin> <ER Pin > <EC Pin> <LMT Pin> LX VIN INT VIN Regulator FB Regulator VIN ER Regulator VIN EC Regulator VIN LMT VIN Regulator Regulator

NO.EY-299-200624 <PLLREF Pin> <PLLFLTR Pin> <RT Pin> <FLG Pin> <CE Pin> <SS Pin> PLLREF VIN PLLFLTR VIN Regulator RT VIN Regulator FLG CE VIN SS Regulator VIN

NO.EY-299-200624 <BST Pin> BST LX Regulator

NO.EY-299-200624 ABSOLUTE MAXIMUM RATINGS (GND = 0 V) Symbol Item Rating Unit VIN Input Voltage −0.3 to 36 V VBST BST Pin Voltage(1) VLX−0.3 to VLX+6 V VLX LX Pin Voltage −0.3 to 36 V VCE CE Pin Input Voltage −0.3 to 36 V VINT INT Pin Voltage −0.3 to 36 V VSS Soft-start Pin Voltage −0.3 to 6 V VER ER Pin Voltage −0.3 to 6 V VEC EC Pin Voltage −0.3 to 6 V VFB Feedback Pin Voltage −0.3 to 6 V VFLG Flag Pin Voltage(1) −0.3 to 24 V VPLLREF External Oscillation Synchronization Pin Voltage −0.3 to 36 V VPLLFLTR PLL Filter Pin Voltage −0.3 to 6 V VRT Oscillation adjustment Pin Voltage −0.3 to 6 V VLMT Current Limit adjustment Pin Voltage −0.3 to 6 V PD Power Dissipation(2) (HSOP-8J, JEDEC STD.51) 3900 mW Tj Junction Temperature −40 to 150 °C Tstg Storage Temperature Range −55 to 150 °C ABSOLUTE MAXIMUM RATINGS Electronic and mechanical stress momentarily exceeded absolut e maximum ratings may cause permanent damage and may degrade the lifetime and safety for both device and system using the device in the field. The functional operation at or over these absolute maximum ratings is not assured. RECOMMENDED OPERATING CONDITIONS Symbol Item Rating Unit VIN Input Voltage 3.6 to 34 V Ta Operating Temperature Range −40 to 125 °C RECOMMENDED OPERATING CONDITIONS All of electronic equipment should be designed that the mounted semiconductor devices operate within the recommended operating conditions. The semiconductor devices cannot operate normally over the recommended operating conditions, even if they are used over such conditions by momentary electronic noise or surge. And the semiconductor devices may receive serious damage when they continue to operate over the recommended operating conditions. (1) The pin voltage except VBST and VFLG must be prevented from exceeding VIN +0.3V. (2) Refer to POWER DISSIPATION for detailed information.

NO.EY-299-200624

ELECTRICAL CHARACTERISTICS

VIN = 12 V, Ta = 25°C, unless otherwise specified. The specifications surrounded by are guaranteed by design engineering at -40°C ≤ Ta ≤ 125°C. R1270S001A/B-YE Electrical Characteristics (Ta = 25°C) Symbol Item Conditions Min. Typ. Max. Unit IIN1 VIN Consumption current 1 VIN = 34 V, VINT = Open, VPLLREF = 34 V, VFB = 1.5 V 0.7 1 1.3 mA IIN2 VIN Consumption current 2 VIN = 34 V, VINT = Open, VPLLREF = 0, VFB = 0.84 V 13 18 30 µA VUVLO2 UVLO Released Voltage VIN Rising 2.5 2.6 2.7 V VUVLO1 UVLO Detect Voltage VIN Falling VUVLO2 −0.16 VUVLO2 −0.15 VUVLO2 −0.11 V VOVLO2 OVLO Released Voltage VIN Falling 34 V VOVLO1 OVLO Detect Voltage VIN Rising 38 V VFB VFB Voltage Tolerance Ta = 25°C 0.792 0.800 0.808 V −40°C ≤ Ta ≤ 125°C 0.784 0.816 V VVFM FB High Detection at VFM mode 0.831 V fosc0 Oscillation Frequency 0 RT = Open 270 300 330 kHz fosc1 Oscillation Frequency 1 RT = 62 kΩ 900 1010 1120 kHz fosc2 Oscillation Frequency 2 RT = GND 2160 2400 2640 kHz toff Minimum Off Time 120 ns DMAX0 Maximum Duty Cycle 0 RT = Open 93 % DMAX0 Maximum Duty Cycle 1 RT = 62 kΩ 83 % DMAX2 Maximum Duty Cycle 2 RT = GND 67 % fSYNC Oscillation Synchronized Frequency fPLLREF = 1000 kHz fosc/2 foscx2 kHz tss1 Soft-start Time 1 SS = Open, VFB = 0.72 V 0.3 0.55 ms tss2 Soft-start Time 2 CSS = 0.01 µF, VFB = 0.72 V 3.1 4.5 ms Itss Soft-start charge current SS = 0 V 1.7 2.0 2.35 µA tdelay Delay Time for Latch Protection for R1270S001A 1.4 2 2.8 ms RLXH Lx High Side Switch ON Resistance VBST−VLX = 4.5V, ILX = 0.1A 0.1 0.15 Ω ILXHOFF Lx High Side Switch Leakage Current 0 20 µA

NO.EY-299-200624 VIN = 12 V, Ta = 25°C, unless otherwise specified. The specifications surrounded by are guaranteed by design engineering at -40°C ≤ Ta ≤ 125°C. R1270S001A/B-YE Electrical Characteristics (Continued) (Ta = 25°C) Symbol Item Conditions Min. Typ. Max. Unit ILIMLXH1 Lx High Side Switch Limited Current 1 LMT = 220 kΩ、DC Current 3.0 3.5 4.3 A ILIMLXH2 Lx High Side Switch Limited Current 2 LMT = 39 kΩ、DC Current 1.25 1.6 2.4 A VCEH CE “H” Input Voltage 1.15 V VCEL CE “L” Input Voltage 0.85 V ICEH CE “H” Input Current −1.0 0 1.0 µA ICEL CE “L” Input Current −1.0 0 1.0 µA IFBH FB “H” Input Current VFB = 1.5 V −0.1 0 0.1 µA IFBL FB “L” Input Current VFB = 0 V −0.1 0 0.1 µA VPLLH PLLREF “H” Input Voltage 0.95 V VPLLL PLLREF “L” Input Voltage 0.67 V IPLLH PLLREF“H” Input Current −1.0 0 1.0 µA IPLLL PLLREF“L” Input Current −1.0 0 1.0 µA TTSD Thermal Shutdown Detect Temperature 160 °C TTSR Thermal Shutdown Release Temperature 130 °C Istandby Standby Current VIN = 34 V, VCE = 0 V 0 20 µA VFLGL FLAG ”L” Voltage VIN = 2.0 V, IFLG = 1 mA 0.25 V IFLGOFF FLAG ”Off” Current VFLG = 6.0 V 0.0 0.1 µA VOVP FB Pin OVP Detect Voltage 0.91 0.98 1.04 V VUVD FB Pin UVD Detect Voltage 0.59 0.64 0.69 V VFLB Fold Back Detect Voltage 0.59 0.69 V VPOVD 6V-rated Pin OVP Detect Voltage VER, VPLLFLTR, VSS 4.0 V VVOS0 INT Pin Operation Voltage 2.75 3.1 V VVOS1 INT Pin Disable Voltage 2.68 2.8 V All test items listed under Electrical Characteristics are done under the pulse load condition (Tj ≈ Ta = 25°C).

NO.EY-299-200624 THEORY OF OPERATION OVLO (Over Voltage Lock Out) Function When the input voltage to V IN pin is higher than OVLO detection voltage, the inside circuit become s standby to prevent malfunction. If the voltage on the V IN pin becomes lower than the OVLO release voltage, R1270S will restart and the soft -start function will begin. Also, t he OVLO protection has a function to prevent the possibility of the malfunction and destruction to the IC. Since the OVLO detection voltage is set higher than the absolute maximum rating for VIN pin, the function itself is not guaranteed. OVP (Over Voltage Protection) Function for FB Pin When the FB pin voltage becomes higher than the OVP detection voltage, the OVP function stops the switching of Lx pin without stopping the function of the internal circuit. When the FB pin voltage becomes lower than the OVP detect voltage, the Lx pin switching return s to normal control. If aberrant conditions around the FB pin circuit occur, the overvoltage of the output voltage may not be decreased because the R1270S indirectly monitors the output voltage via FB pin. Setup for Oscillation Frequency By using RRT between the RT pin and GND, the R1270S can control the oscillation frequency in the range of 300 kHz to 2400 kHz. For example, by using 62k as RRT, the frequency will be set about 1000kHz. When setting the frequency at either 300kHz or 2400kHz, the frequency depends on whether the RT pin is set to "Open" or "GND", without using RRT. That is, the frequency is set at 300 kHz when the RT pin is “Open”, and is set at 2400 kHz when it is “GND”. The Electrical Characteristics guarantees the oscillation frequency under the conditions stated below for fOCS0, fOCS1 and fOCS2. R1270S001A/B Oscillation Frequency Setting Resistor (RRT) vs. Oscillation Frequency (fosc) 500 1000 1500 2000 2500 3000 0 50 100 150 200 250 300 RRT[kΩ] fOSC [kHz]

NO.EY-299-200624 Synchronization of Oscillation Frequency The R1270S can synchronize to an external clock , which is input from the PLLREF pin, with using phase- locked loop. The PWM fixed mode is set during synchronization. The detection threshold of the external clock is 0.8V (Typ.) and the pulse of 100 ns or more are required. The phase compensation filter is required to stabilize the phase-locked loop. The frequency fluctuation, which is changed from the set frequency to the synchronized frequency, can be achieved smoothly by the constant of this filter. Place 10k resistor and 220pF capacitor in series between PLLFTR pin and GND. The oscillation frequency which could be synchronized is 0.5 to 2 times of that stated in the “Setup of Oscillation Frequency”. However the guaranteed oscillation frequency is 270kHz at the minimum, and 2640kHz at the maximum. Until the soft-start sequence is over, the R1270S operates at set oscillation frequency and after the soft-start sequence is over the oscillation frequency is synchronized to the external clock. The phase compensation filter is charged with limited impedance, and the filter must be charged when synchronization starts. The time required for the phase compensation filter to be charged is as bellow. POLEPLL : 1/(CPLL*(RPLL+260k)) 95% charged : 3/POLEPLL[sec] 98% charged : 4/POLEPLL[sec] Adjust the soft-start time or the timing of the external clock input as POLEPLL. The next page shows the timing chart of self oscillation and external clock input. VOUT VCPLL PLLREF fosc R1270S001A/B PLL Filter Start-up Sequence Phase Compensation Filter Charging Time > Soft-Start Time

NO.EY-299-200624 VFM/PWM Alternative Mode and PWM Fixed Mode By applying either the voltage of 0.95V or more or the external clock to the PLLREF pin, the R1270S operates in PWM fixed mode (Pulse-skip at light load). By applying the voltage of 0.67V or less to the PLLREF pin, the R1270S operates in VFM/PWM alternative mode. INT Pin Voltage By applying the voltage of 3.1 V (Typ.) or more to the INT pin via the V OUT pin, the R1270S generates 3 V internal power supply from VOUT. Thereby the R1270S can improve the efficiency of the IC in VFM mode. When IIN_VFM is as the 3 V internal current supply, the approximate expression for IC’s consumption current: IIN is VOUT / VIN  IIN_VFM. That is, the consumption current will decrease as VOUT/VIN becomes smaller. But, when the INT pin voltage is lower than 3.1 V, the consumption current will not be reduced since the internal voltage supply becomes V IN. Therefore, this architecture is aimed for applications which the V OUT is 3.3 V or more. If the VOUT is lower than 3.3 V, set the INT pin OPEN (No CINT necessary). VOUT fosc VCPLL PLLREF R1270S001A/B PLL Filter Start-up Sequence Phase Compensation Filter Charging Time < Soft-Start Time VCPLL PLLREF VOUT fosc R1270S001A/B PLL Filter Start-up Sequence Phase Compensation Filter Charging Time < Synchronous Start Time with Eternal Clock

NO.EY-299-200624 Minimum ON Time The minimum ON time is 160ns that is determined by the current sense circuit. The R1270S adopts a resistor free current control mode. By using RON (Nch driver ON resistor) as a substitute for sense resistor, the R1270S senses ILX (inductor current) according to VIN − VLX = ILX x RON. The R1270S can sense ILX only during the Nch driver is On (Lx = “High”). However, if sensing it during the occurrence of the surge current right after the driver turns On, a malfunction may occur. To avoid the malfunction, the R1270S maintains a none sensing time for a while after the driver turns On. If the current control mode and the current limit circuit will not function properly at none sensing time , the R1270S may result in a rapid deterioration of stability and current limit accuracy. Please select the output voltage settings and frequency settings so that the output voltage does not become lower than the minimum step down ratio VIN160nsfOCS. CSPD Setting The transfer function from feedback resistor of VOUT to FB pin using CSPD is VOUT/FB[s] = (RTOPRBOTCSPDs+RBOT) / (RTOPRBOTCSPDs+RTOP+RBOT) From above equation, the zero is RBOT/(RTOPRBOTCSPD) and the pole is (RTOP+RBOT)/(RTOPRBOTCSPD). At low frequency level below zero V OUT will be multiplication of R BOT/(RTOP+RBOT) which means feedback by 0.8/VOUT and when higher frequency level than the pole it will be feedback by 1. At VFM mode the ripple of VOUT is generated by 40mV (Typ.) higher than that of the reference voltage at PWM mode which is 0.8V. For all operating frequency range, the ripple of VOUT is feedback by 1 to the FB pin despite the output voltage settings ripple of V OUT will follow reference voltage by setting the C SPD large. The bellow shows the example of setting the C SPD large, where the ripple of V OUT is feedback by 1 to the FB pin, and setting the CSPD small, where the ripple of VOUT is feedback by the multiple of RBOT / (RTOP+RBOT). R1270S001A/B VFM Ripple FB vs. VOUT As shown in the above figure, the ripple of VOUT becomes larger when the CSPD is small. 0.8V FB pin Voltage 40mV 0.8V x (RTOP + RBOT) /RBOT 40mV VOUT (CSPD Small) VOUT (CSPD Large) 40mV x (RTOP + RBOT) /RBOT

NO.EY-299-200624 The recommended CSPD value is selected to minimize the ripple of VOUT. When changing the RBOT value from the recommended value, please make sure the RBOTCSPD is also in the range of the recommended value and change the CSPD together. Also, changing L, COUT, RER, CEC from the recommended value is required to change the CSPD. Furthermore, if the ripple of the VOUT is permissible, improving the loop stability is possible by adjusting the positive bump of the zero and pole. First, measure the voltage drop of the output by the load transient response without CSPD. Then measure the voltage drop again with attachment of small enough CSPD. If the selected CSPD is too small, the amount of the voltage drop will be the same value as the value without C SPD. Repeat the procedure with increasing CSPD value gradually. When the voltage drop begins to improve, suppose that value as CSPD1. Further try other CSPD value by increasing it gradually, then the voltage drop improvement will stop. Suppose that the CSPD value as Cspd2. The appropriate C SPD value can be calculated as the next formula; CSPD=√(CSPD1 CSPD2). The zero will be low and pole will be high of the feedback resistor at the whole frequency range, the ripple at VFM mode will be lower than that VOUT (CSPD small) of above diagram FLAG Output Function The R1270S has an Nch open drain FLAG output. When abnormality is detected, the R1270S switches the Nch transistor On, and sets the FLG pin to “Low”. When the abnormality is removed, the R1270S switches the Nch transistor Off and sets the FLG pin to “High” (VFLGIN). The UVD will function only when V FB<0.64V (Typ.) and at max duty detection or VFB<0.64V (Typ.) and current limit detection to prevent abnormal output behavior at load transient and input transient response. The following are the abnormal conditions that the IC can detect.

• CE=”L” (Shut down)
• UVLO (Shut down)
• Thermal Shutdown
• during soft-start time (Css<0.72V)
• VFB Under Voltage Detection (Typ.0.64V) and maxduty detection
• VFB Under Voltage Detection (Typ.0.64V) and current limit detection
• LMT pin Over Voltage Protection (Typ.1.2V)
• Absolute maximum 6V pin (except FB pin、LMT pin、EC pin) Over Voltage Detection (Typ.3.0V)
• When the latch protection runs (R1270S001A) The FLG pin is designed to keep 0.4V or less when the current running into the FLG pin is at 1mA. The recommended values of VFLGIN and RFLG are 6V or less for VFLGIN and 10k to 100k for RFLG. When the FLAG function is not used, set the FLG pin OPEN or connect to GND.

NO.EY-299-200624 R1270S001A/B FLAG Circuit R1270S001A/B FLAG Start-up / Shutdown Sequence FLG R FLG V FLGI N V FLG R1270S “H” is detected under abnormal condition. V CE 1.0V time V FB 0.800V(Typ.) V UVD 0.64V(Typ.) 0.72V(Typ.) time V FLG t ss FLGIN 0.4V> time

NO.EY-299-200624 Soft-Start Time Function The soft-start time is between from ”H” level of CE to 90% of FB (0.72V). The soft-start time for the R1270S could be adjusted by using an external capacitor C SS at the SS pin from minimum of internal soft -start time typically (reaching the set output voltage is 4.0ms (typ.)) when CSS is 0.01µF. If not required to adjust the soft- start time, set the SS pin OPEN. On the condition described in the chapter of “Electrical Characteristics”, the R1270S guarantees each of soft-start time (tss1/tss2) when the SS pin is set to “Open” or when CSS is set to 0.01µF. CSS [μF] = 2 × tss / 0.72 R1270S001A/B Capacitor for Soft-Start Time Adjustment (CSS) vs. Soft-Start Time (tss) Also, when CSPD is set large, the rising speed of VOUT may become slower than the soft -start time because of the bypass characteristic of the feedback resistor. Because the R1270S watches the output voltage using the FB pin voltage, the flag detection may be released before the VOUT is fully at set value. 0.8V(Typ.) 0.72V(Typ.) VFB VOUT VSET tSS VFLG VFLGIN R1270S001A/B Start-up / Shutdown Sequence

NO.EY-299-200624 Lx Current Limit By using external resistor RLMT to the LMT pin, Lx current limit (ILIMLXH), which is high-side switch current limit, can be adjusted as typical 4.5A at maximum. When RLMT is 54k, the Lx current limit is set at 2.0A typical. If not required to adjust Lx current limit, set LMT pin OPEN so that the Lx current limit will be set at typically 4.5A. Setting at 1.5A or less is not recommended. On the condition described in the chapter of “Electrical Characteristics”, the R1270S guarantees each of LX limited current (ILIMLXH1/ILIMLXH2) when connected each of 39 kΩ/220kΩ resistors to the LMT pin. R1270S001A/B LX Current Limit Adjustment Resistor (RLMT) vs. LX Limit Current (ILIMLXH) BST Auxiliary Charge Circuit Under the oscillation frequency or conditions of input/output voltage level and load current, the BST capacitor charge may not be sufficient, and hence BST-Lx pin voltage level (typ.5.0V) may not be reached. However, if the output voltage or another power line at 4.5V to 6.0V is supplied to the R1270S, a drop of BST pin voltage level can be prevented by connecting BST auxiliary charge circuit with BST pin via a diode. In this case, the voltage of Lx pin must be less than the voltage of the auxiliary charge circuit to charge C BST. Also, make sure not to exceed the maximum rating of 6.0V for BST-Lx. When selecting the diode, 10mA current rating is more than enough, but also be aware of the voltage rating, and the characteristic of reverse bias leak current at high temperature. R1270S D COUT VOUT CIN VIN LX CBST VIN BST DBST VBSTIN GND CBSTIN R1270S001A/B BST Charging Circuit 100 200 300 400 500 1.5 2 2.5 3 3.5 4 4.5 ILIMLXH [A] RLMT [kΩ]

NO.EY-299-200624 Sequence Composition By using the soft-start time and the FLAG function (R1270S001A/B), a power up sequence can be composed. The following describes an example application circuit to start up both DC/DC1 and DC/DC2 in a sequence so that the 5.0V output will not to become lower than the DC/DC2 output 3.3V under the following conditions: the input voltage is 12V, two lines of output voltages are 5.0V (DC/DC1) and 3.3V (DC/DC2), the capacitor of the 5.0V output is an electrolytic 470µF, and the capacitor of the 3.3V output is electrolytic 100µF. ◼ Soft-start time and charging current During the soft-start, the R1270S occurs the charging current ICHRG for the capacitor of VOUT besides the output current IOUT. Therefore, the output current IOUTSS will be given by the following equation, IOUTSS = IOUT + ICHRG = IOUT + VOUT x (COUT + CL)/tSS For the output current on the example application circuit, (DCDC1) IOUTSS = IOUT + VOUT/(COUT + CL)/tSS = IOUT + 5.0V x (10μF + 470μF)/26ms = IOUT + 92mA (DCDC2) IOUT2SS = IOUT2 + VOUT2/(COUT2 + CL2) / tSS = IOUT + 3.3V x (10μF + 100μF)/2.6ms = IOUT2 + 140mA Make sure that the output current does not exceed 3.0A even at soft-start. ◼ Using the output of R1270S as the flag pull-up voltage The R1270S has an Nch open drain FLAG output. When detecting an abnormal condition, the R1270S switches the Nch transistor On and sets the FLG pin to “Low”. If the detected condition is not applicable under the FLAG output function, FLAG output will reset to “High” after the completion of the soft -start. When using the VOUT as the VFLGIN, “High” level of the VFLG becomes the same with VOUT. ◼ Using the FLAG output as CE pin input for another R1270S The minimum VCEL is 0.85V and the maximum VCEH is 1.15V. The maximum VFLGL is 0.4V, and VFLGH for DC/DC1 on the example circuit is 5.0V. So, VFLG is usable as CE input for DC/DC2. ◼ Using the FLAG output as auto-discharge function When being shut down, the R1270S switches the Nch transistor On and sets the FLG pin to “Low”. And, VFLGIN sends the FLAG current I FLG via RFLG and Nch transistor. Thereby, the capacitor connected to VOUT can be discharged by using VOUT as VFLGIN. The maximum IFLG is that of VFLGIN divided by RFLG. Set RFLG so that maximum IFLG becomes lower than 5mA. Do not connect VOUT directly to FLG pin because the IFLG may become excessive and may damage the IC. The VFLGL is regulated as IFLG=1mA. When the RFLG is set higher than IFLG=1mA, the maximum voltage 0.4V of VFLGL is not guaranteed, hence the FLAG function itself may be spoiled.

NO.EY-299-200624 (DCDC1) R1270S001A/B: VIN = 12 V, VOUT = 5.0 V, tss = 40 ms (CSS = 0.1 μF) (DCDC2) R1270S001A/B: VIN = 12 V, VOUT = 3.3 V, tss = 4.0 ms (CSS = 0.01 μF) CBST CIN VIN 12V CSS 0.1µF L COUT 10F VOU T 5.0V RTOP RBOT D CSPD GND Lx VIN BST FB FLG CE TSS R1270S001A/B RFLG 10k RCE CBS T2 CIN2 CSS2 0.01µF COU T2 10F VOUT 2 3.3V RTOP2 RBOT2 CSPD2 GND Lx VIN BST FB FLG CE TSS R1270S001A/B RFLG2 1.0k CL 470F CL2 100F VCE VFLG VFLG 2 IFLG 2 DCDC1 DCDC2 IOUT IOU T2 Example Circuit of Sequence Composition

NO.EY-299-200624 Operation of the Buck Converter and the Output Current The DC/DC converter charges energy in the inductor when the switch turns on, and discharges the energy from the inductor when the switch turns off and controls with less energy loss, so that a lower output voltage than the input voltage is obtained. Refer to the following figures. Switch L Diode VIN VOUT COUT GND Basic Circuit Current Through Inductor Step 1: The switch turns on and current IL (=i1) flows, and energy is charged into COUT. At this moment, IL increases from ILmin (=0) to reach ILmax in proportion to the on-time period (ton) of the switch. Step 2: When the switch turns off, the diode turns on in order to maintain IL at ILmax, and current IL ( =i2) flows. Step 3: IL (=i2) decreases gradually and reaches IL = ILmin = 0 after a time period of topen, and the diode turns off. This case is called as discontinuous mode. If the output current becomes large, next switching cycle starts before IL becomes 0 and the diode turns off . In this case, IL value increases from ILmin (>0), and this case is called continuous mode. As for the PWM control system, the output voltage is maintained by control ling the on-time period (ton), with the oscillator frequency (fosc) being maintained constant. t=1/fosc toff topen ILmin ton IL

NO.EY-299-200624 Output Current and Selection of External Components The relation between the output current and external components is as follows: When the switch of LX turns on: Wherein, the peak to peak value of the r ipple current is described as IRP, the ON resistance of the switch is described as RONH, and the diode forward voltage as VF, and the DC resistance of the inductor is described as RL, and on time of the switch is described as ton. When the switch turns off (the diode turns on) as toff: Put Equation 2 to Equation 1 and solve for ON duty of the switch, ton / (ton + toff) = DON, Ripple Current is as follows: Then, peak current that flows through L, and the peak current ILmax is as follows: As for the valley current ILmin, If ILmin<0, the step-down DC/DC converter operation becomes current discontinuous mode. Therefore the current condition of the current discontinuous mode, the next formula is true. Consider ILmax and ILmin, conditions of input and output and select external components. *The above explanation is based on the calculation in an ideal case in continuous mode.

NO.EY-299-200624 Ripple Current and Lx Limited Current The ripple current of the inductor may change according to the various reasons. In the R1270S series, as an Lx current limit, Lx peak current limit is used. Therefore the upper limit of the inductor current is fixed. The peak current limit is not the average current of the inductor (output current). If the ripple current is large, peak current becomes also large. The characteristic is used for the fold back current limit of version B/D. In other words, the peak current limit is maintained and the switching frequency is reduced, as a result, the average current of the inductor is reduced. To release this condition, the peak current must not exceed the peak current limit. Latch Protection Function (R1270S001A) The latch function is enabled after the completion of the soft-start. The latch function works after detecting current limit and starts the internal counter. After the internal counter reaches 2ms (Typ.), the latch function turns the output off. The R1270S has two ways to reset the latch function: one is to set the CE pin “L”, and another one is to set the VIN voltage to become equal to the detection voltage of the UVLO function, or become less. Also, the latch function is reset when the FB pin voltage is 2.0V (Typ.) or more. The start condition for the internal counter is to detect the limited current at each clock, and the reset condition is when a frame without detecting the limit current occurs. When a ringing between the output voltage and the short-circuit impedance including large inductance occurs and the FB pin voltage exceeds 0.80V (Typ.), take note that the latch timer might be reset. Fold-back Protection Function After the soft-start period, fold back protection is enabled. When there is abnormality to the output and the FB voltage becomes lower than 0.64V typical, the oscillation frequency will be limited at 1/2. Furthermore, when the output voltage drops below 50% typical from the set voltage (FB pin voltage 0.4V), oscillation frequency will be limited proportional to the FB pin voltage level. By reducing frequency, the ripple current increases. The R1270S has the peak current limit function, therefore as in the equation 8, the Lx average current decreases by the increase of the ripple current. If the FB pin voltage becomes less than 0.64V, the oscillator frequency is reduced to 1/2. At heavy load, if the R1270S becomes into the fold-back protection mode, the situation may not be released by the increased ripple current. This fold-back protection function is to provide a high degree of safety to the R1270S, not to secure reliability. When using the IC without the latch protection function (R1270S001B), a measure to prevent shorting is required.

NO.EY-299-200624 LX Limited Current Function Sequence VOUT VOUT setting Voltage R1270*001A 2msec t IOUT 0 2ms(Typ.) VOUT short Limit Latch VOUT open reset VOUT VOUT setting Voltage R1270*001B t IOUT VOUT short VOUT open FB<0.64V FB<0.4V FB<0.64V FB<0.4V shutdown

NO.EY-299-200624 Loss and Efficiency Illustrated Description for Loss PON = RONH x IOUT2 x Onduty : loss at switching ON PF = (tR + tF) / 2 × VIN x IOUT x fosc : switching loss POFF = VF × IOUT x Offduty : loss of diode PL = RL x IOUT2 : loss of inductor PD = VIN x ISS : consumption current if IC PPP = 1 / 4 x RC x IRP2 : loss by ripple of the inductor current Efficiency η = (VOUT x IOUT) / ((VOUT x IOUT) + PON + PF + PCL + PD + PPP) x 100% The loss that generated by R1270S is PON, PF, PD. These losses are converted to heat inside the IC. Therefore, the R1270S must be used within the condition below is required. Tj = θja x (PON + PF + PD) +Ta < 150ºC L O A D RONH Lx RL VF VOUT VIN IOUT VIN GND tR tF Lx RC L COUT

NO.EY-299-200624

APPLICATION INFORMATION

Typical Application Circuits “H”active L D GND GND CSS RCE RFLG CBST RRT RPLL CPLL RPLLREF RLMT RER RBOT RTOP CSPD CEC COUT VOUT CINT CIN VIN VFLGIN VFLG VCE VPLLIN TOP VIEW LX FLG VIN BST SS CE FB ER EC RT LMT LX NC PLLFLTR VIN INT PLLREF 15GND PAD RFB RPLLREF2* * PLLREF pin must not be “OPEN”. When using our evaluation board, a pull-down resistor (RPLLREF2：100kΩ) is contained on the evaluation board. R1270S001A/B Typical Application Circuit “H”active L D GND GND CBST RBOT RTOP CSPD CEC COUT VOUT CIN VIN VCE TOP VIEW LX FLG VIN BST SS CE FB ER EC RT LMT LX NC PLLFLTR VIN INT PLLREF PAD GND RFB RER *1 * When not connecting a phase compensation resistor of RER (the ER pin is “OPEN”), characteristics of load transient response becomes deteriorated, as compared with when connecting the RER resister. Please make through evaluation before determining whether connecting the RER resister or not. R1270S001A/B Minimum Composition Circuit

NO.EY-299-200624 R1270S001A/B, Recommended Components of CIN, COUT VIN , VOUT Capacitor Spec. Component Name Maker ≤ 16 V 0.47 µF 25 V/125°C CGA4J2X7R1E474K TDK ≤ 16V 2.2 μF 25 V/125°C CGA4J3X7R1E225K All 2.2 μF 50 V/125°C CGA5L3X7R1H225K ≤ 16V 4.7 μF 25 V/125°C CGA5L1X7R1E475K All 4.7 μF 50 V/125°C CGA6P3X7R1H475K All 10 μF 50 V/125°C CGA6P3X7S1H106K ≤ 16 V 10 μF 25 V/125°C CGA6P1X7R1E106K ≤ 10 V 22 μF 16 V/125°C CGA6P1X7R1C226M ≤ 16 V 22 μF 25 V/125°C CGA8P1X7R1E226M R1270S001A/B, Recommended Components of CBST VOUT Capacitor Spec. Component Name Maker All 0.47 μF 16 V EMK212BJ474KD-T Taiyo Yuden All 0.47 μF 25 V CGA4J2X7R1E474K TDK R1270S001A/B, D Recommended Components VIN Spec. Component Name Maker All 40 V/3 A RB056L-40TE ROHM All 40 V/3 A RB058L-40TE All 60 V/3 A RB058L-60TE All 40 V/3 A CMS30I40A TOSHIBA R1270S001A/B, L Recommended Components Inductor Spec. Component Name Maker 1.0 µH 6.4 A RLF7030T-1R0N6R4 TDK

6.5 A CLF7045NIT-1R0N-D

1.5 µH 7.3 A CLF7045T-1R5-D

5.4 A CLF7045NIT-1R5N-D

2.2 µH 5.5 A CLF7045T-2R2-D

5.1 A CLF7045NIT-2R2N-D

4.7 µH 5.4 A CLF10040T-4R7-D

4.1 A CLF10060NIT-4R7N-D

10 µH 4.0 A CLF10040T-100M-D

3.0 A CLF10060NIT-100M-D

10 µH 6.7 A CLF12555T-100M-D

6.4 A CLF12577NIT-100M-D

15 µH 5.4 A CLF12555T-150M-D

5.1 A CLF12577NIT-150M-D

22 µH 4.2 A CLF12555T-220M-D

4.3 A CLF12577NIT-220M-D

NO.EY-299-200624 Selection of External Components ⚫ Using ceramic capacitors with low ESR (Equivalent Series Resistance) are recommended. The recommended capacitor for CIN between VIN and GND is 4.7 µF or more. Verify the bias dependence and the temperature characteristics of the ceramic capacitors. Recommend ed conditions are written based on the case which the recommended parts are used with the R1270S. ⚫ The R1270S is designed with the recommended inductance value and the COUT ceramic capacitor value to make phase compensation. If the inductance value is large, a lack of the current sensing amount in the current mode might result in an unstable operation. Oppositely, if the inductance value is small, an excess of the current sensing amount might result in the occurrence of the low frequency oscillation on when the on duty ratio is beyond 50%. Ensure that capacitors using for C OUT can meet the voltage - dependent properties in order to have bias dependence. Recommended conditions are written based on the case which the recommended parts are used with the R1270S. ⚫ If the inductance value is small, a ripple to inductor current will be increased and the peak current of the switching will be increased as the load current increases. As a result, the current might reach the current limit value and the current limit might work. ⚫ As for the diode, connect a schottky diode with small capacitance between terminals. The reference characteristic of the capacitance between terminals is around 100 pF or less at 10 V. If using a schottky diode with large capacitance, the operation of the R1270S might be unstable by a flow of an excess switching current. When the capacitance of the schottky diode used is beyond 100 pF at 10 V or is unknown, make sure that the R1270S does not have issues of the load regulation, the line regulation, and the load transient response. And, connect a diode having the smallest possible reverse current IR. Especially, IR’s rising under high temperature conditions might cause a thermal runaway and will lead to cause damage to the IC. ⚫ Output voltage (V OUT) can be set by adjustable values of R TOP and R BOT being expressed by the following equation, VOUT = VFB x (RTOP + RBOT) / RBOT. For example, when setting VOUT = 12 V, and setting RBOT = 16 k, RTOP = (12 V / 0.8 V-1)  (16 k) = 224 k. By using the E24 type resistors to make 224 k, you need (200 k + 24 k) and use them in series. If the tolerance level of the output voltage is relatively wide you may set the output voltage as 11.80 V = 0.8 V  (220 k + 16 k) / 16 k. In this case RTOP will be a single resistor of 220 k. When the values of RTOP and RBOT become larger, the R1270S is susceptible to noise with increasing the impedance of FB pin. The recommended value range of R BOT is approximately between 1.0 kΩ to 160 kΩ. If the operation is unstable, reduce the impedance of FB pin.

NO.EY-299-200624 ⚫ As for the CE pin and the PLLREF pin, an up diode for VIN, which have efficacy as ESD protection element, is internally connected to each pin. If CE pin voltage or PLLREF pin voltage may become higher than VIN pin voltage, connect a resistor between CE or PLLREF and VIN pin to prevent flowing large current from CE pin or PLLREF pin to VIN pin. When using external oscillation synchronization, the input signal must be used to become lower than the VIN voltage without using a resistor because the input voltage of PLLREF is filtered out via the resistor. ⚫ When using a phase compensation resistor pin (ER pin), the recommended value range of RER is 220 kΩ or more. If not using phase the compensation resistor pin, the ER pin must be set to “OPEN”. ⚫ The RFB is the resistance to prevent feedback of the noise to the FB pin. The appropriate value is about 1 kΩ. ⚫ The BST voltage might fall depending on how to use the R1270S. By drops of the BST voltage, R1270S might not function properly. As result, the current limit detection may be caused by an inductor current lower than the set current limit value by reducing the effect. ⚫ The R1270S has the driver buffer and the BST voltage detector between BST and Lx pins. When the R1270S is in PWM fixed mode and the light load current is caused by requiring the consumption current always, VOUT might move up by the consumption current. In this case, the load current including the feedback resistor must be set to 0.5 mA or more. In VFM/PWM alternative mode, the R1270S has no problem, as long as RBOT is set between 1.0 kΩ and 160 kΩ. ⚫ Recommended ratings to principal set output voltages are as following: R1270S001A/B, 300 kHz Recommended Constant VOUT CIN [μF] L [μH] COUT [μF] CBST [μF] CSPD [pF] RTOP [kΩ] RBOT [kΩ] RRT [kΩ] RER [kΩ] CEC [pF] 0.8 ≤ VOUT ≤ 1.5 10 10 47 0.47 Open *1 160 Open 470 2200 1.0 ≤ VOUT ≤ 6 10 10 47 0.47 100 [1000]*4 *1 160 [16]*4 Open 470 2200 1 ≤ VOUT ≤ VIN × DMAX*2 10 15 47 0.47 100 [1000]*4 *1 160 [16]*4 Open 470 2200 R1270S001A/B, 1000 kHz Recommended Constant VOUT CIN [μF] L [μH] COUT [μF] CBST [μF] CSPD [pF] RTOP [kΩ] RBOT [kΩ] RRT [kΩ] RER [kΩ] CEC [pF] 1 ≤ VOUT ≤ 6 4.7 2.2 47 0.47 2200 *1 16 62 470 220 1 ≤ VOUT ≤ 15 4.7 4.7 47 0.47 2200 *1 16 62 470 220 5 ≤ VOUT ≤ VIN × DMAX 4.7 4.7 47 0.47 470 *1 16 62 680 220 5 ≤ VOUT ≤ VIN × DMAX *2 4.7 10.0 47 0.47 1000 *1 16 62 680 470 *1 RTOP = (VOUT / VFB-1) x (RBOT) *2 Condition recommended at VIN > 18 V *4 If RBOT is 16 kΩ, the constant value of CSPD requires ten times as much as when RBOT is 160 kΩ.

NO.EY-299-200624 R1270S001A/B, 2400 kHz Recommended Constant VOUT CIN [μF]*3 L [μH] COUT [μF] CBST [μF] CSPD [pF] RTOP [kΩ] RBOT [kΩ] RRT [kΩ] RER [kΩ] CEC [pF] 1 ≤ VOUT ≤ 6 2.2 1.0 22 0.47 1000 *1 16 0.0 470 220 1 ≤ VOUT ≤ 9 2.2 2.2 22 0.47 1000 *1 16 0.0 470 220 5 ≤ VOUT ≤ VIN × DMAX *2 2.2 4.7 22 0.47 1000 *1 16 0.0 680 470 *1 RTOP = (VOUT / VFB-1) x (RBOT) *2 Condition recommended at VIN > 18 V *3 4.7 µF or more recommended at VOUT < 5 V

NO.EY-299-200624 TECHNICAL NOTES The performance of a power source circuit using this device is highly dependent on a peripheral circuit. A peripheral component or the device mounted on PCB should not exceed its rated voltage, rated current or rated power. When designing a peripheral circuit, please be fully aware of the following points. (Refer to PCB Layout Considerations below.) ⚫ External components must be connected as close as possible to the ICs and make wiring as short as possible. Especially, the capacitor connected in between VIN pin and GND pin must be wiring the shortest. If their impedance is high, internal voltage of the IC may shift by the switching current, and the operating may be unstable. Make the power supply and GND lines sufficient. ⚫ The backside thermal pad of the HSOP-18 package must be connected to GND. To improve the thermal dissipation on multi -layered boards, the thermal must be dissipated to another layer by putting some thermal vias on the thermal pad in the land pattern. ⚫ NC pin must be set to “OPEN”. ⚫ Switching regulator is required some caution. Because, a large current variation occurs by the following different current loops in every switching, and a high-frequency noise occurs by parasitic current. ▪ The current loop when the switch is “ON”, Input Capacitor (CIN) → Hi-side Switch → Inductor → Output Capacitor (COUT) → CIN ▪ The current loop when the switch is “OFF”, Rectifier Diode (D) → Inductor →COUT → D ▪ The current loop via Diode Parasitic Capacitor when the switch is “ON”, C IN → Hi-side Switch → Parasitic Capacitor of D →CIN A large EMI noise source is caused in this loop. Therefore, extreme caution is required. These loops have to design as short as possible, and design not to cross lines in the subsequent load side to C OUT in order to avoid the influence of switching noise. ⚫ The line between the Lx pin and the inductor have to wire as close as possible in order to avoid the parasitic capacitor. ⚫ It is recommended the input capacitor (CIN) and the rectifier diode (D) be placed on the same side with the R1270x chip. If placing the other side through via-hole, noise may increase by a parasitic inductance of via. And, it may have the influence on ringing of the Lx pin voltage. ⚫ The power lines (V IN, GND) have to design as widely as possible in order to avoid the parasitic inductance. And, the CIN have to place as close to between VIN and GND as possible.

NO.EY-299-200624 ⚫ On this evaluation board, the land for the Lx pin is wide to connect with large inductor and diode. ⚫ VOUT feedback has to be provided near COUT. ⚫ RTOP, RBOT, and CSPD pins have to design as close to the FB pin as possible and to keep a distance from the Lx and the BST pins in order to avoid the influence of noise. R1270X001 Typical Board Layout Top View Bottom View

NO.EY-299-200624 TYPICAL CHARACTERISTICS Note: Typical Characteristics are intended to be used as reference data; they are not guaranteed. 1) FB Voltage vs. Temperature 2) Oscillation Frequency 0 vs. Temperature 3) Maximum Duty cycle 0 vs. Temperature 4) Oscillation Frequency 1 vs. Temperature 5) Maximum Duty cycle 1 vs. Temperature R1270 Feedback Voltage VIN = 12V 0.792 0.794 0.796 0.798 0.8 0.802 0.804 0.806 0.808 -40 -20 0 20 40 60 80 100 120 Ta [°C] VFB [V] R1270 Oscillation Frequency 0 VIN = 12V 270 280 290 300 310 320 330 -40 -20 0 20 40 60 80 100 120 Ta [°C] fOSC0 [kHz] R1270 Maximum Duty Cycle 0 VIN = 12V 100 -40 -20 0 20 40 60 80 100 120 Ta[°C] DMAX0 [%] R1270 Maximum Duty Cycle 1 VIN = 12V 100 -40 -20 0 20 40 60 80 100 120 Ta [°C] DMAX1 [%] R1270 Oscillation Frequency 1 VIN = 12V 900 920 940 960 980 1000 1020 1040 1060 1080 1100 -40 -20 0 20 40 60 80 100 120 Ta [°C] fOSC1 [kHz]

NO.EY-299-200624 6) Oscillation Frequency 2 vs. Temperature 7) Maximum Duty cycle 2 vs. Temperature 8) Soft-start time 1 vs. Temperature 9) Soft-start time 2 vs. Temperature 10) Delay time for latch protection vs. Temperature R1270 Oscillation Frequency 2 VIN = 12V 2160 2240 2320 2400 2480 2560 2640 -40 -20 0 20 40 60 80 100 120 Ta [°C] fOSC2 [kHz] R1270 Maximum Duty Cycle 2 VIN = 12V 100 -40 -20 0 20 40 60 80 100 120 Ta [°C] DMAX2 [%] R1270 Soft-Start Time 1 VIN = 12V 0.2 0.3 0.4 0.5 0.6 0.7 0.8 -40 -20 0 20 40 60 80 100 120 Ta [°C] TSS1 [ms] R1270 Soft-Start Time2 VIN=12V 3.1 3.3 3.5 3.7 3.9 4.1 4.3 4.5 -40 -20 0 20 40 60 80 100 120 Ta[°C] TSS2[ms] R1270x001A Delay Time for Latch Protection VIN = 12V 1.2 1.4 1.6 1.8 2.2 2.4 2.6 2.8 -40 -20 0 20 40 60 80 100 120 Ta[°C] tDLY[ms]

NO.EY-299-200624 11) High side switch current limit1 vs. Temperature 12) High side switch current limit2 vs. Temperature 13) CE “H” Input voltage vs. Temperature 14) CE “L” Input voltage vs. Temperature 15) Consumption Current 1 16) Consumption Current 2 R1270 Hi-side Sw itch Current Limit 1 VIN = 5.0V -5.8 -5.6 -5.4 -5.2 -4.8 -4.6 -4.4 -4.2 -40 -20 0 20 40 60 80 100 120 Ta [°C] ILIMLXH1 [A] R1270 Hi-side Sw itch Current Limit 2 VIN = 5.0V -2.8 -2.6 -2.4 -2.2 -1.8 -1.6 -1.4 -1.2 -40 -20 0 20 40 60 80 100 120 Ta[°C] ILIMLXH2 [A] R1270 CE"H" Input Voltage VIN = 12V 0.9 0.95 1.05 1.1 -40 -20 0 20 40 60 80 100 120 Ta [°C] VCEH [V] R1270 CE"L" Input Votlage VIN = 12V 0.9 0.95 1.05 1.1 -40 -20 0 20 40 60 80 100 120 Ta [°C] VCEL [V] R1270 Consumption Current 1 VIN = 34V 500 600 700 800 900 1000 1100 1200 1300 1400 1500 -40 -20 0 20 40 60 80 100 120 Ta [°C] IIN1 [uA] R1270 Consumption Current 2 VIN = 34V -40 -20 0 20 40 60 80 100 120 Ta [°C] IIN2 [uA]

NO.EY-299-200624 17) UVLO Release voltage vs. Temperature 18) UVLO Threshold voltage vs. Temperature 19) Output current vs. Efficiency VOUT = 1.8 V VOUT = 3.3 V R1270 UVLO Release Voltage 2.35 2.4 2.45 2.5 2.55 2.6 2.65 2.7 2.75 -40 -20 0 20 40 60 80 100 120 Ta [°C] VUVLO2 [V] R1270 UVLO Threshold Voltage 2.35 2.4 2.45 2.5 2.55 2.6 2.65 2.7 2.75 -40 -20 0 20 40 60 80 100 120 Ta [°C] VUVLO1 [V] fosc = 300kHz / VOUT = 1.8V 100 0.01 0.1 1 10 100 1000 10000 Output Current [mA] Efficiency [%] 12V VFM<->PWM 12V PWM 24V VFM<->PWM 24V PWM ( Ta = 25°C)( Ta = 25°C) fosc = 450kHz / VOUT = 1.8V 100 0.01 0.1 1 10 100 1000 10000 Output Current [mA] Efficiency [%] 12V VFM<->PWM 12V PWM 24V VFM<->PWM 24V PWM ( Ta = 25°C)( Ta = 25°C) fosc = 300kHz / VOUT = 3.3V 100 0.01 0.1 1 10 100 1000 10000 Output Current [mA] Efficiency [%] 12V VFM<->PWM 12V PWM 24V VFM<->PWM 24V PWM ( Ta = 25°C)( Ta = 25°C) fosc = 450kHz / VOUT = 3.3V 100 0.01 0.1 1 10 100 1000 10000 Output Current [mA] Efficiency [%] 12V VFM<->PWM 12V PWM 24V VFM<->PWM 24V PWM ( Ta = 25°C)( Ta = 25°C)

NO.EY-299-200624 VOUT = 3.3 V VOUT = 5.0 V fosc = 1000kHz / VOUT = 3.3V 100 0.01 0.1 1 10 100 1000 10000 Output Current [mA] Efficiency [%] 12V VFM<->PWM 12V PWM 24V VFM<->PWM 24V PWM ( Ta = 25°C)( Ta = 25°C) fosc = 300kHz / VOUT = 5.0V 100 0.01 0.1 1 10 100 1000 10000 Output Current [mA] Efficiency [%] 12V VFM<->PWM 12V PWM 24V VFM<->PWM 24V PWM ( Ta = 25°C)( Ta = 25°C) fosc = 450kHz / VOUT = 5.0V 100 0.01 0.1 1 10 100 1000 10000 Output Current [mA] Efficiency [%] 12V VFM<->PWM 12V PWM 24V VFM<->PWM 24V PWM 系列3 系列4 系列5 ( Ta = 25°C)( Ta = 25°C) fosc = 1000kHz / VOUT = 5.0V 100 0.01 0.1 1 10 100 1000 10000 Output Current [mA] Efficiency [%] 12V VFM<->PWM 12V PWM 24V VFM<->PWM 24V PWM ( Ta = 25°C)( Ta = 25°C) fosc = 2000kHz / VOUT = 5.0V 100 0.01 0.1 1 10 100 1000 10000 Output Current [mA] Efficiency [%] 12V VFM<->PWM 12V PWM ( Ta = 25°C)

NO.EY-299-200624 VOUT = 7.0 V VOUT = 12 V fosc = 300kHz / VOUT = 7.0V 100 0.01 0.1 1 10 100 1000 10000 Output Current [mA] Efficiency [%] 12V VFM<->PWM 12V PWM 24V VFM<->PWM 24V PWM ( Ta = 25°C)( Ta = 25°C) fosc = 450kHz / VOUT = 7.0V 100 0.01 0.1 1 10 100 1000 10000 Output Current [mA] Efficiency [%] 12V VFM<->PWM 12V PWM 24V VFM<->PWM 24V PWM ( Ta = 25°C)( Ta = 25°C) fosc = 1000kHz / VOUT = 7.0V 100 0.01 0.1 1 10 100 1000 10000 Output Current [mA] Efficiency [%] 12V VFM<->PWM 12V PWM 24V VFM<->PWM 24V PWM ( Ta = 25°C)( Ta = 25°C) fosc = 2000kHz / VOUT = 7.0V 100 0.01 0.1 1 10 100 1000 10000 Output Current [mA] Efficiency [%] 12V VFM<->PWM 12V PWM ( Ta = 25°C) fosc = 300kHz / VOUT = 12V 100 0.01 0.1 1 10 100 1000 10000 Output Current [mA] Efficiency [%] 24V VFM<->PWM 24V PWM ( Ta = 25°C) fosc = 450kHz / VOUT = 12V 100 0.01 0.1 1 10 100 1000 10000 Output Current [mA] Efficiency [%] 24V VFM<->PWM 24V PWM ( Ta = 25°C)

NO.EY-299-200624 VOUT = 12 V fosc = 1000kHz / VOUT = 12V 100 0.01 0.1 1 10 100 1000 10000 Output Current [mA] Efficiency [%] 24V VFM<->PWM 24V PWM ( Ta = 25°C) fosc = 2000kHz / VOUT = 12V 100 0.01 0.1 1 10 100 1000 10000 Output Current [mA] Efficiency [%] 24V VFM<->PWM 24V PWM ( Ta = 25°C) fosc = 2400kHz / VOUT = 12V 100 0.01 0.1 1 10 100 1000 10000 Output Current [mA] Efficiency [%] 24V VFM<->PWM 24V PWM ( Ta = 25°C)

NO.EY-299-200624 20) Load Transient Response fosc = 300 kHz fosc = 1000 kHz 3.7 3.7 3.7 3.7 3.3 3.5 3.7 Output Current [A] Output Voltage [V] Time [ms] f = 300kHz / VOUT = 3.3V / VFM<=>PWM VIN = 12V / 0A <-> 1A OUTPUT VOLTAGE OUTPUT CURRENT 3.7 3.7 3.7 3.7 3.3 3.5 3.7 Output Current [A] Output Voltage [V] Time [ms] f = 300kHz / VOUT = 3.3V / VFM<=>PWM VIN = 12V / 0A <-> 1A OUTPUT VOLTAGE OUTPUT CURRENT 3.9 3.9 3.9 3.9 2.9 3.1 3.3 3.5 3.7 3.9 Output Current [A] Output Voltage [V] Time [ms] f = 300kHz / VOUT = 3.3V / VFM<=>PWM VIN = 12V / 1A <-> 3A OUTPUT VOLTAGE OUTPUT CURRENT 3.9 3.9 3.9 3.9 2.9 3.1 3.3 3.5 3.7 3.9 Output Current [A] Output Voltage [V] Time [ms] f = 300kHz / VOUT = 3.3V / VFM<=>PWM VIN = 12V / 1A <-> 3A OUTPUT VOLTAGE OUTPUT CURRENT fosc = 1000kHz / VOUT = 3.3V / VFM <=> PWM VIN = 12V / IOUT = 0A -> 1A 3.1 3.3 3.5 3.7 0 0.02 0.04 0.06 0.08 time [ms] Output Voltage [V] Output Current [A] Output Voltage Output Current fosc = 1000kHz / VOUT = 3.3V / VFM <=> PWM VIN = 12V / IOUT = 1A -> 0A 3.3 3.5 3.7 0 0.1 0.2 0.3 0.4 time [s] Output Voltage [V] Output Current [A] Output Voltage Output Current

NO.EY-299-200624 fosc = 1000 kHz fosc = 2000 kHz fosc = 1000kHz / VOUT = 3.3V / VFM <=> PWM VIN = 12V / IOUT = 1A -> 3A 3.2 3.3 3.4 3.5 3.6 0 0.04 0.08 0.12 0.16 time [ms] Output Voltage [V] 1.5 Output Current [A] Output Voltage Output Current fosc = 1000kHz / VOUT = 3.3V / VFM <=> PWM VIN = 12V / IOUT = 3A -> 1A 3.3 3.4 3.5 3.6 0 0.04 0.08 0.12 0.16 time [ms] Output Voltage [V] 1.5 Output Current [A] Output Voltage Output Current fosc = 2000kHz / VOUT = 5.0V / VFM <=> PWM VIN = 12V / IOUT = 0A -> 1A 4.9 5.1 5.2 0 0.04 0.08 0.12 0.16 time [ms] Output Voltage [V] Output Current [A] Output Voltage Output Current fosc = 2000kHz / VOUT = 5.0V / VFM <=> PWM VIN = 12V / IOUT = 1A -> 0A 5.1 5.2 0 0.1 0.2 0.3 0.4 time [s] Output Voltage [V] Output Current [A] Output Voltage Output Current fosc = 2000kHz / VOUT = 5.0V / VFM <=> PWM VIN = 12V / IOUT = 1A -> 3A 4.75 5.25 5.5 0 0.02 0.04 0.06 0.08 time [ms] Output Voltage [V] 1.5 Output Current [A] Output Voltage Output Current fosc = 2000kHz / VOUT = 5.0V / VFM <=> PWM VIN = 12V / IOUT = 3A -> 1A 5.25 5.5 0 0.02 0.04 0.06 0.08 time [ms] Output Voltage [V] 1.5 Output Current [A] Output Voltage Output Current

NO.EY-299-200624 21) Output Current Vs. Output Voltage fosc = 300 kHz fosc = 1000 kHz fosc = 2000 kHz fosc = 300kHz / VOUT = 3.3V VIN = 12V 3.1 3.15 3.2 3.25 3.3 3.35 3.4 3.45 3.5 0 1000 2000 3000 4000 Output Current [mA] Output Voltage [V] 12V VFM<->PWM 12V PWM ( Ta = 25°C) fosc = 1000kHz / VOUT = 3.3V VIN = 12V 3.1 3.15 3.2 3.25 3.3 3.35 3.4 3.45 3.5 0 1000 2000 3000 4000 Output Current [mA] Output Voltage [V] 12V VFM<->PWM 12V PWM ( Ta = 25°C) fosc = 2000kHz / VOUT = 5.0V VIN = 12V 4.7 4.8 4.9 5.1 5.2 5.3 0 1000 2000 3000 4000 Output Current [mA] Output Voltage [V] 12V VFM<->PWM 12V PWM ( Ta = 25°C)

NO.EY-299-200624 22) Input Transient Response fosc = 300 kHz fosc = 1000 kHz fosc = 2000 kHz fosc = 300kHz / VOUT = 3.3V / VFM <=> PWM VIN = 8V <-> 16V / IOUT = 0.1A 3.3 3.5 3.7 3.9 0 2 4 6 8 time [ms] Output Voltage [V] Input Voltage [V] Input Voltage Output Voltage fosc = 300kHz / VOUT = 3.3V / VFM <=> PWM VIN = 8V <-> 16V / IOUT = 1.5A 3.05 3.1 3.15 3.2 3.25 3.3 3.35 3.4 3.45 0 2 4 6 8 time [ms] Output Voltage [V] Input Voltage [V] Input Voltage Output Voltage fosc = 1000kHz / VOUT = 3.3V / VFM <=> PWM VIN = 8V <-> 16V / IOUT = 0.1A 3.3 3.5 3.7 3.9 0 2 4 6 8 time [ms] Output Voltage [V] Input Voltage [V] Input Voltage Output Voltage fosc = 1000kHz / VOUT = 3.3V / VFM <=> PWM VIN = 8V <-> 16V / IOUT = 1.5A 3.25 3.3 3.35 3.4 3.45 0 2 4 6 8 time [ms] Output Voltage [V] Input Voltage [V] Input Voltage Output Voltage fosc = 2000kHz / VOUT = 5.0V / VFM <=> PWM VIN = 8V <-> 16V / IOUT = 0.1A 5.2 5.4 5.6 0 2 4 6 8 time [ms] Output Voltage [V] Input Voltage [V] Input Voltage Output Voltage fosc = 2000kHz / VOUT = 5.0V / VFM <=> PWM VIN = 8V <-> 16V / IOUT = 1.5A 4.95 5.05 5.1 0 2 4 6 8 time [ms] Output Voltage [V] Input Voltage [V] Input Voltage Output Voltage

NO.EY-299-200624 23) Input Voltage Vs. Output Voltage fosc = 300 kHz fosc = 1000 kHz fosc = 2000 kHz fosc = 300kHz / VOUT = 3.3V / VFM <=> PWM 3.2 3.22 3.24 3.26 3.28 3.3 3.32 3.34 3.36 3.38 3.4 0 10 20 30 Input Voltage [V] Output Voltage [V] 0mA 1mA 10mA 100mA ( IOUT ) fosc = 300kHz / VOUT = 3.3V / PWM 3.2 3.22 3.24 3.26 3.28 3.3 3.32 3.34 3.36 3.38 3.4 0 10 20 30 Input Voltage [V] Output Voltage [V] 0mA 1mA 10mA 100mA ( IOUT ) fosc = 1000kHz / VOUT = 3.3V / VFM <=> PWM 3.2 3.22 3.24 3.26 3.28 3.3 3.32 3.34 3.36 3.38 3.4 0 10 20 30 Input Voltage [V] Output Voltage [V] 0mA 1mA 10mA 100mA ( IOUT ) fosc = 1000kHz / VOUT = 3.3V / PWM 3.2 3.22 3.24 3.26 3.28 3.3 3.32 3.34 3.36 3.38 3.4 0 10 20 30 Input Voltage [V] Output Voltage [V] 0mA 1mA 10mA 100mA ( IOUT ) fosc = 2000kHz / VOUT = 5.0V / VFM <=> PWM 4.7 4.8 4.9 5.1 5.2 5.3 5 15 25 35 Input Voltage [V] Output Voltage [V] 0mA 1mA 10mA 100mA ( IOUT ) fosc = 2000kHz / VOUT = 5.0V / PWM 4.9 4.92 4.94 4.96 4.98 5.02 5.04 5.06 5.08 5.1 5 15 25 35 Input Voltage [V] Output Voltage [V] 0mA 1mA 10mA 100mA ( IOUT )

Ver. B i The power dissipation of the package is dependent on PCB material, layout, and environmental conditions. The following measurement conditions are based on JEDEC STD. 51-7. Measurement Conditions Item Measurement Conditions Environment Mounting on Board (Wind Velocity = 0 m/s) Board Material Glass Cloth Epoxy Plastic (Four-Layer Board) Board Dimensions 76.2 mm × 114.3 mm × 0.8 mm Copper Ratio Outer Layer (First Layer): Less than 95% of 50 mm Square Inner Layers (Second and Third Layers): Approx. 100% of 50 mm Square Outer Layer (Fourth Layer): Approx. 100% of 50 mm Square Through-holes φ 0.3 mm × 21 pcs Measurement Result (Ta = 25°C, Tjmax = 150°C) Item Measurement Result Power Dissipation 3900 mW Thermal Resistance (θja) θja = 32°C/W Thermal Characterization Parameter (ψjt) ψjt = 8°C/W θja: Junction-to-Ambient Thermal Resistance ψjt: Junction-to-Top Thermal Characterization Parameter Power Dissipation vs. Ambient Temperature Measurement Board Pattern 500 1000 1500 2000 2500 3000 3500 4000 0 25 50 75 100 125 150 Power Dissipation PD (mW) Ambient Temperature (°C) 3900

PACKAGE DIMENSIONS HSOP-18 i Ver. A

1. T he products and the product specifications described in this document are subject to change or discontinuation of production without notice for reasons such as improvement. Therefore, before deciding to use the products, please refer to our sales representatives for the latest information thereon. 2. The materials in this document may not be copied or otherwise reproduced in whole or in part without the prior written consent of us. 3. This product and any technical information relating thereto are subject to complementary export controls (so- called KNOW controls) under the Foreign Exchange and Foreign Trade Law, and related politics ministerial ordinance of the law. (Note that the complementary export controls are inapplicable to any application-specific products, except rockets and pilotless aircraft, that are insusceptible to design or program changes.) Accordingly, when exporting or carrying abroad this product, follow the Foreign Exchange and Foreign Trade Control Law and its related regulations with respect to the complementary export controls. 4. The technical information described in this document shows typical characteristics and example application circuits for the products. The release of such information is not to be construed as a warranty of or a grant of license under our or any third party's intellectual property rights or any other rights. 5. The products listed in this document are intended and designed for use as general electronic components in standard applications (office equipment, telecommunication equipment, measuring instruments, consumer electronic products, amusement equipment etc.). Those customers intending to use a product in an application requiring extreme quality and reliability, for example, in a highly specific application where the failure or misoperation of the product could result in human injury or death should first contact us.

• Aerospace Equipment
• Equipment Used in the Deep Sea
• Power Generator Control Equipment (nuclear, steam, hydraulic, etc.)
• Life Maintenance Medical Equipment
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• Vehicle Control Equipment (automotive, airplane, railroad, ship, etc.)
• Various Safety Devices
• Traffic control system
• Combustion equipment In case your company desires to use this product for any applications other than general electronic equipment mentioned above, make sure to contact our company in advance. Note that the important requirements mentioned in this section are not applicable to cases where operation requirements such as application conditions are confirmed by our company in writing after consultation with your company. 6. We are making our continuous effort to improve the quality and reliability of our products, but semiconductor products are likely to fail with certain probability. In order to prevent any injury to persons or damages to property resulting from such failure, customers should be careful enough to incorporate safety measures in their design, such as redundancy feature, fire containment feature and fail-safe feature. We do not assume any liability or responsibility for any loss or damage arising from misuse or inappropriate use of the products. 7. The products have been designed and tested to function within controlled environmental conditions. Do not use products under conditions that deviate from methods or applications specified in this datasheet. Failure to employ the products in the proper applications can lead to deterioration, destruction or failure of the products. We shall not be responsible for any bodily injury, fires or accident, property damage or any consequential damages resulting from misuse or misapplication of the products. 8. Quality Warranty 8-1. Quality Warranty Period In the case of a product purchased through an authorized distributor or directly from us, the warranty period for this product shall be one (1) year after delivery to your company. For defective products that occurred during this period, we will take the quality warranty measures described in section 8-2. However, if there is an agreement on the warranty period in the basic transaction agreement, quality assurance agreement, delivery specifications, etc., it shall be followed. 8-2. Quality Warranty Remedies When it has been proved defective due to manufacturing factors as a result of defect analysis by us, we will either deliver a substitute for the defective product or refund the purchase price of the defective product. Note that such delivery or refund is sole and exclusive remedies to your company for the defective product. 8-3. Remedies after Quality Warranty Period With respect to any defect of this product found after the quality warranty period, the defect will be analyzed by us. On the basis of the defect analysis results, the scope and amounts of damage shall be determined by mutual agreement of both parties. Then we will deal with upper limit in Section 8-2. This provision is not intended to limit any legal rights of your company. 9. Anti-radiation design is not implemented in the products described in this document. 10. The X-ray exposure can influence functions and characteristics of the products. Confirm the product functions and characteristics in the evaluation stage. 11. WLCSP products should be used in light shielded environments. The light exposure can influence functions and characteristics of the products under operation or storage. 12. Warning for handling Gallium and Arsenic (GaAs) products (Applying to GaAs MMIC, Photo Reflector). These products use Gallium (Ga) and Arsenic (As) which are specified as poisonous chemicals by law. For the prevention of a hazard, do not burn, destroy, or process chemically to make them as gas or power. When the product is disposed of, please follow the related regulation and do not mix this with general industrial waste or household waste. 13. Please contact our sales representatives should you have any questions or comments concerning the products or the technical information. Official website https://www.nisshinbo-microdevices.co.jp/en/ Purchase information https://www.nisshinbo-microdevices.co.jp/en/buy/