TPA4860D

TPA4860 TI | Alldatasheet

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1-W MONO AUDIO POWER AMPLIFIER SLOS164A – SEPTEMBER 1996 – REVISED MARCH 2000 1POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 /C00681-W BTL Output (5 V, 0.2 % THD+N) /C0068 3.3-V and 5-V Operation /C0068No Output Coupling Capacitors Required /C0068Shutdown Control (IDD = 0.6 mA) /C0068Headphone Interface Logic /C0068Uncompensated Gains of 2 to 20 (BTL Mode) /C0068Surface-Mount Packaging /C0068Thermal and Short-Circuit Protection /C0068High Power Supply Rejection (56-dB at 1 kHz) /C0068LM4860 Drop-In Compatible

description

The TPA4860 is a bridge-tied load (BTL) audio power amplifier capable of delivering 1 W of continuous average power into an 8-W load at 0.4 % THD+N from a 5-V power supply in voiceband frequencies (f < 5 kHz). A BTL configuration eliminates the need for external coupling capacitors on the output in most applications. Gain is externally configured by means of two resistors and does not require compensation for settings of 2 to 20. Features of this amplifier are a shutdown function for power-sensitive applications as well as headphone interface logic that mutes the output when the speaker drive is not required. Internal thermal and short-circuit protection increases device reliability. It also includes headphone interface logic circuitry to facilitate headphone applications. The amplifier is available in a 16-pin SOIC surface-mount package that reduces board space and facilitates automated assembly. typical application circuit Audio Input Bias Control VDD 1 W 1, 4, 8, 9, 16 VO 1 VO 2 VDD

11 GAIN

IN– BYPASS HP-IN1 HP-IN2 HP-SENSE SHUTDOWN VDD /2 C I R I R F VDD R PU Headphone Plug NC C B C S Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet. GND SHUTDOWN HP-SENSE GND BYPASS HP-IN1 HP-IN2 GND GND VO 2 IN+ IN– VDD GAIN VO 1 GND D PACKAGE (TOP VIEW) PRODUCTION DATA information is current as of publication date. Products conform to specifications per the terms of Texas Instruments standard warranty. Production processing does not necessarily include testing of all parameters. Copyright  2000, Texas Instruments Incorporated

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(D) –40°C to 85°C TPA4860D absolute maximum ratings over operating free-air temperature range (unless otherwise noted)† † Stresses beyond those listed under “absolute maximum ratings” may cause permanent damage to the device. These are stress ratings only, and functional operation of the device at these or any other conditions beyond those indicated under “recommended operating conditions” is not implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability. DISSIPATION RATING TABLE PACKAGE TA ≤ 25°C DERATING FACTOR TA = 70°C TA = 85°C D 1250 mW 10 mW/°C 800 mW 650 mW recommended operating conditions MIN MAX UNIT ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Supply voltage, VDD ÁÁÁ ÁÁÁ 2.7 ÁÁÁ ÁÁÁ 5.5 ÁÁÁ ÁÁÁ V ÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁ Common mode in put voltage VIC ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ VDD = 3.3 V ÁÁÁ ÁÁÁ 1.25 ÁÁÁ ÁÁÁ 2.7 ÁÁÁ ÁÁÁ V ÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁ Common -mode input voltage, VIC ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ VDD = 5 V ÁÁÁ ÁÁÁ 1.25 ÁÁÁ ÁÁÁ 4.5 ÁÁÁ ÁÁÁ V ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Operating free-air temperature, TA ÁÁÁ ÁÁÁ –40 ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ

1-W MONO AUDIO POWER AMPLIFIER SLOS164A – SEPTEMBER 1996 – REVISED MARCH 2000 3POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 electrical characteristics at specified free-air temperature range, VDD = 3.3 V (unless otherwise noted) PARAMETER TEST CONDITIONS TPA4860 UNITPARAMETER TEST CONDITIONS MIN TYP MAX UNIT ÁÁÁ ÁÁÁ VOO ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Output offset voltage (measured differentially) ÁÁÁÁÁÁ ÁÁÁÁÁÁ See Note 1 ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ mV ÁÁÁ ÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Supply ripple rejection ratio ÁÁÁÁÁÁ ÁÁÁÁÁÁ VDD = 3.2 V to 3.4 V ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ dB ÁÁÁ ÁÁÁ IDD ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Quiescent current ÁÁÁÁÁÁ ÁÁÁÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ 2.5 ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ mA ÁÁÁ ÁÁÁ IDD(M)ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Quiescent current, mute mode ÁÁÁÁÁÁ ÁÁÁÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ 750 ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ mA ÁÁÁ IDD(SD) ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Quiescent current, shutdown mode ÁÁÁÁÁÁ ÁÁÁ ÁÁÁ 0.6 ÁÁÁ ÁÁÁ mA ÁÁÁ ÁÁÁ VIH ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ High-level input voltage (HP-IN) ÁÁÁÁÁÁ ÁÁÁÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ 1.7 ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ V ÁÁÁ ÁÁÁ VIL ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Low-level input voltage (HP-IN) ÁÁÁÁÁÁ ÁÁÁÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ 1.7 ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ V ÁÁÁ ÁÁÁ VOH ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ High-level output voltage (HP-SENSE) ÁÁÁÁÁÁ ÁÁÁÁÁÁ IO = 100 mA ÁÁÁ ÁÁÁ 2.5 ÁÁÁ ÁÁÁ 2.8 ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ V ÁÁÁ ÁÁÁ VOL ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Low-level output voltage (HP-SENSE) ÁÁÁÁÁÁ ÁÁÁÁÁÁ IO = –100 mA ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ 0.2 ÁÁÁ ÁÁÁ 0.8 ÁÁÁ ÁÁÁ V NOTE 1: At 3 V < VDD < 5 V the dc output voltage is approximately VDD /2. operating characteristics, VDD = 3.3 V, TA = 25°C, RL = 8 W PARAMETER TEST CONDITIONS TPA4860 UNITPARAMETER TEST CONDITIONS MIN TYP MAX UNIT ÁÁÁ Á Á Á ÁÁÁ PO ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Á ÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Á ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Outputpower see Note 2 ÁÁÁÁÁ Á ÁÁÁ Á ÁÁÁÁÁ THD = 0.2%, AV = 2 ÁÁÁÁ Á ÁÁ Á ÁÁÁÁ f = 1 kHz, ÁÁÁ Á Á Á ÁÁÁ ÁÁÁ Á Á Á ÁÁÁ 350 ÁÁÁ Á Á Á ÁÁÁ ÁÁÁ Á Á Á ÁÁÁ mW ÁÁÁ Á Á Á ÁÁÁ PO ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Á ÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Á ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ O utput pow er, see Note 2 ÁÁÁÁÁ Á ÁÁÁ Á ÁÁÁÁÁ THD = 2%, AV = 2 ÁÁÁÁ Á ÁÁ Á ÁÁÁÁ f = 1 kHz, ÁÁÁ Á Á Á ÁÁÁ ÁÁÁ Á Á Á ÁÁÁ 500 ÁÁÁ Á Á Á ÁÁÁ ÁÁÁ Á Á Á ÁÁÁ mW ÁÁÁ BOM ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Maximum output power bandwidth ÁÁÁÁÁ Gain = 10, ÁÁÁÁ THD = 2% ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ kHz ÁÁÁ ÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Unity-gain bandwidth ÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁ Open Loop ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ 1.5 ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ MHz ÁÁÁ ÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁ Supply ripple rejection ratio ÁÁÁÁÁ ÁÁÁÁÁ BTL ÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁ f = 1 kHz ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ dB ÁÁÁ ÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁ Supply ripple rejection ratio ÁÁÁÁÁ ÁÁÁÁÁ SE ÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁ f = 1 kHz ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ dB ÁÁÁ ÁÁÁ Vn ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Noise output voltage, see Note 3 ÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁ Gain = 2 ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ mV NOTES: 2. Output power is measured at the output terminals of the device. 3. Noise voltage is measured in a bandwidth of 20 Hz to 20 kHz.

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electrical characteristics at specified free-air temperature range, VDD = 5 V (unless otherwise noted) PARAMETER TEST CONDITIONS TPA4860 UNITPARAMETER TEST CONDITIONS MIN TYP MAX UNIT ÁÁÁÁ ÁÁÁÁ VOO ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Output offset voltage ÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁ See Note 1 ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ mV ÁÁÁÁ ÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Supply ripple rejection ratio ÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁ VDD = 4.9 V to 5.1 V ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ dB ÁÁÁÁ ÁÁÁÁ IDD ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Supply current ÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ 3.5 ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ mA ÁÁÁÁ ÁÁÁÁ IDD(M) ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Supply current, mute ÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ 750 ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ mA ÁÁÁÁ IDD(SD) ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Supply current, shutdown ÁÁÁÁÁÁÁ ÁÁÁ ÁÁÁ 0.6 ÁÁÁ ÁÁÁ mA ÁÁÁÁ ÁÁÁÁ VIH ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ High-level input voltage (HP-IN) ÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ 2.5 ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ V ÁÁÁÁ ÁÁÁÁ VIL ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Low-level input voltage (HP-IN) ÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ 2.5 ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ V ÁÁÁÁ ÁÁÁÁ VOH ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ High-level output voltage (HP-SENSE) ÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁ IO = 500 mA ÁÁÁ ÁÁÁ 2.5 ÁÁÁ ÁÁÁ 2.8 ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ V ÁÁÁÁ ÁÁÁÁ VOL ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Low-level output voltage (HP-SENSE) ÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁ IO = –500 mA ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ 0.2 ÁÁÁ ÁÁÁ 0.8 ÁÁÁ ÁÁÁ V NOTE 1: At 3 V < VDD < 5 V the dc output voltage is approximately VDD /2. operating characteristic, VDD = 5 V, TA = 25°C, RL = 8 W PARAMETER TEST CONDITIONS TPA4860 UNITPARAMETER TEST CONDITIONS MIN TYP MAX UNIT ÁÁÁÁ Á ÁÁ Á ÁÁÁÁ PO ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Á ÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Á ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Outputpower see Note 2 ÁÁÁÁ Á ÁÁ Á ÁÁÁÁ THD = 0.2%, AV = 2 ÁÁÁÁÁ Á ÁÁÁ Á ÁÁÁÁÁ f = 1 kHz, ÁÁÁ Á Á Á ÁÁÁ ÁÁÁ Á Á Á ÁÁÁ 1000 ÁÁÁ Á Á Á ÁÁÁ ÁÁÁ Á Á Á ÁÁÁ mW ÁÁÁÁ Á ÁÁ Á ÁÁÁÁ PO ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Á ÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Á ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ O utput pow er, see Note 2 ÁÁÁÁ Á ÁÁ Á ÁÁÁÁ THD = 2%, AV = 2 ÁÁÁÁÁ Á ÁÁÁ Á ÁÁÁÁÁ f = 1 kHz, ÁÁÁ Á Á Á ÁÁÁ ÁÁÁ Á Á Á ÁÁÁ 1100 ÁÁÁ Á Á Á ÁÁÁ ÁÁÁ Á Á Á ÁÁÁ mW ÁÁÁÁ BOM ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Maximum output power bandwidth ÁÁÁÁ Gain = 10, ÁÁÁÁÁ THD = 2% ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ kHz ÁÁÁÁ ÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Unity-gain bandwidth ÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁ Open Loop ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ 1.5 ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ MHz ÁÁÁÁ ÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁ Supply ripple rejection ratio ÁÁÁÁÁ ÁÁÁÁÁ BTL ÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁ f = 1 kHz ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ dB ÁÁÁÁ ÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁ Supply ripple rejection ratio ÁÁÁÁÁ ÁÁÁÁÁ SE ÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁ f = 1 kHz ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ dB ÁÁÁÁ ÁÁÁÁ Vn ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Noise output voltage, see Note 3 ÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁ Gain = 2 ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ mV NOTES: 2. Output power is measured at the output terminals of the device. 3. Noise voltage is measured in a bandwidth of 20 Hz to 20 kHz.

1-W MONO AUDIO POWER AMPLIFIER SLOS164A – SEPTEMBER 1996 – REVISED MARCH 2000 5POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 TYPICAL CHARACTERISTICS Table of Graphs ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁ ÁÁÁÁ FIGURE ÁÁÁÁ ÁÁÁÁ VOO ÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁ Output offset voltage ÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁ Distribution ÁÁÁÁ ÁÁÁÁ 1,2 ÁÁÁÁ ÁÁÁÁ IDD ÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁ Supply current distribution ÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁ vs Free-air temperature ÁÁÁÁ ÁÁÁÁ 3,4 ÁÁÁÁ Á ÁÁ Á ÁÁÁÁ THD+N ÁÁÁÁÁÁÁÁÁÁÁ Á ÁÁÁÁÁÁÁÁÁ Á ÁÁÁÁÁÁÁÁÁÁÁ Total harmonic distortion plus noise ÁÁÁÁÁÁÁ Á ÁÁÁÁÁ Á ÁÁÁÁÁÁÁ vs Frequency ÁÁÁÁ Á ÁÁ Á ÁÁÁÁ 5,6,7,8,9, 10,11,15, 16,17,18 ÁÁÁÁ Á ÁÁ Á ÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁ Á ÁÁÁÁÁÁÁÁÁ Á ÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁ Á ÁÁÁÁÁ Á ÁÁÁÁÁÁÁ vs Output power ÁÁÁÁ Á ÁÁ Á ÁÁÁÁ 12,13,14, 19,20,21 ÁÁÁÁ ÁÁÁÁ IDD ÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁ Supply current ÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁ vs Supply voltage ÁÁÁÁ ÁÁÁÁ ÁÁÁÁ Vn ÁÁÁÁÁÁÁÁÁÁÁ Output noise voltage ÁÁÁÁÁÁÁ vs Frequency ÁÁÁÁ 23,24 ÁÁÁÁ ÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁ Maximum package power dissipation ÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁ vs Free-air temperature ÁÁÁÁ ÁÁÁÁ ÁÁÁÁ ÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁ Power dissipation ÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁ vs Output power ÁÁÁÁ ÁÁÁÁ 26,27 ÁÁÁÁ ÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁ Maximum output power ÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁ vs Free-air temperature ÁÁÁÁ ÁÁÁÁ ÁÁÁÁ ÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁ Outputpower ÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁ vs Load Resistance ÁÁÁÁ ÁÁÁÁ ÁÁÁÁ ÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁ O utput pow er ÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁ vs Supply Voltage ÁÁÁÁ ÁÁÁÁ ÁÁÁÁ ÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁ Open loop frequency response ÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁ vs Frequency ÁÁÁÁ ÁÁÁÁ ÁÁÁÁ ÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁ Supply ripple rejection ratio ÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁ vs Frequency ÁÁÁÁ ÁÁÁÁ 32,33

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VOO – Output Offset Voltage – mV VCC = 5 V – 3 – 2 – 101234567 Figure 2 Number of Amplifiers DISTRIBUTION OF TPA4860 OUTPUT OFFSET VOLTAGE VOO – Output Offset Voltage – mV –3 –2 –1 0 1 2 3 4 5 6 7 VCC = 3.3 V Figure 3 – Supply Current – mA SUPPLY CURRENT DISTRIBUTION vs FREE-AIR TEMPERATURE 3.5 TA – Free-Air Temperature –°C –20 25 2.5 1.5 0.5 VCC = 5 V IDD 4.5 Typical Figure 4 – Supply Current – mA SUPPLY CURRENT DISTRIBUTION vs FREE-AIR TEMPERATURE 3.5 TA – Free-Air Temperature –°C –20 25 2.5 1.5 0.5 VCC = 3.3 V IDD Typical

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TOTAL HARMONIC DISTORTION PLUS NOISE vs FREQUENCY 0.1 0.01 100 1 k 10 k 20 k f – Frequency – Hz VDD = 5 V PO = 0.5 W AV = –10 V/V R L = 8 W C B = 0.1 mF C B = 1 mF THD+N – Total Harmonic Distortion Plus Noise – % Figure 10 TOTAL HARMONIC DISTORTION PLUS NOISE vs FREQUENCY 0.1 0.01 100 1 k 10 k 20 k f – Frequency – Hz THD+N – Total Harmonic Distortion Plus Noise – % VDD = 5 V PO = 0.5 W AV = –20 V/V R L = 8 WC B = 0.1 mF C B = 1 mF Figure 11 TOTAL HARMONIC DISTORTION PLUS NOISE vs FREQUENCY 0.1 0.01 100 1 k 10 k 20 k f – Frequency – Hz THD+N – Total Harmonic Distortion Plus Noise – % VDD = 5 V AV = –10 V/V Single Ended R L = 8 W PO = 250 mW R L = 32 W PO = 60 mW Figure 12 TOTAL HARMONIC DISTORTION PLUS NOISE vs OUTPUT POWER 0.02 0.1 0.01 0.1 1 PO – Output Power – W THD+N – Total Harmonic Distortion Plus Noise – % VDD = 5 V AV = –2 V/V R L = 8 W f = 20 Hz C B = 0.1 mF C B = 1 mF

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TOTAL HARMONIC DISTORTION PLUS NOISE vs FREQUENCY 0.1 0.01 100 1 k 10 k 20 k f – Frequency – Hz THD+N – Total Harmonic Distortion Plus Noise – % VDD = 3.3 V PO = 350 mW R L = 8 W AV = –20 V/V C B = 1 mF C B = 0.1 mF Figure 18 TOTAL HARMONIC DISTORTION PLUS NOISE vs FREQUENCY 0.1 0.01 100 1 k 10 k 20 k f – Frequency – Hz THD+N – Total Harmonic Distortion Plus Noise – % VDD = 3.3 V AV = –10 V/V Single Ended R L = 32 W PO = 60 mW R L = 8 W PO = 250 mW Figure 19 TOTAL HARMONIC DISTORTION PLUS NOISE vs OUTPUT POWER 0.02 0.1 0.01 0.1 1 PO – Output Power – W THD+N – Total Harmonic Distortion Plus Noise – % VDD = 3.3 V AV = –2 V/V R L = 8 W f = 20 Hz C B = 0.1 mF C B = 1.0 mF Figure 20 TOTAL HARMONIC DISTORTION PLUS NOISE vs OUTPUT POWER 0.02 0.1 0.01 0.1 1 PO – Output Power – W THD+N – Total Harmonic Distortion Plus Noise – % VDD = 3.3 V AV = –2 V/V R L = 8 W f = 1 kHz C B = 0.1 mF

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Maximum Package Power Dissipation – W MAXIMUM PACKAGE POWER DISSIPATION vs FREE-AIR TEMPERATURE –25 1.5 0.5 0 75 175 TA – Free-Air Temperature – °C 25 50 100 125 150 1.25 0.75 0.25 Figure 26 Power Dissipation – W POWER DISSIPATION vs OUTPUT POWER 1.5 0.5 0 0.75 1.75 PO – Output Power – W 0.25 0.5 1 1.25 1.5 VDD = 5 V R L = 4 W R L = 8 W R L = 16 W Figure 27 POWER DISSIPATION vs OUTPUT POWER 0.5 0.25 0 0.75 PO – Output Power – W 0.25 0.5 VDD = 3.3 V R L = 4 W R L = 8 W R L = 16 W 0.75 Power Dissipation – W Figure 28 160 0 0.25 1.50 0.5 0.75 1 R L = 16 W – Free-Air Temperature – PO – Maximum Output Power – W 1.25 R L = 8 W R L = 4 W C°TA 120 100 140 MAXIMUM OUTPUT POWER vs FREE-AIR TEMPERATURE

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SUPPLY RIPPLE REJECTION RATIO vs FREQUENCY 100 –90 –100 1 k 10 k 20 k f – Frequency – Hz C B = 0.1 mF C B = 1 mF –80 –70 –60 –50 –40 –30 –20 –10 VDD = 5 V R L = 8 W Single Ended Figure 33 Supply Ripple Rejection Ratio – dB

APPLICATION INFORMATION

bridged-tied load versus single-ended mode Figure 34 shows a linear audio power amplifier (APA) in a bridge tied load (BTL) configuration. A BTL amplifier actually consists of two linear amplifiers driving both ends of the load. There are several potential benefits to this differential drive configuration but initially let us consider power to the load. The differential drive to the speaker means that as one side is slewing up the other side is slewing down and vice versa. This in effect doubles the voltage swing on the load as compared to a ground referenced load. Plugging twice the voltage into the power equation, where voltage is squared, yields 4 times the output power from the same supply rail and load impedance (see equation 1). Power /C0043 V (rms) R L (1) V (rms) /C0043 V O(PP) 22/C0504

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bridged-tied load versus single-ended mode (continued) Increasing power to the load does carry a penalty of increased internal power dissipation. The increased dissipation is understandable considering that the BTL configuration produces 4 times the output power of the SE configuration. Internal dissipation versus output power is discussed further in the thermal considerations section. BTL amplifier efficiency Linear amplifiers are notoriously inefficient. The primary cause of these inefficiencies is voltage drop across the output stage transistors. There are two components of the internal voltage drop. One is the headroom or dc voltage drop that varies inversely to output power. The second component is due to the sinewave nature of the output. The total voltage drop can be calculated by subtracting the RMS value of the output voltage from V DD . The internal voltage drop multiplied by the RMS value of the supply current, IDD rms, determines the internal power dissipation of the amplifier. An easy to use equation to calculate efficiency starts out as being equal to the ratio of power from the power supply to the power delivered to the load. To accurately calculate the RMS values of power in the load and in the amplifier, the current and voltage waveform shapes must first be understood (see Figure 36). V(LRMS) VO IDD IDD(RMS) Figure 36. Voltage and Current Waveforms for BTL Amplifiers shape, whereas in BTL it is a full-wave rectified waveform. This means RMS conversion factors are different. supports the fact that each amplifier in the BTL device only draws current from the supply for half the waveform. The following equations are the basis for calculating amplifier efficiency.

1-W MONO AUDIO POWER AMPLIFIER SLOS164A – SEPTEMBER 1996 – REVISED MARCH 2000 17POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 /C0112R L P SUP /C0043V DD IDD rms /C0043 V DD 2V P /C0112R L Efficiency/C0043 P L P SUP Efficiency of a BTL Configuration/C0043 /C0112V P 2V DD /C0043 /C0112/C0466 P LR L 2 /C0467 1/C03242 2V DD (3) P L /C0043 V Lrms2 R L /C0043 V p 2R L Where: (4) NO TAG employs equation 4 to calculate efficiencies for four different output power levels. Note that the efficiency of the amplifier is quite low for lower power levels and rises sharply as power to the load is increased, resulting in a nearly flat internal power dissipation over the normal operating range. Note that the internal dissipation at full output power is less than in the half power range. Calculating the efficiency for a specific system is the key to proper power supply design. For a stereo 1-W audio system with 8-W loads and a 5-V supply, the maximum draw on the power supply is almost 3.25 W. Table 1. Efficiency vs Output Power in 5-V 8-W BTL Systems † High peak voltages cause the THD to increase. denominator. This indicates that as VDD goes down, efficiency goes up. would be almost 6.5 W. Choose the correct supply voltage and speaker impedance for the application.

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Figure 37 is a schematic diagram of a typical notebook computer application circuit. Audio Input Bias Control VDD = 5 V 1 W Internal Speaker 1, 4, 8, 9, 16 VO 1 VO 2 VDD IN– BYPASS HP-IN1 HP-IN2 HP-SENSE SHUTDOWN VDD /2 C I R I R F VDD R PU Headphone Plug NC C F 50 kW 50 kW 46 kW 46 kWC B C S Figure 37. TPA4860 Typical Notebook Computer Application Circuit The gain for the TPA4860 is set by resistors RF and RI according to equation 5. amplifier be set between 5 kW and 20 kW . The effective impedance is calculated in equation 6.

1-W MONO AUDIO POWER AMPLIFIER SLOS164A – SEPTEMBER 1996 – REVISED MARCH 2000 19POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 gain setting resistors, RF and RI (continued) For high performance applications metal film resistors are recommended because they tend to have lower noise levels than carbon resistors. For values of RF above 50 kW the amplifier tends to become unstable due to a pole formed from RF and the inherent input capacitance of the MOS input structure. For this reason, a small compensation capacitor of approximately 5 pF should be placed in parallel with RF. This, in effect, creates a low pass filter network with the cutoff frequency defined in equation 7. (7)fc(lowpass)/C00431 2/C0112R F C F For example, if RF is 100 kW and Cf is 5 pF then fc is 318 kHz, which is well outside of the audio range. input capacitor, CI In the typical application an input capacitor, CI, is required to allow the amplifier to bias the input signal to the proper dc level for optimum operation. In this case, CI and RI form a high-pass filter with the corner frequency determined in equation 8. (8)fc(highpass)/C00431 2/C0112R IC I The value of CI is important to consider as it directly affects the bass (low frequency) performance of the circuit. Consider the example where RI is 10 kW and the specification calls for a flat bass response down to 40 Hz. Equation 8 is reconfigured as equation 9. (9)C I /C00431 2/C0112R Ifc In this example, CI is 0.40 mF, so one would likely choose a value in the range of 0.47 mF to 1 mF. A further consideration for this capacitor is the leakage path from the input source through the input network (RI, CI) and the feedback resistor (RF) to the load. This leakage current creates a dc offset voltage at the input to the amplifier that reduces useful headroom, especially in high gain applications. For this reason a low-leakage tantalum or ceramic capacitor is the best choice. When polarized capacitors are used, the positive side of the capacitor should face the amplifier input in most applications as the dc level there is held at V DD /2, which is likely higher that the source dc level. Note that it is important to confirm the capacitor polarity in the application. power supply decoupling, CS The TPA4860 is a high-performance CMOS audio amplifier that requires adequate power supply decoupling to ensure the output total harmonic distortion (THD) is as low as possible. Power supply decoupling also prevents oscillations for long lead lengths between the amplifier and the speaker. The optimum decoupling is achieved by using two capacitors of different types that target different types of noise on the power supply leads. For higher frequency transients, spikes, or digital hash on the line, a good low equivalent-series-resistance (ESR) ceramic capacitor, typically 0.1 mF placed as close as possible to the device V DD lead, works best. For filtering lower-frequency noise signals, a larger aluminum electrolytic capacitor of 10 mF or greater placed near the power amplifier is recommended.

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midrail bypass capacitor, CB The midrail bypass capacitor, CB, serves several important functions. During start-up or recovery from shutdown mode, CB determines the rate at which the amplifier starts up. This helps to push the start-up pop noise into the subaudible range (so low it can not be heard). The second function is to reduce noise produced by the power supply caused by coupling into the output drive signal. This noise is from the midrail generation circuit internal to the amplifier. The capacitor is fed from a 25-kW source inside the amplifier. To keep the start-up pop as low as possible, the relationship shown in equation 10 should be maintained. (10) /C0466C B /C003225 kW /C0467 /C01181 /C0466C IR I/C0467 As an example, consider a circuit where CB is 0.1 mF, CI is 0.22 mF and RI is 10 kW . Inserting these values into the equation 9 we get: 400 ≤ 454 which satisfies the rule. Bypass capacitor, CB, values of 0.1 mF to 1 mF ceramic or tantalum low-ESR capacitors are recommended for the best THD and noise performance. single-ended operation Figure 38 is a schematic diagram of the recommended SE configuration. In SE mode configurations, the load should be driven from the primary amplifier output (OUT1, terminal 10). Audio Input VDD = 5 V 250-mW External Speaker VO 1 VO 2 VDD IN– BYPASS VDD /2 C I R I R F C SE = 0.1 mF R SE = 50 W C C C B C S Figure 38. Singled-Ended Mode mirror the voltage swing on the load, the factor of 2 is not included. to ground. It is important to avoid oscillation of the inverting output to minimize noise and power dissipation.

1-W MONO AUDIO POWER AMPLIFIER SLOS164A – SEPTEMBER 1996 – REVISED MARCH 2000 21POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 single-ended operation (continued) The output coupling capacitor required in single-supply SE mode also places additional constraints on the selection of other components in the amplifier circuit. The rules described earlier still hold with the addition of the following relationship: (12) /C0466C B /C003225 kW /C0467 /C01181 /C0466C IR I/C0467 /C04161 R LC C output coupling capacitor, CC In the typical single-supply SE configuration, an output coupling capacitor (CC ) is required to block the dc bias at the output of the amplifier thus preventing dc currents in the load. As with the input coupling capacitor, the output coupling capacitor and impedance of the load form a high-pass filter governed by equation 13. (13)f ch i g h/C00431 2/C0112R LC C The main disadvantage, from a performance standpoint, is that the load impedances are typically small, which drives the low-frequency corner higher. Large values of CC are required to pass low frequencies into the load. Consider the example where a CC of 68 mF is chosen and loads vary from 8 W , 32 W, to 47 kW . Table 2 summarizes the frequency response characteristics of each configuration. Table 2. Common Load Impedances vs Low Frequency Output Characteristics in SE Mode

8 W 68 mF 293 Hz

32 W 68 mF 73 Hz

adequate and drive into line level inputs (a home stereo for example) is very good. single-pole single-throw (SPST) switch that makes or breaks a circuit when the headphone plug is inserted. power savings. Pullup resistors in the range from 1 kW to 10 kW are recommended for 5-V and 3.3-V operation.

1-W MONO AUDIO POWER AMPLIFIER SLOS164A – SEPTEMBER 1996 – REVISED MARCH 2000

22 POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

6 HP-IN1

Figure 39. Schematic Diagram of Typical Headphone Sense Application Table 3 details the logic for the mute function of the TPA4860. Table 3. Truth Table for Headphone Sense and Shutdown Functions † Inputs should never be left unconnected. DD <1 mA. SHUTDOWN should never be left unconnected because amplifier operation would be unpredictable. real capacitor behaves like an ideal capacitor.

1-W MONO AUDIO POWER AMPLIFIER SLOS164A – SEPTEMBER 1996 – REVISED MARCH 2000 23POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 0 0.25 1.50 0.5 0.75 1 R L = 16 W – Free-Air Temperature – Maximum Output Power – W 1.25 R L = 8 W R L = 4 W C°TA 120 100 140 VDD = 5 V Figure 40. Free-Air Temperature Versus Maximum Continuous Output Power power into an 8-W load to less than 0.33 W before distortion begins to become significant. approximately two-thirds the supply power for a given output-power level than operation from 5-V supplies. in battery-powered applications.

1-W MONO AUDIO POWER AMPLIFIER SLOS164A – SEPTEMBER 1996 – REVISED MARCH 2000

24 POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

D (R-PDSO-G**) PLASTIC SMALL-OUTLINE PACKAGE

14 PINS SHOWN

0.228 (5,80) 0.244 (6,20) 0.069 (1,75) MAX 0.010 (0,25) 0.004 (0,10) 0.014 (0,35) 0.020 (0,51) A 0.157 (4,00) 0.150 (3,81) 0.044 (1,12) 0.016 (0,40) Seating Plane 0.010 (0,25) PINS ** 0.008 (0,20) NOM A MIN A MAX DIM Gage Plane 0.189 (4,80) (5,00) 0.197 (8,55) (8,75) 0.337 0.344 (9,80) 0.394 (10,00) 0.386 0.004 (0,10) M0.010 (0,25) 0.050 (1,27) 0°–8° NOTES: A. All linear dimensions are in inches (millimeters). B. This drawing is subject to change without notice. C. Body dimensions do not include mold flash or protrusion, not to exceed 0.006 (0,15). D. Falls within JEDEC MS-012

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