TPA2000D2_07 TI | Alldatasheet
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FEATURES
V DD ROSC RINP PV DD GAIN1 ROUTP PGND PW OR PWP P ACKAGE (TOP VIEW)
DESCRIPTION
(Short to Battery, Ground, and Load) Modulation Scheme Optimized to Operate Without a Filter -40 C to C Operating Temperature Range W Into Ω Speakers (THD+N 0.4%) 0.08% THD+N at kHz, Into Ω Load Extremely Efficient Third Generation 5-V Class-D Technology: Low Supply Current (No Filter) mA Low Supply Current (Filter) mA Low Shutdown Current µ A Low Noise Floor µ V RMS Maximum Efficiency Into Ω 65-70% Maximum Efficiency Into Ω 75-85% Internal Gain Settings 8-23.5 dB PSRR -77 dB Integrated Depop Circuitry The TPA2000D2 is the third generation 5-V class-D amplifier from Texas Instruments. Improvements to previous generation devices include: lower supply current, lower noise floor, better efficiency, four different gain settings, smaller packaging, and fewer external components. The most significant advancement with this device is its modulation scheme that allows the amplifier to operate without the output filter. Eliminating the output filter saves the user approximately 30% in system cost and 75% in PCB area. The TPA2000D2 is a monolithic class-D power IC stereo audio amplifier, using the high switching speed of power MOSFET transistors. These transistors reproduce the analog signal through high-frequency switching of the output stage. The TPA2000D2 is configured as a bridge-tied load (BTL) amplifier capable of delivering greater than W of continuous average power into a Ω load at less than THD+N from a 5-V power supply in the high fidelity range (20 Hz to kHz). With W being delivered to a Ω load at kHz, the typical THD+N is less than 0.08%. A BTL configuration eliminates the need for external coupling capacitors on the output. Low supply current of mA makes the device ideal for battery-powered applications. Protection circuitry increases device reliability: thermal, over-current, and under-voltage shutdown. Efficient class-D modulation enables the TPA2000D2 to operate at full power into Ω loads at an ambient temperature of AVAILABLE OPTIONS (1) PACKAGED DEVICE T A TSSOP (PW) TSSOP (PWP) (2) C to C TPA2000D2PW TPA2000D2PWP (1) For the most current package and ordering information, see the Package Option Addendum at the end of this document, or see the TI web site at www.ti.com. (2) The PWP package is available taped and reeled. To order a taped and reeled part, add the suffix R to the part number (e.g., TPA2000D2PWPR). Please be aware that an important notice concerning availability, standard warranty, and use in critical
applications
sheet. PRODUCTION DATA information is current as of publication date. Copyright 2000 2007, Texas Instruments Incorporated Products conform to specifications per the terms of the Texas Instruments standard warranty. Production processing does not necessarily include testing of all parameters.
www.ti.com Gate Drive_ Gate Drive Gain Adjust Gain Adjust Start-Up Protection Logic OC Detect OC Detect Thermal VDD ok Ramp Generator Biases and References Gate Drive_ Gate Drive Gain Adjust Gain Adjust Gain AGNDVDD VDD PV DD RINN ROUTN PGND PV DD ROUTP PGND PV DD LOUTP PGND PV DD LOUTN PGND RINP SHUTDOWN GAIN1 GAIN0 COSC ROSC BYPASS LINP LINN TPA2000D2 SLOS291F MARCH 2000 REVISED MARCH 2007 These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam during storage or handling to prevent electrostatic damage to the MOS gates. Submit Documentation Feedback
www.ti.com ABSOLUTE MAXIMUM RATINGS TPA2000D2 SLOS291F MARCH 2000 REVISED MARCH 2007 TERMINAL FUNCTION TERMINAL I/O NO. AGND Analog ground BYPASS I Tap to voltage divider for internal midsupply bias generator used for analog reference. A capacitor connected to this terminal sets the oscillation frequency in conjunction with ROSC. For COSC I proper operation, connect a 220 pF capacitor from COSC to ground. GAIN0 I Bit of gain control (TTL logic level) GAIN1 I Bit of gain control (TTL logic level) LINN I Left channel negative differential audio input LINP I Left channel positive differential audio input LOUTN O Left channel negative audio output LOUTP O Left channel positive audio output Power ground for left channel H-bridge PGND 12, Power ground for right channel H-bridge Power supply for left channel H-bridge PV DD Power supply for right channel H-bridge RINN I Right channel negative differential audio input RINP I Right channel positive differential audio input A resistor connected to this terminal sets the oscillation frequency in conjunction with COSC. For ROSC I proper operation, connect a 120 k Ω resistor from ROSC to ground. ROUTN O Right channel negative audio output ROUTP O Right channel positive output Places the amplifier in shutdown mode if a TTL logic low is placed on this terminal; normal operation if SHUTDOWN I a TTL logic high is placed on this terminal. V DD Analog power supply over operating free-air temperature range (unless otherwise noted) (1) UNIT V DD PV DD Supply voltage -0.3 V to V V I Input voltage -0.3 V to V DD +0.3 V Continuous total power dissipation See Dissipation Rating Table T A Operating free-air temperature range -40 C to C T J Operating junction temperature range -40 C to 150 C T stg Storage temperature range -65 C to 150 C Lead temperature 1,6 mm (1/16 inch) from case for seconds 260 C (1) Stresses beyond those listed under absolute maximum ratings may cause permanent damage to the device. These are stress ratings only, and functional operation of the device at these or any other conditions beyond those indicated under recommended operating conditions is not implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability. DISSIPATION RATING TABLE T A C DERATING FACTOR T A C T A C PACKAGE POWER RATING ABOVE T A C POWER RATING POWER RATING PW 1.04 W 8.34 mW/ C 0.67 W 0.54 W PWP 2.7 W 21.8 mW/ C 1.7 W 1.4 W Submit Documentation Feedback
www.ti.com RECOMMENDED OPERATING CONDITIONS ELECTRICAL CHARACTERISTICS OPERATING CHARACTERISTICS TPA2000D2 SLOS291F MARCH 2000 REVISED MARCH 2007 MIN TYP MAX UNIT V DD PV DD Supply voltage 4.5 5.5 V V IH High-level input voltage GAIN0, GAIN1, SHUTDOWN V V IL Low-level input voltage GAIN0, GAIN1, SHUTDOWN 0.8 V R OSC Oscillator resistance 120 k Ω C OSC Oscillator capacitance 220 pF f s Switching frequency 200 300 kHz T A Operating free-air temperature -40 C T A V DD PV DD V (unless otherwise noted) PARAMETER TEST CONDITIONS MIN TYP MAX UNIT V OO Output offset voltage (measured differentially) V I V mV PSRR Power supply rejection ratio V DD =PV DD 4.5 V to 5.5 V -77 dB I IH High-level input current V DD =PV DD 5.5 V I V DD PV DD µ A I IL Low-level input current V DD =PV DD 5.5 V I V µ A I DD Supply current No filter (with or without speaker load) mA I DD Supply current With filter, L µ C µ F mA I DD(SD) Supply current, shutdown mode µ A T A V DD PV DD R L Ω Gain dB (unless otherwise noted) PARAMETER TEST CONDITIONS MIN TYP MAX UNIT P O Output power THD 0.1%, f kHz, R L Ω W THD+N Total harmonic distortion plus noise P O f Hz to kHz <0.5% B OM Maximum output power bandwidth THD kHz k SVR Supply ripple rejection ratio f kHz, C (BYPASS) 0.4 µ F -60 dB SNR Signal-to-noise ratio dBV Integrated noise floor Hz to kHz, No input µ V Z I Input impedance >20 k Ω Table Gain Settings AMPLIFIER GAIN INPUT IMPEDANCE (dB) Ω GAIN1 GAIN0 TYP TYP 104 17.5 23.5 Submit Documentation Feedback
www.ti.com TYPICAL CHARACTERISTICS TEST SET-UP FOR GRAPHS OUT± OUT+ TPA2000D2 SLOS291F MARCH 2000 REVISED MARCH 2007 Table of Graphs FIGURE η Efficiency vs Output power FFT at 1.5 W output power vs Frequency vs Output power 5-7 THD+N Total harmonic distortion plus noise vs Frequency Crosstalk vs Frequency Power supply rejection ratio vs Frequency The THD+N measurements shown do not use an LC output filter, but use a low pass filter with a cutoff frequency of kHz so the switching frequency does not dominate the measurement. This is done to ensure that the THD+N measured is just the audible THD+N. The THD+N measurements are shown at the highest gain for worst case. The LC output filter used in the efficiency curves Figure and Figure is shown in Figure µ H (DCR 110 m Ω Part number SCD0703T-220 M-S, Manufacturer GCI) µ F The ferrite filter used in the efficiency curves Figure and Figure is shown in Figure where L is a ferrite bead. ferrite bead (part number 2512067007Y3, manufacturer Fair-Rite) nF Figure Class-D Output Filter Submit Documentation Feedback
www.ti.com TYPICAL CHARACTERISTICS No Filter Ferrite Bead Filter LC Filter Class−AB R L = 8 Ω, Multimedia Speaker VDD = 5 V Efficiency − % PO − Output Power − W 0 0.5 1 1.5 2 Ferrite Bead Filter Notebook Speaker Class−AB Efficiency − % PO − Output Power − W LC Filter R L = 3 Ω, Notebook PC Speaker VDD = 5 V −140 −120 −100 −80 −60 −40 −20 0 24k2k 4k 6k 8k 10k 12k 14k 16k 18k 20k 22k Power − VdB f − Frequency − Hz VDD = 5 V, Gain = 8 dB, f = 1 kHz, P O = 1.5 W, Bandwidth = 20 Hz to 22 kHz,
16386 Frequency Bins
1.5 W OUTPUT POWER vs FREQUENCY Figure Submit Documentation Feedback
www.ti.com 0.01 0.1 10 m THD+N − Total Harmonic Distortion − % 100 m 1 2 3 PO − Output Power − W VDD = 5 V Gain = 23.5 dB R L = 3 Ω 1 kHz 20 kHz 20 Hz 1 kHz 20 kHz 20 Hz VDD = 5 V Gain = 23.5 dB R L = 4 Ω 0.1 0.01 10 m 100 m 1 2 3 THD+N − Total Harmonic Distortion − % PO − Output Power − W 1 kHz 0.1 0.01 10 m 100 m 1 2 THD+N − Total Harmonic Distortion − % PO − Output Power − W VDD = 5 V Gain = 23.5 dB R L = 8 Ω 20 Hz 20 kHz 0.1 0.01 20 100 1 k f − Frequency − Hz 10 k 20 k 0.2 W 0.75 W 1.5 W THD+N − Total Harmonic Distortion − % VDD = 5 V Gain = 23.5 dB R L = 4 Ω TPA2000D2 SLOS291F MARCH 2000 REVISED MARCH 2007 TYPICAL CHARACTERISTICS (continued) TOTAL HARMONIC DISTORTION PLUS NOISE TOTAL HARMONIC DISTORTION PLUS NOISE vs vs OUTPUT POWER OUTPUT POWER Figure Figure TOTAL HARMONIC DISTORTION PLUS NOISE TOTAL HARMONIC DISTORTION PLUS NOISE vs vs OUTPUT POWER FREQUENCY Figure Figure Submit Documentation Feedback
www.ti.com 0.1 0.01 20 100 1 k 20 k f − Frequency − Hz 0.1 W 1 W 0.5 W THD+N − Total Harmonic Distortion − % VDD = 5 V Gain = 23.5 dB R L = 8 Ω f − Frequency − Hz Crosstalk − dB −70 −60 −50 −40 −30 1 10 100 1 k 10 k 100 k Left to Right Right to Left −90 −80 −70 −60 −50 −40 −30 10 100 1 k 10 k 100 k f − Frequency − Hz PSRR − Power Supply Rejection Ratio − dB TPA2000D2 SLOS291F MARCH 2000 REVISED MARCH 2007 TYPICAL CHARACTERISTICS (continued) TOTAL HARMONIC DISTORTION PLUS NOISE vs FREQUENCY Figure CROSSTALK POWER SUPPLY REJECTION RATIO vs vs FREQUENCY FREQUENCY Figure 10. Figure 11. Submit Documentation Feedback
www.ti.com APPLICATION INFORMATION ELIMINATING THE OUTPUT FILTER WITH THE TPA2000D2 EFFECT ON AUDIO TRADITIONAL CLASS-D MODULATION SCHEME O V ±5 V +5 V Current OUT+ Differential Voltage Across Load OUT± TPA2000D2 MODULATION SCHEME TPA2000D2 SLOS291F MARCH 2000 REVISED MARCH 2007 This section focuses on why the user can eliminate the output filter with the TPA2000D2. The class-D amplifier outputs a pulse-width modulated (PWM) square wave, which is the sum of the switching waveform and the amplified input audio signal. The human ear acts as a band-pass filter such that only the frequencies between approximately Hz and kHz are passed. The switching frequency components are much greater than kHz, so the only signal heard is the amplified input audio signal. The traditional class-D modulation scheme, which is used in the TPA005Dxx family, has a differential output where each output is 180 degrees out of phase and changes from ground to the supply voltage, V DD Therefore, the differential prefiltered output varies between positive and negative V DD where filtered 50% duty cycle yields volts across the load. The traditional class-D modulation scheme with voltage and current waveforms is shown in Figure Note that even at an average of volts across the load (50% duty cycle), the current to the load is high causing high loss, thus causing a high supply current. Figure 12. Traditional Class-D Modulation Scheme's Output Voltage and Current Waveforms Into an Inductive Load With No Input The TPA2000D2 uses a modulation scheme that still has each output switching from to the supply voltage. However, OUT+ and OUT- are now in phase with each other with no input. The duty cycle of OUT+ is greater than 50% and OUT- is less than 50% for positive voltages. The duty cycle of OUT+ is less than 50% and OUT- is greater than 50% for negative voltages. The voltage across the load sits at volts throughout most of the switching period greatly reducing the switching current, which reduces any I R losses in the load. Submit Documentation Feedback
www.ti.com 0 V ±5 V +5 V Current OUT+ OUT± Differential Voltage Across Load 0 V ±5 V +5 V Current OUT+ OUT± Differential Voltage Across Load Output = 0 V Output > 0 V EFFICIENCY: WHY YOU MUST USE A FILTER WITH THE TRADITIONAL CLASS-D EFFECTS OF APPLYING A SQUARE WAVE INTO A SPEAKER TPA2000D2 SLOS291F MARCH 2000 REVISED MARCH 2007 APPLICATION INFORMATION (continued) Figure 13. The TPA2000D2 Output Voltage and Current Waveforms Into an Inductive Load MODULATION SCHEME The main reason that the traditional class-D amplifier needs an output filter is that the switching waveform results in maximum current flow. This causes more loss in the load, which causes lower efficiency. The ripple current is large for the traditional modulation scheme because the ripple current is proportional to voltage multiplied by the time at that voltage. The differential voltage swing is V DD and the time at each voltage is half the period for the traditional modulation scheme. An ideal LC filter is needed to store the ripple current from each half cycle for the next half cycle, while any resistance causes power dissipation. The speaker is both resistive and reactive, whereas an LC filter is almost purely reactive. The TPA2000D2 modulation scheme has very little loss in the load without a filter because the pulses are very short and the change in voltage is V DD instead of V DD As the output power increases, the pulses widen making the ripple current larger. Ripple current could be filtered with an LC filter for increased efficiency, but for most needed. An LC filter with a cutoff frequency less than the class-D switching frequency allows the switching current to flow through the filter instead of the load. The filter has less resistance than the speaker, which results in less power dissipated and increased efficiency. Audio specialists have said for years not to apply a square wave to speakers. If the amplitude of the waveform is high enough and the frequency of the square wave is within the bandwidth of the speaker, the square wave could cause the voice coil to jump out of the air gap and/or scar the voice coil. A 250-kHz switching frequency, however, is not significant because the speaker cone movement is proportional to 1/f for frequencies beyond the audio band. Therefore, the amount of cone movement at the switching frequency is very small. However, Submit Documentation Feedback
www.ti.com PSPKR = PSUP ± PSUP THEORETICAL (at max output power) (1) PSPKR = PSUP / POUT ± PSUP THEORETICAL / POUT (at max output power) (2) PSPKR = 1/ηMEASURED ± 1/ηTHEORETICAL (at max output power) (3) WHEN TO USE AN OUTPUT FILTER GAIN SETTING VIA GAIN0 AND GAIN1 INPUTS TPA2000D2 SLOS291F MARCH 2000 REVISED MARCH 2007 APPLICATION INFORMATION (continued) damage could occur to the speaker if the voice coil is not designed to handle the additional power. To size the speaker for added power, the ripple current dissipated in the load needs to be calculated by subtracting the theoretical supplied power, P SUP THEORETICAL from the actual supply power, P SUP at maximum output power, P OUT The switching power dissipated in the speaker is the inverse of the measured efficiency, η MEASURED minus the theoretical efficiency, η THEORETICAL The maximum efficiency of the TPA2000D2 with an Ω load is 85%. Using Equation with the efficiency at maximum power from Figure (78%), we see that there is an additional 106 mW dissipated in the speaker. The added power dissipated in the speaker is not an issue as long as it is taken into account when choosing the speaker. Design the TPA2000D2 without the filter if the traces from amplifier to speaker are short. The TPA2000D2 passed FCC and CE radiated emissions with no shielding with speaker wires inches (20,32 cm) long or less. Notebook PCs and powered speakers where the speaker is in the same enclosure as the amplifier are good a filter. A ferrite bead filter can often be used if the design is failing radiated emissions without a filter, and the frequency sensitive circuit is greater than MHz. This is good for circuits that just have to pass FCC and CE because FCC and CE only test radiated emissions greater than MHz. If choosing a ferrite bead, choose one with high impedance at high frequencies, but very low impedance at low frequencies. Use an output filter if there are low frequency MHz) EMI sensitive circuits and/or there are long leads from amplifier to speaker. The gain of the TPA2000D2 is set by two input terminals, GAIN0 and GAIN1. The gains listed in Table are realized by changing the taps on the input resistors inside the amplifier. This causes the input impedance, Z I to be dependent on the gain setting. The actual gain settings are controlled by ratios of resistors, so the actual gain distribution from part-to-part is quite good. However, the input impedance may shift by 30% due to shifts in the actual resistance of the input resistors. For design purposes, the input network (discussed in the next section) should be designed assuming an input impedance of k Ω which is the absolute minimum input impedance of the TPA2000D2. At the lower gain settings, the input impedance could increase to as high as 115 k Ω Table Gain Settings AMPLIFIER GAIN INPUT IMPEDANCE (dB) Ω GAIN1 GAIN0 TYP TYP 104 17.5 23.5 Submit Documentation Feedback
www.ti.com INPUT RESISTANCE C I IN ZI ZF Input Signal f/C00423 dB/C00431 2/C0112C I ZI (4) INPUT CAPACITOR, C I fc(highpass)/C00431 2/C0112ZIC I −3 dB fc (5) C I /C00431 2/C0112ZIfc (6) C I ≤ CBYP / 10 (7) TPA2000D2 SLOS291F MARCH 2000 REVISED MARCH 2007 Each gain setting is achieved by varying the input resistance of the amplifier, which can range from its smallest value to over times that value. The dB frequency can be calculated using Equation In the typical application an input capacitor, C I is required to allow the amplifier to bias the input signal to the proper dc level for optimum operation. In this case, C I and the input impedance of the amplifier, Z I form a high-pass filter with the corner frequency determined in Equation The value of C I is important, as it directly affects the bass (low frequency) performance of the circuit. Consider the example where Z I is k Ω and the specification calls for a flat bass response down to Hz. Equation is reconfigured as Equation In this example, C I is 0.1 µ so one would likely choose a value in the range of 0.1 µ F to µ If the gain is known and is constant, use Z I from Table to calculate C I A further consideration for this capacitor is the leakage path from the input source through the input network I and the feedback network to the load. This leakage current creates a dc offset voltage at the input to the amplifier that reduces useful headroom, especially in high gain applications. For this reason a low-leakage tantalum or ceramic capacitor is the best choice. When polarized capacitors are used, the positive side of the capacitor should face the amplifier input in most V DD /2, which is likely higher than the source dc level. Note that it is important to confirm the capacitor polarity in the application. C I should be times smaller than the bypass capacitor to reduce clicking and popping noise from power on/off and entering and leaving shutdown. After sizing CI for a given cutoff frequency, size the bypass capacitor up to times that of the input capacitor. Submit Documentation Feedback
www.ti.com SWITCHING FREQUENCY fs /C00436.6 R OSC C OSC (8) POWER SUPPLY DECOUPLING, C S MIDRAIL BYPASS CAPACITOR, C BYP C BYP ≥/charBnZrBnZrBnZrBnZrBnZrBnZrBnZrBnZr10 × CI (9) DIFFERENTIAL INPUT SHUTDOWN MODES TPA2000D2 SLOS291F MARCH 2000 REVISED MARCH 2007 The switching frequency is determined using the values of the components connected to R OSC (pin 18) and C OSC (pin and is calculated with the following equation: The switching frequency was chosen to be centered on 250 kHz. This frequency is the optimum audio fidelity of oversampling and of maximizing efficiency by minimizing the switching losses of the amplifier. The recommended values are a resistance of 120 k Ω and a capacitance of 220 pF. Using these component values, the amplifier operates properly by using tolerance resistors and 10% tolerance capacitors. The tolerance of the components can be changed, as long as the switching frequency remains between 200 kHz and 300 kHz. Within this range, the internal circuitry of the device provides stable operation. The TPA2000D2 is a high-performance CMOS audio amplifier that requires adequate power supply decoupling to ensure the output total harmonic distortion (THD) is as low as possible. Power supply decoupling also prevents oscillations for long lead lengths between the amplifier and the speaker. The optimum decoupling is achieved by using two capacitors of different types that target different types of noise on the power supply leads. For higher frequency transients, spikes, or digital hash on the line, a good low equivalent-series-resistance (ESR) ceramic capacitor, typically 0.1 µ F placed as close as possible to the device V DD lead works best. For filtering lower-frequency noise signals, a larger aluminum electrolytic capacitor of µ F or greater placed near the audio power amplifier is recommended. The midrail bypass capacitor, C BYP is the most critical capacitor and serves several important functions. During start-up or recovery from shutdown mode, C BYP determines the rate at which the amplifier starts up. The second function is to reduce noise produced by the power supply caused by coupling into the output drive signal. This noise is from the midrail generation circuit internal to the amplifier, which appears as degraded PSRR and THD+N. Bypass capacitor, C BYP values of 0.47 µ F to µ F ceramic or tantalum low-ESR capacitors are recommended for the best THD and noise performance. Increasing the bypass capacitor reduces clicking and popping noise from power on/off and entering and leaving shutdown. To have minimal pop, C BYP should be times larger than C I The differential input stage of the amplifier cancels any noise that appears on both input lines of a channel. To use the TPA2000D2 EVM with a differential source, connect the positive lead of the audio source to the RINP (LINP) input and the negative lead from the audio source to the RINN (LINN) input. To use the TPA2000D2 with a single-ended source, ac ground the RINN and LINN inputs through a capacitor and apply the audio single to the RINP and LINP inputs. In a single-ended input application, the RINN and LINN inputs should be ac-grounded at the audio source instead of at the device inputs for best noise performance. The TPA2000D2 employs a shutdown mode of operation designed to reduce supply current, I DD to the absolute minimum level during periods of nonuse for battery-power conservation. The SHUTDOWN input terminal should be held high during normal operation when the amplifier is in use. Pulling SHUTDOWN low causes the outputs to mute and the amplifier to enter a low-current state, I DD(SD) µ SHUTDOWN should never be left unconnected, because amplifier operation would be unpredictable. Submit Documentation Feedback
www.ti.com USING LOW-ESR CAPACITORS EVALUATION CIRCUIT RIGHT AUDIO INPUT+ TO SYSTEM CONTROL TPA2000D2 220 pF C18 LEFT AUDIO INPUT+ C17 LEFT AUDIO OUTPUT+ VDD VDD RIGHT AUDIO OUTPUT ± 120k C19 C20 C210.1 µF 0.1 µF 0.1 µF 0.1 µF 0.1 µF 0.1 µF 1 µF 10 µF 0.1 µF 0.1 µF 0.1 µF SHUTDOWN PGND LOUTN GAIN0 LPVDD LINN AGND COSC RINN RPVDD ROUTN PGND PGND LOUTP BYPASS LPVDD LINP VDD ROSC RINP RPVDD GAIN1 ROUTP PGND 10 10 µF LEFT AUDIO INPUT± RIGHT AUDIO INPUT± VDD VDD GAIN SELECT GAIN SELECT RIGHT AUDIO OUTPUT + LEFT AUDIO OUTPUT± TPA2000D2 SLOS291F MARCH 2000 REVISED MARCH 2007 Low-ESR capacitors are recommended throughout this application section. A real (as opposed to ideal) capacitor can be modeled simply as a resistor in series with an ideal capacitor. The voltage drop across this resistor minimizes the beneficial effects of the capacitor in the circuit. The lower the equivalent value of this resistance the more the real capacitor behaves like an ideal capacitor. Table TPA2000D2 Application Bill of Materials REFERENCE C1-4, C17-21 Capacitor, ceramic chip, 0.1 µ 10%, X7R, V 0805 Kemet C0805C104K5RAC Capacitor, ceramic, 1.0 µ 80%/-20%, Y5V, V 0805 Murata GRM40-Y5V105Z16 C6, Capacitor, ceramic, µ 80%/-20%, Y5V, V 1210 Murata GRM235-Y5V106Z16 Capacitor, ceramic, 220 pF, 10%, XICON, V 0805 Mouser 140-CC501B221K Resistor, chip, 120 k Ω 5%, XICON 0805 Mouser 260-120K IC, TPA2000D2, audio power amplifier, 2-W, pin TI TPA2000D2PWP 2-channel, class-D TSSOP Submit Documentation Feedback
Orderable Device Status(1) Package Type Package Drawing Pins Package Qty Eco Plan(2) Lead/Ball FinishMSL Peak Temp (3) TPA2000D2PW ACTIVE TSSOP PW 24 60 Green (RoHS & no Sb/Br) CU NIPDAU Level-2-260C-1 YEAR TPA2000D2PWG4 ACTIVE TSSOP PW 24 60 Green (RoHS & no Sb/Br) CU NIPDAU Level-2-260C-1 YEAR TPA2000D2PWP ACTIVE HTSSOP PWP 24 60 Green (RoHS & no Sb/Br) CU NIPDAU Level-2-260C-1 YEAR TPA2000D2PWPG4 ACTIVE HTSSOP PWP 24 60 Green (RoHS & no Sb/Br) CU NIPDAU Level-2-260C-1 YEAR TPA2000D2PWPR ACTIVE HTSSOP PWP 24 2000 Green (RoHS & no Sb/Br) CU NIPDAU Level-2-260C-1 YEAR TPA2000D2PWPRG4 ACTIVE HTSSOP PWP 24 2000 Green (RoHS & no Sb/Br) CU NIPDAU Level-2-260C-1 YEAR TPA2000D2PWR ACTIVE TSSOP PW 24 2000 Green (RoHS & no Sb/Br) CU NIPDAU Level-2-260C-1 YEAR TPA2000D2PWRG4 ACTIVE TSSOP PW 24 2000 Green (RoHS & no Sb/Br) CU NIPDAU Level-2-260C-1 YEAR (1)The marketing status values are defined as follows: ACTIVE: Product device recommended for new designs. LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect. NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design. PREVIEW: Device has been announced but is not in production. Samples may or may not be available. OBSOLETE: TI has discontinued the production of the device. (2)Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check http://www.ti.com/productcontentfor the latest availability information and additional product content details. TBD: The Pb-Free/Green conversion plan has not been defined. Pb-Free (RoHS):TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements for all 6 substances, including the requirement that lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes. Pb-Free (RoHS Exempt):This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and package, or 2) lead-based die adhesive used between the die and leadframe. The component is otherwise considered Pb-Free (RoHS compatible) as defined above. Green (RoHS & no Sb/Br):TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame retardants (Br or Sb do not exceed 0.1% by weight in homogeneous material) (3) MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature. Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals. TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for release. In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis. PACKAGE OPTION ADDENDUM www.ti.com 18-Apr-2006 Addendum-Page 1
MTSS001C – JANUARY 1995 – REVISED FEBRUARY 1999 POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 PW (R-PDSO-G**) PLASTIC SMALL-OUTLINE PACKAGE
14 PINS SHOWN
0,65 M0,10 0,10 0,25 0,50 0,75 0,15 NOM Gage Plane 9,80 9,60 7,90 7,70 2016 6,60 6,40 4040064/F 01/97 0,30 6,60 6,20 0,19 4,30 4,50 0,15 A 1,20 MAX 5,10 4,90 3,10 2,90 A MAX A MIN DIM PINS ** 0,05 4,90 5,10 Seating Plane 0°–8° NOTES: A. All linear dimensions are in millimeters. B. This drawing is subject to change without notice. C. Body dimensions do not include mold flash or protrusion not to exceed 0,15. D. Falls within JEDEC MO-153
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