TPA0112PWP

TPA0112 TI | Alldatasheet

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2-W STEREO AUDIO POWER AMPLIFIER WITH FOUR SELECTABLE GAIN SETTINGS SLOS204B – MAY 1999 – REVISED MARCH 2000 1POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 /C0068Compatible With PC 99 Desktop Line-Out Into 10-kW Load /C0068Internal Gain Control, Which Eliminates External Gain-Setting Resistors /C00682-W/Ch Output Power Into 3-W Load /C0068PC-Beep Input /C0068Depop Circuitry /C0068Stereo Input MUX /C0068Fully Differential Input /C0068Low Supply Current and Shutdown Current /C0068Surface-Mount Power Packaging 24-Pin TSSOP PowerPAD 

description

The TPA0112 is a stereo audio power amplifier in a 24-pin TSSOP thermally enhanced package capable of delivering 2 W of continuous RMS power per channel into 3-W loads. This device minimizes the number of external components needed, simplifying the design, and freeing up board space for other features. When driving 1 W into 8-W speakers, the TPA0112 has less than 0.8% THD+N across its specified frequency range. Included within this device is integrated depop circuitry that virtually eliminates transients that cause noise in the speakers. Amplifier gain is internally configured and controlled by way of two terminals (GAIN0 and GAIN1). BTL gain settings of –2, –6, –12, and –24 V/V are provided, while SE gain is always configured as –1 V/V for headphone drive. An internal input MUX allows two sets of stereo inputs to the amplifier. In notebook applications, where internal speakers are driven as BTL and the line outputs (often headphone drive) are required to be SE, the TPA0112 automatically switches into SE mode when the SE/BTL input is activated, and this reduces the gain to –1 V/V. The TPA0112 consumes only 6 mA of supply current during normal operation. A miserly shutdown mode reduces the supply current to less than 150 mA. The PowerPAD package (PWP) delivers a level of thermal performance that was previously achievable only in TO-220-type packages. Thermal impedances of approximately 35°C/W are readily realized in multilayer PCB applications. This allows the TPA0112 to operate at full power into 8-W loads at an ambient temperature of 85°C. Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet. Copyright  2000, Texas Instruments IncorporatedPRODUCTION DATA information is current as of publication date. Products conform to specifications per the terms of Texas Instruments standard warranty. Production processing does not necessarily include testing of all parameters. PWP PACKAGE (TOP VIEW) GND GAIN0 GAIN1 LOUT+ LLINEIN LHPIN PV DD RIN LOUT– LIN BYPASS GND GND RLINEIN SHUTDOWN ROUT+ RHPIN V DD PV DD PCB ENABLE ROUT– SE/BTL PC-BEEP GND PowerPAD is a trademark of Texas Instruments Incorporated.

2-W STEREO AUDIO POWER AMPLIFIER WITH FOUR SELECTABLE GAIN SETTINGS SLOS204B – MAY 1999 – REVISED MARCH 2000

2 POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

R MUX PC- Beep Gain/ MUX Control Depop Circuitry Power Management L MUX RHPIN RLINEIN RIN PC-BEEP GAIN0 GAIN1 SE/BTL LHPIN LLINEIN LIN ROUT– PV DD VDD BYPASS SHUTDOWN GND LOUT+ LOUT– PC ENABLE

2-W STEREO AUDIO POWER AMPLIFIER WITH FOUR SELECTABLE GAIN SETTINGS SLOS204B – MAY 1999 – REVISED MARCH 2000 3POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 AVAILABLE OPTIONS PACKAGED DEVICE TA TSSOP † (PWP) –40°C to 85°C TPA0112PWP † The PWP package is available taped and reeled. To order a taped and reeled part, add the suffix R to the part number (e.g., TPA0112PWPR). Terminal Functions TERMINAL I/O DESCRIPTIONNAME NO. I/O DESCRIPTION BYPASS 11 Tap to voltage divider for internal mid-supply bias generator GAIN0 2 I Bit 0 of gain control GAIN1 3 I Bit 1 of gain control GND 1, 12, 13, 24 Ground connection for circuitry. Connected to the thermal pad. LHPIN 6 I Left channel headphone input, selected when SE/BTL is held high LIN 10 I Common left input for fully differential input. AC ground for single-ended inputs. LLINEIN 5 I Left channel line input, selected when SE/BTL is held low LOUT+ 4 O Left channel positive output in BTL mode and positive output in SE mode LOUT– 9 O Left channel negative output in BTL mode and high-impedance in SE mode PC-BEEP 14 I The input for PC Beep mode. PC-BEEP is enabled when a > 1-V (peak-to-peak) square wave is input to PC-BEEP or PCB ENABLE is high. PCB ENABLE 17 I If this terminal is high, the detection circuitry for PC-BEEP is overridden and passes PC-BEEP through the amplifier, regardless of its amplitude. If PCB ENABLE is floating or low, the amplifier continues to operate normally. PV DD 7, 18 I Power supply for output stage RHPIN 20 I Right channel headphone input, selected when SE/BTL is held high RIN 8 I Common right input for fully differential input. AC ground for single-ended inputs. RLINEIN 23 I Right channel line input, selected when SE/BTL is held low ROUT+ 21 O Right channel positive output in BTL mode and positive output in SE mode ROUT– 16 O Right channel negative output in BTL mode and high-impedance in SE mode SHUTDOWN 22 I Places entire IC in shutdown mode when held low, except PC-BEEP remains active SE/BTL 15 I Input MUX control input. When this terminal is held high, the LHPIN or RHPIN and SE output is selected. When this terminal is held low, the LLINEIN or RLINEIN and BTL output are selected. VDD 19 I Analog VDD input supply. This terminal needs to be isolated from PVDD to achieve highest performance.

2-W STEREO AUDIO POWER AMPLIFIER WITH FOUR SELECTABLE GAIN SETTINGS SLOS204B – MAY 1999 – REVISED MARCH 2000

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absolute maximum ratings over operating free-air temperature range (unless otherwise noted)† † Stresses beyond those listed under “absolute maximum ratings” may cause permanent damage to the device. These are stress ratings only, and functional operation of the device at these or any other conditions beyond those indicated under “recommended operating conditions” is not implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability. DISSIPATION RATING TABLE PACKAGE TA ≤ 25°C DERATING FACTOR TA = 70°C TA = 85°C PWP 2.7 W‡ 21.8 mW/°C 1.7 W 1.4 W ‡ Please see the Texas Instruments document, PowerPAD Thermally Enhanced Package Application Report (literature number SLMA002), for more information on the PowerPAD package. The thermal data was measured on a PCB layout based on the information in the section entitled Texas Instruments Recommended Board for PowerPAD on page 33 of the before mentioned document. recommended operating conditions MIN MAX UNIT ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Supply voltage, VDD ÁÁÁ ÁÁÁ 4.5 ÁÁÁ ÁÁÁ 5.5 ÁÁÁ ÁÁÁ V High level input voltage VIH SE/BTL 4 VHigh-level input voltage, VIH SHUTDOWN 2 V Low level input voltage VIL SE/BTL 3 VLow-level input voltage, VIL SHUTDOWN 0.8 V ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Operating free-air temperature, TA ÁÁÁ ÁÁÁ –40 ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ electrical characteristics at specified free-air temperature, VDD = 5 V, TA = 25°C (unless otherwise noted) PARAMETER TEST CONDITIONS MIN TYP MAX UNIT ÁÁÁÁ ÁÁÁÁ |VOO | ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Output offset voltage (measured differentially) ÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁ VI = 0, AV = 2 ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ mV ÁÁÁÁ ÁÁÁÁ PSRR ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Power supply rejection ratio ÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁ VDD = 4 V to 5 V ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ dB |IIH| High-level input current VDD = 5.5 V, VI = VDD ÁÁÁ Á Á Á ÁÁÁ ÁÁÁ Á Á Á ÁÁÁ ÁÁÁ Á Á Á ÁÁÁ 900 ÁÁÁ Á Á Á ÁÁÁ nA |IIL| Low-level input current VDD = 5.5 V, VI = 0 V ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ 900 ÁÁÁ ÁÁÁ nA ÁÁÁÁ ÁÁÁÁ IDD ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Supply current ÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁ BTL mode ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ mA ÁÁÁÁ ÁÁÁÁ IDD ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Supply current ÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁ SE mode ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ mA ÁÁÁÁ ÁÁÁÁ IDD(SD) ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Supply current, shutdown mode ÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ 150 ÁÁÁ ÁÁÁ 300 ÁÁÁ ÁÁÁ mA

2-W STEREO AUDIO POWER AMPLIFIER WITH FOUR SELECTABLE GAIN SETTINGS SLOS204B – MAY 1999 – REVISED MARCH 2000 5POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 operating characteristics, VDD = 5 V, TA = 25°C, RL = 8 W , Gain = –2 V/V, BTL mode PARAMETER TEST CONDITIONS MIN TYP MAX UNIT ÁÁÁÁ Á ÁÁ Á ÁÁÁÁ PO ÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁ Á ÁÁÁÁÁÁÁÁÁÁÁÁ Output power ÁÁÁÁÁÁ Á ÁÁÁÁ Á ÁÁÁÁÁÁ THD = 1%, R L = 4 W ÁÁÁÁÁÁ Á ÁÁÁÁ Á ÁÁÁÁÁÁ f = 1 kHz, ÁÁÁ Á Á Á ÁÁÁ ÁÁÁ Á Á Á ÁÁÁ 1.9 ÁÁÁ Á Á Á ÁÁÁ ÁÁÁ Á Á Á ÁÁÁ W ÁÁÁÁ ÁÁÁÁ THD + N ÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁ Total harmonic distortion plus noise ÁÁÁÁÁÁ ÁÁÁÁÁÁ PO = 1 W, ÁÁÁÁÁÁ ÁÁÁÁÁÁ f = 20 Hz to 15 kHz ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ 0.75% ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁÁ ÁÁÁÁ BOM ÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁ Maximum output power bandwidth ÁÁÁÁÁÁ ÁÁÁÁÁÁ THD = 5% ÁÁÁÁÁÁ ÁÁÁÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ >15 ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ kHz ÁÁÁÁ ÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁ Supply ripple rejection ratio ÁÁÁÁÁÁ ÁÁÁÁÁÁ f = 1 kHz, C B = 0.47 mF ÁÁÁÁÁÁ ÁÁÁÁÁÁ BTL mode ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ dB SNR Signal-to-noise ratio 105 dB ÁÁÁÁ ÁÁÁÁ V ÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁ Noise output voltage ÁÁÁÁÁÁ ÁÁÁÁÁÁ C B = 0.47 mF, ÁÁÁÁÁÁ ÁÁÁÁÁÁ BTL mode ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ mV RMS ÁÁÁÁ ÁÁÁÁ Vn ÁÁÁÁÁÁÁÁÁÁÁÁ ÁÁÁÁÁÁÁÁÁÁÁÁ Noise output voltage ÁÁÁÁÁÁ ÁÁÁÁÁÁ B m , f = 20 Hz to 20 kHz ÁÁÁÁÁÁ ÁÁÁÁÁÁ SE mode ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ ÁÁÁ mV RMS ZI Input impedance See Table 1 TYPICAL CHARACTERISTICS Table of Graphs FIGURE vs Output power 1, 4–7, 10–13, 16–19, 21 THD+N Total harmonic distortion plus noise vs Frequency 2, 3, 8, 9, 14, 15, 20, 22 vs Output voltage 23 Vn Output noise voltage vs Bandwidth 24 Supply ripple rejection ratio vs Frequency 25, 26 Crosstalk vs Frequency 27–29 Shutdown attenuation vs Frequency 30 SNR Signal-to-noise ratio vs Frequency 31 Closed loop respone 32–35 PO Output power vs Load resistance 36, 37 PD Power dissipation vs Output power 38, 39 PD Pow er dissipation vs Ambient temperature 40

2-W STEREO AUDIO POWER AMPLIFIER WITH FOUR SELECTABLE GAIN SETTINGS SLOS204B – MAY 1999 – REVISED MARCH 2000

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0.1% 0.01% 10% 2.25 2.5 2.75 3 PO – Output Power – W AV = –2 V/V f = 1 kHz BTL THD+N –Total Harmonic Distortion + Noise TOTAL HARMONIC DISTORTION PLUS NOISE vs OUTPUT POWER R L = 8 W R L = 3 W R L = 4 W Figure 2 0.01% 10% 20 100 1k 10k 20k THD+N –Total Harmonic Distortion + Noise f – Frequency – Hz TOTAL HARMONIC DISTORTION PLUS NOISE vs FREQUENCY 0.1% PO = 1.75 W R L = 3 W BTL AV = –6 V/V AV = –24 V/V AV = –2 V/VAV = –12 V/V Figure 3 0.01% 10% 20 100 1k 10k 20k THD+N –Total Harmonic Distortion + Noise f – Frequency – Hz TOTAL HARMONIC DISTORTION PLUS NOISE vs FREQUENCY 0.1% R L = 3 W AV = –2 V/V BTL Po = 1.75 W Po = 0.5 W Po = 1.0 W Figure 4 0.1% 0.01% 0.01 0.1 10% 11 0 f = 20 Hz f = 1 kHz PO – Output Power – W R L = 3 W AV = –2 V/V BTL THD+N –Total Harmonic Distortion + Noise TOTAL HARMONIC DISTORTION PLUS NOISE vs OUTPUT POWER f = 15 kHz

2-W STEREO AUDIO POWER AMPLIFIER WITH FOUR SELECTABLE GAIN SETTINGS SLOS204B – MAY 1999 – REVISED MARCH 2000

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0.01% 10% 20 100 1k 10k 20k THD+N –Total Harmonic Distortion + Noise f – Frequency – Hz TOTAL HARMONIC DISTORTION PLUS NOISE vs FREQUENCY 0.1% R L = 4 W AV = –2 V/V BTL PO = 0.25 W PO = 1.0 W PO = 1.5 W Figure 10 0.1% 0.01% 0.01 0.1 10% 11 0 f = 20 Hz f = 1 kHz PO – Output Power – W R L = 4 W AV = –2 V/V BTL THD+N –Total Harmonic Distortion + Noise TOTAL HARMONIC DISTORTION PLUS NOISE vs OUTPUT POWER f = 15 kHz Figure 11 0.1% 0.01% 0.01 0.1 10% 11 0 f = 20 Hz f = 1 kHz PO – Output Power – W R L = 4 W AV = –6 V/V BTL THD+N –Total Harmonic Distortion + Noise TOTAL HARMONIC DISTORTION PLUS NOISE vs OUTPUT POWER f = 15 kHz Figure 12 0.1% 0.01% 0.01 0.1 10% 11 0 f = 20 Hz f = 1 kHz PO – Output Power – W R L = 4 W AV = –12 V/V BTL THD+N –Total Harmonic Distortion + Noise TOTAL HARMONIC DISTORTION PLUS NOISE vs OUTPUT POWER f = 15 kHz

2-W STEREO AUDIO POWER AMPLIFIER WITH FOUR SELECTABLE GAIN SETTINGS SLOS204B – MAY 1999 – REVISED MARCH 2000

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0.1% 0.01% 0.01 0.1 10% 11 0 f = 20 Hz f = 1 kHz PO – Output Power – W R L = 8 W AV = –6 V/V BTL THD+N –Total Harmonic Distortion + Noise TOTAL HARMONIC DISTORTION PLUS NOISE vs OUTPUT POWER f = 15 kHz Figure 18 0.1% 0.01% 0.01 0.1 10% 11 0 f = 20 Hz f = 1 kHz PO – Output Power – W R L = 8 W AV = –12 V/V BTL THD+N –Total Harmonic Distortion + Noise TOTAL HARMONIC DISTORTION PLUS NOISE vs OUTPUT POWER f = 15 kHz Figure 19 0.1% 0.01% 0.01 0.1 10% 11 0 f = 20 Hz f = 1 kHz PO – Output Power – W R L = 8 W AV = –24 V/V BTL THD+N –Total Harmonic Distortion + Noise TOTAL HARMONIC DISTORTION PLUS NOISE vs OUTPUT POWER f = 15 kHz Figure 20 0.01% 10% 20 100 1k 10k 20k THD+N –Total Harmonic Distortion + Noise f – Frequency – Hz TOTAL HARMONIC DISTORTION PLUS NOISE vs FREQUENCY R L = 32 W AV = –1 V/V SE Po = 75 mW Po = 25 mW Po = 50 mW 0.1%

2-W STEREO AUDIO POWER AMPLIFIER WITH FOUR SELECTABLE GAIN SETTINGS SLOS204B – MAY 1999 – REVISED MARCH 2000

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–120 –40 20 100 1k 10k 20k f – Frequency – Hz SUPPLY RIPPLE REJECTION RATIO vs FREQUENCY –60 –80 –100 R L = 8 W C B = 0.47 mF BTL–20 AV = –24 V/V AV = –2 V/V Supply Ripple Rejection Ratio – dB Figure 26 –120 –40 20 100 1k 10k 20k f – Frequency – Hz SUPPLY RIPPLE REJECTION RATIO vs FREQUENCY –60 –80 –100 R L = 32 W C B = 0.47 mF SE–20 AV = –1 V/V Supply Ripple Rejection Ratio – dB Figure 27 –120 –40 20 100 1k 10k 20k Crosstalk – dB f – Frequency – Hz CROSSTALK vs FREQUENCY –60 –80 –100 PO = 1 W R L = 8 W AV = –2 V/V BTL –20 LEFT TO RIGHT RIGHT TO LEFT Figure 28 –120 –40 20 100 1k 10k 20k Crosstalk – dB f – Frequency – Hz CROSSTALK vs FREQUENCY –60 –80 –100 PO = 1 W R L = 8 W AV =– 24 V/V BTL –20 LEFT TO RIGHT RIGHT TO LEFT

2-W STEREO AUDIO POWER AMPLIFIER WITH FOUR SELECTABLE GAIN SETTINGS SLOS204B – MAY 1999 – REVISED MARCH 2000

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–10 10 100 1k 10k 100k Gain – dB f – Frequency – Hz CLOSED LOOP RESPONSE 2.5 –2.5 7.5 –7.5 360° 270° 180° 90° Phase R L = 8 W AV = –2 V/V BTL Gain Phase Figure 32 –10 10 100 1k 10k 100k Gain – dB f – Frequency – Hz CLOSED LOOP RESPONSE 360° 270° 180° 90° R L = 8 W AV = –6 V/V BTL Gain Phase Phase Figure 33

2-W STEREO AUDIO POWER AMPLIFIER WITH FOUR SELECTABLE GAIN SETTINGS SLOS204B – MAY 1999 – REVISED MARCH 2000

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1.5 0 8 16 24 32 40 2.5 3.5 48 56 64 R L – Load Resistance – W AV = –2 V/V BTL – Output Power – WPO OUTPUT POWER vs LOAD RESISTANCE 1% THD+N 10% THD+N 0.5 Figure 37 750 0 8 16 24 32 40 1000 1250 1500 48 56 64 R L – Load Resistance – W AV = –1 V/V SE – Output Power – mWPO OUTPUT POWER vs LOAD RESISTANCE 1% THD+N 10% THD+N 500 250 Figure 38 0.6 0.4 0.2 – Power Dissipation – W 1.2 POWER DISSIPATION vs OUTPUT POWER 1.4 1.5 2.5 0.8 PO – Output Power – W PD 4 W 8 W f = 1 kHz BTL Each Channel 3 W1.6 1.8 0.5 2 Figure 39 0.1 0.05 0 0.2 – Power Dissipation – W 0.2 0.25 POWER DISSIPATION vs OUTPUT POWER 0.3 0.3 0.8 0.15 PO – Output Power – W PD 8 W

32 W f = 1 kHz

0.35 0.4

2-W STEREO AUDIO POWER AMPLIFIER WITH FOUR SELECTABLE GAIN SETTINGS SLOS204B – MAY 1999 – REVISED MARCH 2000 17POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 TYPICAL CHARACTERISTICS –40 0 – Power Dissipation – W POWER DISSIPATION vs AMBIENT TEMPERATURE 20 160 TA – Ambient Temperature – °C PD –20 100 40 60 80 120 140 Q JA3 Q JA1,2 Q JA4 Q JA1 = 45.9°C/W Q JA2 = 45.2°C/W Q JA3 = 31.2°C/W Q JA4 = 18.6°C/W Figure 40

2-W STEREO AUDIO POWER AMPLIFIER WITH FOUR SELECTABLE GAIN SETTINGS SLOS204B – MAY 1999 – REVISED MARCH 2000

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The thermally enhanced PWP package is based on the 24-pin TSSOP, but includes a thermal pad (see Figure 41) to provide an effective thermal contact between the IC and the PWB. Traditionally, surface mount and power have been mutually exclusive terms. A variety of scaled-down TO-220-type packages have leads formed as gull wings to make them applicable for surface-mount applications. These packages, however, have only two shortcomings: they do not address the very low profile requirements (<2 mm) of many of today’s advanced systems, and they do not offer a terminal-count high enough to accommodate increasing integration. On the other hand, traditional low-power surface-mount packages require power-dissipation derating that severely limits the usable range of many high-performance analog circuits. The PowerPAD package (thermally enhanced TSSOP) combines fine-pitch surface-mount technology with thermal performance comparable to much larger power packages. The PowerPAD package is designed to optimize the heat transfer to the PWB. Because of the very small size and limited mass of a TSSOP package, thermal enhancement is achieved by improving the thermal conduction paths that remove heat from the component. The thermal pad is formed using a patented lead-frame design and manufacturing technique to provide a direct connection to the heat-generating IC. When this pad is soldered or otherwise thermally coupled to an external heat dissipator, high power dissipation in the ultra-thin, fine-pitch, surface-mount package can be reliably achieved. DIE Side View (a) End View (b) Bottom View (c) DIE Thermal Pad Figure 41. Views of Thermally Enhanced PWP Package

APPLICATION INFORMATION

Figure 42 and Figure 43 are a schematic diagrams of typical notebook computer application circuits.

8 RIN

10 LIN

electrolytic capacitor of 10 mF or greater should be placed near the audio power amplifier. Figure 42. Typical TPA0112 Application Circuit Using Single-Ended Inputs and Input MUX

2-W STEREO AUDIO POWER AMPLIFIER WITH FOUR SELECTABLE GAIN SETTINGS SLOS204B – MAY 1999 – REVISED MARCH 2000

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R MUX RHPIN RLINEIN C CRIN– 0.47 mF ROUT– 16 1 kW C OUTR 330 mF 100 kW L MUX LHPIN LLINEIN5 C IlHP 0.47 mF Left Head– phone Input Signal C ILLINE 0.47 mFLeft Line Input Signal C LIN 0.47 mF SHUT– DOWN 22 GND LOUT+ 4 LOUT– 9 C BYP 0.47 mF 1,12, 13,24 To System Control C SR 0.1 mF VDD C SR 0.1 mF VDD See Note A PC– Beep PC–BEEP PC ENABLE C PCB 0.47 mF PC BEEP Input Signal Gain/ MUX Control GAIN0 GAIN1 SE/BTL15 N/C C RIN+ 0.47 mFRight Positive Differential Input Signal Right Negative Differential Input Signal NOTE A: A 0.1 mF ceramic capacitor should be placed as close as possible to the IC. For filtering lower–frequency noise signals, a larger electrolytic capacitor of 10 mF or greater should be placed near the audio power amplifier. Figure 43. Typical TPA0112 Application Circuit Using Differential Inputs

2-W STEREO AUDIO POWER AMPLIFIER WITH FOUR SELECTABLE GAIN SETTINGS SLOS204B – MAY 1999 – REVISED MARCH 2000 21POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 gain setting via GAIN0 and GAIN1 inputs The gain of the TPA0112 is set by two input terminals, GAIN0 and GAIN1. Table 1. Gain Settings impedance will shift by 30% due to shifts in the actual resistance of the input impedance. settings, the input impedance could increase as high as 115 kW .

2-W STEREO AUDIO POWER AMPLIFIER WITH FOUR SELECTABLE GAIN SETTINGS SLOS204B – MAY 1999 – REVISED MARCH 2000

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The –3 dB frequency can be calculated using equation 1: (1) f–3 dB/C0043 1 2/C0112C /C0466R /C0248R I/C0467 If the filter must be more accurate, the value of the capacitor should be increased while value of the resistor to ground should be decreased. In addition, the order of the filter could be increased. input capacitor, CI In the typical application an input capacitor, CI, is required to allow the amplifier to bias the input signal to the proper dc level for optimum operation. In this case, CI and the input impedance of the amplifier, ZI, form a high-pass filter with the corner frequency determined in equation 2. fc(highpass)/C00431 2/C0112ZIC I –3 dB fc (2) The value of CI is important to consider as it directly affects the bass (low frequency) performance of the circuit. Consider the example where ZI is 710 kW and the specification calls for a flat bass response down to 40 Hz. Equation 2 is reconfigured as equation 3. C I /C00431 2/C0112ZIfc (3) In this example, CI is 5.6 nF so one would likely choose a value in the range of 5.6 nF to 1 mF. A further consideration for this capacitor is the leakage path from the input source through the input network (CI) and the feedback network to the load. This leakage current creates a dc offset voltage at the input to the amplifier that reduces useful headroom, especially in high gain applications. For this reason a low-leakage tantalum or ceramic capacitor is the best choice. When polarized capacitors are used, the positive side of the capacitor should face the amplifier input in most applications as the dc level there is held at V DD /2, which is likely higher than the source dc level. Note that it is important to confirm the capacitor polarity in the application.

2-W STEREO AUDIO POWER AMPLIFIER WITH FOUR SELECTABLE GAIN SETTINGS SLOS204B – MAY 1999 – REVISED MARCH 2000 23POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 power supply decoupling, CS The TPA0112 is a high-performance CMOS audio amplifier that requires adequate power supply decoupling to ensure the output total harmonic distortion (THD) is as low as possible. Power supply decoupling also prevents oscillations for long lead lengths between the amplifier and the speaker. The optimum decoupling is achieved by using two capacitors of different types that target different types of noise on the power supply leads. For higher frequency transients, spikes, or digital hash on the line, a good low equivalent-series-resistance (ESR) ceramic capacitor, typically 0.1 mF placed as close as possible to the device V DD lead works best. For filtering lower-frequency noise signals, a larger aluminum electrolytic capacitor of 10 mF or greater placed near the audio power amplifier is recommended. midrail bypass capacitor, CBYP The midrail bypass capacitor, CBYP , is the most critical capacitor and serves several important functions. During start-up or recovery from shutdown mode, CBYP determines the rate at which the amplifier starts up. The second function is to reduce noise produced by the power supply caused by coupling into the output drive signal. This noise is from the midrail generation circuit internal to the amplifier, which appears as degraded PSRR and THD+N. Bypass capacitor, C BYP , values of 0.47 mF to 1 mF ceramic or tantalum low-ESR capacitors are recommended for the best THD and noise performance. output coupling capacitor, CC In the typical single-supply SE configuration, an output coupling capacitor (CC ) is required to block the dc bias at the output of the amplifier thus preventing dc currents in the load. As with the input coupling capacitor, the output coupling capacitor and impedance of the load form a high-pass filter governed by equation 4. (4) fc(high)/C00431 2/C0112R LC C –3 dB fc The main disadvantage, from a performance standpoint, is the load impedances are typically small, which drives the low-frequency corner higher degrading the bass response. Large values of CC are required to pass low frequencies into the load. Consider the example where a CC of 330 mF is chosen and loads vary from 3 W , 4 W , 8 W , 32 W , 10 kW , to 47 kW . Table 2 summarizes the frequency response characteristics of each configuration.

2-W STEREO AUDIO POWER AMPLIFIER WITH FOUR SELECTABLE GAIN SETTINGS SLOS204B – MAY 1999 – REVISED MARCH 2000

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Table 2. Common Load Impedances Vs Low Frequency Output Characteristics in SE Mode

3 W 330 mF 161 Hz

4 W 330 mF 120 Hz

8 W 330 mF 60 Hz

32 W 330 mF 15 Hz

headphone response is good, and drive into line level inputs (a home stereo for example) is exceptional. resistance the more the real capacitor behaves like an ideal capacitor. voltage is squared, yields 4× the output power from the same supply rail and load impedance (see equation 5).

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Increasing power to the load does carry a penalty of increased internal power dissipation. The increased dissipation is understandable considering that the BTL configuration produces 4× the output power of the SE configuration. Internal dissipation versus output power is discussed further in the crest factor and thermal considerations section. single-ended operation In SE mode (see Figure 44 and Figure 45), the load is driven from the primary amplifier output for each channel (OUT+, terminals 21 and 4). The amplifier switches single-ended operation when the SE/BTL terminal is held high. This puts the negative outputs in a high-impedance state, and reduces the amplifier’s gain to 1 V/V. BTL amplifier efficiency Class-AB amplifiers are notoriously inefficient. The primary cause of these inefficiencies is voltage drop across the output stage transistors. There are two components of the internal voltage drop. One is the headroom or dc voltage drop that varies inversely to output power. The second component is due to the sinewave nature of the output. The total voltage drop can be calculated by subtracting the RMS value of the output voltage from V DD . The internal voltage drop multiplied by the RMS value of the supply current, IDD rms, determines the internal power dissipation of the amplifier. An easy-to-use equation to calculate efficiency starts out as being equal to the ratio of power from the power supply to the power delivered to the load. To accurately calculate the RMS and average values of power in the load and in the amplifier, the current and voltage waveform shapes must first be understood (see Figure 46). V(LRMS) VO IDD IDD(avg) Figure 46. Voltage and Current Waveforms for BTL Amplifiers shape whereas in BTL it is a full-wave rectified waveform. This means RMS conversion factors are different. supports the fact that each amplifier in the BTL device only draws current from the supply for half the waveform. The following equations are the basis for calculating amplifier efficiency.

2-W STEREO AUDIO POWER AMPLIFIER WITH FOUR SELECTABLE GAIN SETTINGS SLOS204B – MAY 1999 – REVISED MARCH 2000 27POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 Efficiency of a BTL amplifier/C0043 P L P SUP (7) Where: (8) P L /C0043 V Lrms2 R L , and VLRMS /C0043 V P 2/C0504, therefore, PL /C0043 V P 2R L PL = Power devilered to load PSUP = Power drawn from power supply VLRMS = RMS voltage on BTL load R L = Load resistance VP = Peak voltage on BTL load IDD avg = Average current drawn from the power supply V DD = Power supply voltage hBTL = Efficiency of a BTL amplifier and P SUP /C0043V DD IDD avg and IDD avg /C00431 /C0112/C0341 /C0112 V P R L sin(t) dt/C00431 /C0112/C0032 V P R L [cos(t)] /C0112 0 /C0043 2V P /C0112R L Therefore, P SUP /C0043 2V DD V P /C0112R L substituting PL and PSUP into equation 7, Efficiency of a BTL amplifier/C0043 V P 2R L 2V DD V P /C0112R L /C0043 /C0112V P 4V DD V P /C00432P L R L/C0504 /C0104BTL /C0043 /C01122P L R L/C0504 4V DD Where: Therefore, Table 3 employs equation 8 to calculate efficiencies for four different output power levels. Note that the efficiency of the amplifier is quite low for lower power levels and rises sharply as power to the load is increased resulting in a nearly flat internal power dissipation over the normal operating range. Note that the internal dissipation at full output power is less than in the half power range. Calculating the efficiency for a specific system is the key to proper power supply design. For a stereo 1-W audio system with 8-W loads and a 5-V supply, the maximum draw on the power supply is almost 3.25 W. Table 3. Efficiency Vs Output Power in 5-V 8-W BTL Systems † High peak voltages cause the THD to increase. indicates that as VDD goes down, efficiency goes up.

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crest factor and thermal considerations Class-AB power amplifiers dissipate a significant amount of heat in the package under normal operating conditions. A typical music CD requires 12 dB to 15 dB of dynamic range, or headroom above the average power output, to pass the loudest portions of the signal without distortion. In other words, music typically has a crest factor between 12 dB and 15 dB. When determining the optimal ambient operating temperature the internal dissipated power at the average output power level must be used. From the TPA0112 data sheet, one can see that when the TPA0112 is operating from a 5-V supply into a 3-W speaker that 4 W peaks are available. Converting watts to dB: P dB /C004310Log P W P ref /C004310Log 4W 1W /C00436d B (9) Subtracting the headroom restriction to obtain the average listening level without distortion yields: 6 dB – 15 dB = –9 dB (15 dB crest factor) 6 dB – 12 dB = –6 dB (12 dB crest factor) 6 dB – 9 dB = –3 dB (9 dB crest factor) 6 dB – 6 dB = 0 dB (6 dB crest factor) 6 dB – 3 dB = 3 dB (3 dB crest factor) Converting dB back into watts: P W /C004310PdB /C032410 /C0032P ref /C004363 mW (18 dB crest factor) /C0043125 mW (15 dB crest factor) /C0043250 mW (9 dB crest factor) /C0043500 mW (6 dB crest factor) /C00431000 mW (3 dB crest factor) (10) /C00432000 mW (15 dB crest factor) This is valuable information to consider when attempting to estimate the heat dissipation requirements for the amplifier system. Comparing the absolute worst case, which is 2 W of continuous power output with a 3 dB crest factor, against 12 dB and 15 dB applications drastically affects maximum ambient temperature ratings for the system. Using the power dissipation curves for a 5-V, 3-W system, the internal dissipation in the TPA0112 and maximum ambient temperatures is shown in Table 4. Table 4. TPA0112 Power Rating, 5-V, 3-W , Stereo

2-W STEREO AUDIO POWER AMPLIFIER WITH FOUR SELECTABLE GAIN SETTINGS SLOS204B – MAY 1999 – REVISED MARCH 2000 29POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 crest factor and thermal considerations (continued) Table 5. TPA0112 Power Rating, 5-V, 8-W , Stereo However, in the case of a 3 W load, the PDmax occurs at a point well above the normal operating power level. 150°C. The internal dissipation figures are taken from the Power Dissipation vs Output Power graphs. Internal dissipation of 0.6 W is estimated for a 2-W system with 15 dB crest factor per channel.

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The ability of the TPA0112 to easily switch between BTL and SE modes is one of its most important cost saving features. This feature eliminates the requirement for an additional headphone amplifier in applications where internal stereo speakers are driven in BTL mode but external headphone or speakers must be accommodated. Internal to the TPA0112, two separate amplifiers drive OUT+ and OUT–. The SE/BTL input (terminal 15) controls the operation of the follower amplifier that drives LOUT– and ROUT– (terminals 9 and 16). When SE/BTL is held low, the amplifier is on and the TPA0112 is in the BTL mode. When SE/BTL is held high, the OUT– amplifiers are in a high output impedance state, which configures the TPA0112 as an SE driver from LOUT+ and ROUT+ (terminals 4 and 21). I DD is reduced by approximately one-half in SE mode. Control of the SE/BTL input can be from a logic-level CMOS source or, more typically, from a resistor divider network as shown in Figure 47. ROUT+ 21 Figure 47. TPA0112 Resistor Divider Network Circuit O ) into the headphone jack.

2-W STEREO AUDIO POWER AMPLIFIER WITH FOUR SELECTABLE GAIN SETTINGS SLOS204B – MAY 1999 – REVISED MARCH 2000 31POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 The PC BEEP input allows a system beep to be sent directly from a computer through the amplifier to the speakers with few external components. The input is normally activated automatically, but may be selected manually by pulling PCB ENABLE high. When the PC BEEP input is active, both of the LINEIN and HPIN inputs are deselected and both the left and right channels are driven in BTL mode with the signal from PC BEEP. The gain from the PC BEEP input to the speakers is fixed at 0.3 V/V and is independent of the volume setting. When the PC BEEP input is deselected, the amplifier will return to the previous operating mode and volume setting. Furthermore, if the amplifier is in shutdown mode, activating PC BEEP will take the device out of shutdown and output the PC BEEP signal, then return the amplifier to shutdown mode. When PCB ENABLE is held low, the amplifier will automatically switch to PC BEEP mode after detecting a valid signal at the PC BEEP input. The preferred input signal is a square wave or pulse train with an amplitude of 1 V pp or greater. To be a accurately detected, the signal must have a minimum of 1 Vpp amplitude, rise and fall times of less than 0.1 ms and a minimum of 8 rising edges. When the signal is no longer detected, the amplifier will return to its previous operating mode and volume setting. When PCB ENABLE is held high, PC BEEP is selected and the LINEIN and HPIN inputs are deactivated regardless of the input signal. PCB ENABLE has an internal 100 kW pulldown resistor and will trip at approximately VDD /2. If it is desired to ac couple the PC BEEP input, the value of the coupling capacitor should be chosen to satisfy equation 14: C PCB /C01191 2/C0112fPCB (100 k/C0087) (14) The PC BEEP input can also be dc coupled to avoid using this coupling capacitor. The pin normally sits at midrail when no signal is present.

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R MUX RHPIN RLINEIN C IRHP 0.47 mFRight Headphone Input Signal C IRLINE 0.47 mF Right Line Input Signal C RIN 0.47 mF ROUT– 16 Figure 48. TPA0112 Example Input MUX Circuit operation section for a description of the headphone jack control circuit. unconnected because amplifier operation would be unpredictable. Table 6. Shutdown and Mute Mode Functions † Inputs should never be left unconnected.

2-W STEREO AUDIO POWER AMPLIFIER WITH FOUR SELECTABLE GAIN SETTINGS SLOS204B – MAY 1999 – REVISED MARCH 2000 33POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 MECHANICAL DATA PWP (R-PDSO-G) PowerPAD  PLASTIC SMALL-OUTLINE PACKAGE 4073225/E 03/97 0,50 0,75 0,25 0,15 NOM Thermal Pad (See Note D) Gage Plane 2824 7,70 7,90 6,40 6,60 9,60 9,80 6,60 6,20 0,19 4,50 4,30 0,15 A 0,30 1,20 MAX 1614 5,10 4,90 PINS 4,90 5,10 DIM A MIN A MAX 0,05 Seating Plane 0,65 0,10 M0,10 0°–8° 20-PIN SHOWN NOTES: A. All linear dimensions are in millimeters. B. This drawing is subject to change without notice. C. Body dimensions do not include mold flash or protrusions. D. The package thermal performance may be enhanced by bonding the thermal pad to an external thermal plane. This pad is electrically and thermally connected to the backside of the die and terminals 1, 12, 13, and 24. The dimensions of the thermal pad are 2.40 mm × 4.70 mm (maximum). The pad is centered on the bottom of the package. E. Falls within JEDEC MO-153 PowerPAD is a trademark of Texas Instruments Incorporated.

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