MP3115

MP3115 MPS | Alldatasheet

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Technical content

High-Efficiency, Single-Cell Alkaline, 1.3MHz Synchronous Step-up Converter with Output Disconnect MP3115 Rev. 0.9 www.MonolithicPower.com 1 4/12/2016 MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2016 MPS. All Rights Reserved. The Future of Analog IC Technology

DESCRIPTION

The MP3115 is a synchronous, fixed frequency, current mode step-up converter with output-to- input disconnect optimized to boost a single AA Alkaline battery to 2.5V or 3.3V. It can startup from an input voltage as low as 0.950V and provide in-rush current limiting as well as output short circuit protection. The integrated P-Channel synchronous rectified switch provides improved efficiency and eliminates an external schottky diode. The output disconnect feature allows the output to be completely discharged, thus allowing the part to draw less than 1µA of current in shutdown mode. The 1.3MHz switching frequency allows for the use of smaller external components and the internal compensation and soft-start minimize the external component count, all helping to produce a compact solution for a wide range of load current. The MP3115 regulates the output voltage up to 4.0V or 3.3V at 200mA from a single cell AA battery, without the use of an external Schottky diode. The MP3115 is offered in a SOT23-6 package. EVALUATION BOARD REFERENCE Board Number Dimensions EV3115DT-00A L x W x H (5cm x 5cm x 1.2cm)

FEATURES

• Over 90% Efficiency
• Output-to-Input Disconnect in Shutdown Mode
• Internal Synchronous Rectifier
• Output Voltage up to 4.0V without an External Schottky Diode
• Inrush Current Limiting and Internal Soft-Start
• Internal Compensation
• 1A Minimum Peak Current Limit
• 1.3MHz Fixed Switching Frequency
• Zero Current Shutdown Mode
• Thermal Shutdown
• 6-Pin SOT-23 Package

APPLICATIONS

• Single-cell Alkaline Consumer Products
• MP3 Players
• Wireless Mouse
• RFTags
• Audio Recorders “MPS” and “The Future of Analog IC Technology” are Registered Trademarks of Monolithic Power Systems, Inc. TYPICAL APPLICATION VIN 0.95V to 2.5V EN VOUT 3.3V GND SW IN EN OUT FB MP3115

MP3115 – HIGH-EFFICIENCY 1.3MHz SYNCHRONOUS STEP-UP CONVERTER MP3115 Rev. 0.9 www.MonolithicPower.com 2 4/12/2016 MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2016 MPS. All Rights Reserved. PACKAGE REFERENCE TOP VIEW SW GND FB IN OUT EN Part Number* Package Temperature MP3115DT SOT23-6 –40°C to +85°C * For Tape & Reel, add suffix –Z (eg. MP3115DT–Z) For RoHS Compliant Packaging, add suffix –LF (eg. MP3115DT–LF–Z) ABSOLUTE MAXIMUM RATINGS (1) Thermal Resistance (3) θJA θJC Notes: 1) Exceeding these ratings may damage the device. 2) The device is not guaranteed to function outside of its operating conditions. 3) Measured on approximately 1” square of 1 oz copper.

ELECTRICAL CHARACTERISTICS

VIN = 1.5V, VEN = VOUT = 3.3V, TA = +25°C, unless otherwise noted. Parameter Symbol Condition Min Typ Max Units Minimum Startup Voltage VST R L = 3kΩ, Rising Edge 0.95 1.1 V Minimum Operating Voltage (4) V IN V EN = VIN 0.5 V Output Voltage Range VOUT 2.5 4.0 V Supply Current (Shutdown) V EN = VOUT = 0V 0 1 μA Supply Current (Quiescent) V FB = 1.3V 200 μA Feedback Voltage VFB 1.225 V Feedback Input Current V FB = 1.2V 10 nA Switching Frequency fSW V FB= 1.1V 1.3 MHz Maximum Duty Cycle DMAX V FB= 1.1V 85 90 % EN Input Low Voltage 0.4 V EN Input High Voltage 0.9 V EN Input Current V EN = 3V 0 1 μA NMOS On Resistance RNMOS 300 m Ω NMOS Leakage Current V SW = 5.5V 1 μA NMOS Current Limit ILIM 1 1.3 A PMOS On Resistance RPMOS 600 m Ω PMOS Leakage Current V EN = VOUT = 0V, VSW = 3V 1 μA Thermal Shutdown (5) 160 °C Thermal Shutdown Hysteresis (5) 30 °C Minimum On Time (5) 100 150 ns Notes: 4) The MP3115 is not dependent on V IN when VOUT is greater than 2.4V. 5) Guaranteed by design, not tested.

MP3115 – HIGH-EFFICIENCY 1.3MHz SYNCHRONOUS STEP-UP CONVERTER MP3115 Rev. 0.9 www.MonolithicPower.com 3 4/12/2016 MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2016 MPS. All Rights Reserved. PIN FUNCTIONS Pin # Name Description 1 SW Output Switch Node. SW is the drain of the internal N-Channel and P-Channel MOSFETs. Connect the inductor to SW to complete the step-up converter. 2 GND Ground. 3 FB Regulation Feedback Input. Connect an external resistive voltage divider from the output to FB to set the output voltage. 4 EN Regulator On/Off Control Input. A logic high input (V EN > 0.9V) turns on the regulator. A logic low input (VEN < 0.4V) puts the MP3115 into low current shutdown mode. 5 OUT Supply Input for the MP3115 and Output Volt age Sense Input. Connect to the output of the converter. 6 IN Input Voltage.

MP3115 – HIGH-EFFICIENCY 1.3MHz SYNCHRONOUS STEP-UP CONVERTER MP3115 Rev. 0.9 www.MonolithicPower.com 4 4/12/2016 MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2016 MPS. All Rights Reserved. TYPICAL PERFORMANCE CHARACTERISTICS C1 = 10µF, C2=22µF, L=1.7µH,R2=20K, TA = +25ºC, unless otherwise noted. EFFICIENCY(%) Efficiency vs. Load Current VIN 1V/div. VOUT 50mV/div. VEN 2V/div. VOUT 2V/div. IIN 0.2A/div. IOUT 50mA/div. VOUT 0.1V/div. Line Regulation VIN=1.2V to 2V,VOUT=2.5V, IOUT=48mA VEN=VIN,Resistor Load VIN=1.2V,VOUT=2.5V,IOUT =0mA to 50mA VEN=VIN,Resistor Load Minimum Start V IN vs. IOUT IPEAK vs. Duty Cycle Line Transient Load Transient VEN=2V,VIN=1.5V,VOUT =3.3V IOUT =41mA,C FF =10nF Inrush Current EFFICIENCY(%) Efficiency vs. Load Current EFFICIENCY(%) 10 13 16 19 22 25 0 30 60 90 120 150 EFFICIENCY(%)EFFICIENCY(%)EFFICIENCY(%) OUTPUT VOLTAGE (V) INPUT VOLTAGE (V) PEAK CURRENT (mA) 100 1001000 1000 0 2.40 2.44 2.48 2.52 2.56 2.60 OUTPUT VOLTAGE (V) 2.40 0.8 1.0 1.2 1.4 1.6 1.8 2.0 2.44 2.48 2.52 2.56 2.60 50 100 150 200 250 Efficiency vs. Load Current Efficiency vs. Load Current Efficiency vs. Load Current Efficiency vs. Load Regulation Load Current LOAD CURRENT (mA) INPUT VOLTAGE (V) OUTPUT CURRENT (mA) LOAD CURRENT (mA) LOAD CURRENT (mA) 700 900 1100 1300 1500 1700 40 50 60 70 80 Duty Cycle (%) VIN=1.5V VOUT=2.5V VIN=1.5V VIN=2.5V VOUT=3.3V VIN=1.5V IOUT=100mA VOUT=3.3V VOUT=2.5V 200 s/div. 40 s/div. 1ms/div.

MP3115 – HIGH-EFFICIENCY 1.3MHz SYNCHRONOUS STEP-UP CONVERTER MP3115 Rev. 0.9 www.MonolithicPower.com 5 4/12/2016 MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2016 MPS. All Rights Reserved. TYPICAL PERFORMANCE CHARACTERISTICS (continued) C1 = 10µF, C2=22µF, L=1.7µH,R2=20K, TA = +25ºC, unless otherwise noted. VIN 1V/div. VSW 2V/div. IL 1A/div. VIN 1V/div. VSW 2V/div. IL 1A/div. VIN 0.5V/div. VSW 2V/div. VEN 2V/div. VIN 2V/div. VSW 2V/div. IL 0.2A/div. VIN 2V/div. VSW 2V/div. VO 5V/div. IL 0.2A/div. VIN 1V/div. VSW 2V/div. IL 1A/div. VIN 0.5V/div. VSW 2V/div. VEN 2V/div. VIN 1V/div. VSW 2V/div. IL 1A/div. Short Circuit VIN=VEN=2V, VOUT=3.3V No Load Ripple VIN=VEN=0.92V, VOUT=3.3V IOUT=0mA Full Load Ripple VIN=VEN=0.95V, VOUT=3.3V IOUT=150mA Short Circuit Recovery VIN=VEN=2V, VOUT=3.3V 20ms/div. 20ms/div. VOUT 2V/div VOUT 5V/div VOUT 10mV/div VOUT 50mV/div VOUT 2V/div VOUT 2V/div VOUT 2V/div 10ms/div1ms/div

MP3115 – HIGH-EFFICIENCY 1.3MHz SYNCHRONOUS STEP-UP CONVERTER MP3115 Rev. 0.9 www.MonolithicPower.com 6 4/12/2016 MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2016 MPS. All Rights Reserved. OPERATION GND SW OUT CONTROL LOGIC RSENSE CURRENT SENSE AMPLIFIERPWM COMPARATOR RAMP OSC 1.3MHz BIAS STARTUP SOFT-START PROTECTION ERROR AMPLIFIER FB EN IN 6 Figure 1—Functional Block Diagram The MP3115 uses a 1.3MHz fixed-frequency, current-mode regulation architecture to regulate the output voltage. The MP3115 measures the output voltage through an external resistive voltage divider and compares that to the internal 1.2V reference to generate the error voltage. The current-mode regulator compares the error voltage to the inductor current to regulate the output voltage. The use of current- mode regulation improves transient response and control loop stability. When the MP3115 is disabled (EN<0.4V), both power switches are off. The body of the P-Channel MOSFET connects to SW thus there is no current path from SW to OUT. When the MP3115 is enabled (EN>0.8V), the P-Channel MOSFET turns on to charge the output capacitor to a voltage close to the input voltage. During this time, the gate of the P-Channel is controlled to limit the chip power dissipation. The MP3115 starts switching when the output voltage is close to the input voltage. If the input voltage is less than 1.6V, the MP3115 will start with CCM (constant current mode) until the output voltage crosses 1.6V. After that, the soft-start circuit will take over to bring the output voltage to the regulated value. At the beginning of each cycle, the N-channel MOSFET switch is turned on, forcing the inductor current to rise. The current at the source of the switch is internally measured and converted to a voltage by the current sense amplifier. That voltage is compared to the error voltage. When the inductor current rises sufficiently, the PWM comparator turns off the switch, forcing the inductor current to the output capacitor through the internal P-Channel MOSFET rectifier, which forces the inductor current to decrease. The peak inductor current is controlled by the error voltage, which in turn is controlled by the output voltage. Thus the output voltage controls the inductor current to satisfy the load. The MP3115 has a temperature sensing circuit to protect the part. The MP3115 turns off both switches when the chip temperature reaches 150°C.

MP3115 – HIGH-EFFICIENCY 1.3MHz SYNCHRONOUS STEP-UP CONVERTER MP3115 Rev. 0.9 www.MonolithicPower.com 7 4/12/2016 MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2016 MPS. All Rights Reserved.

APPLICATION INFORMATION

Setting the Output Voltage Set the output voltage by selecting the resistive voltage divider ratio. The voltage divider drops the output voltage to the 1.2V feedback voltage. Use 20k Ω for the low-side resistor (R2) of the voltage divider. Determine the high-side resistor (R1) by the equation: 2 R V V V1 R FB FBOUT Where V OUT is the output voltage, V FB is the 1.2V feedback voltage and R2=20kΩ. Selecting the Input Capacitor An input capacitor is required to supply the AC ripple current to the inductor while limiting noise at the input source. Multi-layer ceramic capacitors are recommended as they have extremely low ESR and are available in small footprints. Use an input capacitor of 4.7 μF or greater, and place it physically close to the device. Selecting the Output Capacitor A single 4.7µF to 10µF ceramic capacitor normally provides sufficient output capacitance for most applications. Larger values (up to 22µF) may be used to obtain extremely low output voltage ripple and improve transient response. The impedance of the ceramic capacitor at the switching frequency is dominated by its capacitance, so the output voltage ripple is mostly independent of ESR. The output voltage ripple V RIPPLE is calculated as: ( ) SWUTO INUTOLOAD RIPPLE f 2 C V V V IV × × Where VIN is the input voltage, I LOAD is the load current, C2 is the capacitance of the output capacitor and f SW is the 1.3MHz switching frequency. Selecting the Inductor The inductor is required to force the output voltage higher while being driven by the lower input voltage. A good rule for determining the inductance is to allow the peak-to-peak ripple current to be approximately 30%-50% of the maximum input current. Make sure that the peak inductor current is below the minimum current limit at the duty cycle used to prevent loss of regulation due to current limit variation. Calculate the required inductance value L using the equations: I f V ) V - (V VL SWOUT INOUT IN Δ × ×= η × IN ) MAX (LOADOUT ) MAX ( IN V I V I ( ) ) MAX ( INI % 50 % 30 I−=Δ Where ILOAD(MAX) is the maximum load current, ΔI is the peak-to-peak inductor ripple current and η is the efficiency. For the MP3115, 4.7µH is recommended for most applications. Choose an inductor that does not saturate at the peak switch current as calculated above with additional margin to cover for heavy load transients and extreme startup conditions. Selecting the Feed-Forward Capacitor A feed-forward capacitor in parallel with the high-side resistor R1 can be added to improve the output ripple at both discontinuous conduction modes and the load transient response. A 47pF capacitor is recommended for most applications. LAYOUT CONSIDERATIONS High frequency switching regulators require very careful layout for stable operation and low noise. All components must be placed as close to the IC as possible. All feedback components must be kept close to the FB pin to prevent noise injection on the FB pin trace. The ground return of C1 and C2 should be tied close to the GND pin. See the MP3115 demo board layout for reference.

MP3115 – HIGH-EFFICIENCY 1.3MHz SYNCHRONOUS STEP-UP CONVERTER NOTICE: The information in this document is subject to change wi thout notice. Users should warra nt and guarantee that third party Intellectual Property rights are not infringed upon w hen integrating MPS products into any application. MPS will not assume any legal responsibility for any said applications. MP3115 Rev. 0.9 www.MonolithicPower.com 8 4/12/2016 MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2016 MPS. All Rights Reserved.

PACKAGE INFORMATION

0.30 0.50 SEATING PLANE

0.95 BSC

0.90 1.30 1.45 MAX 0.00 0.15 PACKAGE OUTLINE DRAWING FOR 6-SOT23 MF-PO-D-0032 revision 2.1 TOP VIEW FRONT VIEW SIDE VIEW RECOMMENDED LAND PATTERN 2.80 3.00 1.50 1.70 2.60 3.00 1 3 0.09 0.20 0.30 0.550o-8o

0.25 BSC

2.60 TYP 1.20 TYP 0.95 BSC 0.60 TYP SEE DETAIL "A" AAAAPIN 1 See Note 7 EXAMPLE TOP MARK NOTE: 1) ALL DIMENSIONS ARE IN MILLIMETERS. 2) PACKAGE LENGTH DOES NOT INCLUDE MOLD FLASH, PROTRUSION OR GATE BURR. 3) PACKAGE WIDTH DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSION. 4) LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.10 MILLIMETERS MAX. 5) DRAWING CONFORMS TO JEDEC MO-178, VARIATION AB. 6) DRAWING IS NOT TO SCALE. 7) PIN 1 IS LOWER LEFT PIN WHEN READING TOP MARK FROM LEFT TO RIGHT, (SEE EXAMPLE TOP MARK)