MP2303

MP2303 MPS | Alldatasheet

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3A, 28V, 340KHz Synchronous Rectified Step-Down Converter INITIAL RELEASE – SPECIFICATIONS SUBJECT TO CHANGE MP2303 Rev. 0.91 www.MonolithicPower.com 1 3/10/2006 MPS Proprietary Information. Unaut horized Photocopy and Duplication Prohibited. © 2006 MPS. All Rights Reserved. The Future of Analog IC Technology TM TM

DESCRIPTION

The MP2303 is a monolithic synchronous buck regulator. The device integrates 120m Ω MOSFETS that provide 3A continuous load current over a wide operating input voltage of 4.75V to 28V. Current mode control provides fast transient response and cycle-by-cycle current limit. An adjustable soft-start prevents inrush current at turn-on. In shutdown mode, the supply current drops to 1µA. This device, available in an 8-pin SOIC package, provides a very compact system solution with minimal reliance on external components. EVALUATION BOARD REFERENCE Board Number Dimensions EV2303DN-00A 2.0”X x 1.5”Y x 0.5”Z

FEATURES

• 3A Output Current
• Wide 4.75V to 28V Operating Input Range
• Integrated 120m Ω Power MOSFET Switches
• Output Adjustable from 0.8V to 25V
• Up to 95% Efficiency
• Programmable Soft-Start
• Stable with Low ESR Ceramic Output Capacitors
• Fixed 340KHz Frequency
• Cycle-by-Cycle Over Current Protection
• Input Under Voltage Lockout
• Thermally Enhanced 8-Pin SOIC Package

APPLICATIONS

• Distributed Power Systems
• Pre-Regulator for Linear Regulators
• Notebook Computers “MPS” and “The Future of Analog IC Technology” are Trademarks of Monolithic Power Systems, Inc. TYPICAL APPLICATION VIN 4.75V-28V VOUT 5V/3A 10nF 3.3nF MP2303 BS SS EN COMP FB IN SW GND MP2303_TAC01 (optional) 100 EFFICIENCY (%) LOAD CURRENT (A) MP2303-EC01 Efficiency vs Load Current VIN = 12V VIN = 24V VOUT = 5V

MP2303 – 3A, 28V, 340KHz SYNCHRONOUS RECTIFIED, STEP-DOWN CONVERTER INITIAL RELEASE – SPECIFICATIONS SUBJECT TO CHANGE MP2303 Rev. 0.91 www.MonolithicPower.com 2 3/10/2006 MPS Proprietary Information. Unaut horized Photocopy and Duplication Prohibited. © 2006 MPS. All Rights Reserved. TM PACKAGE REFERENCE Part Number* Package Temperature MP2303DN SOIC8N (Exposed Pad) –40°C to +85°C * For Tape & Reel, add suffix –Z (eg. MP2303DN–Z) For Lead Free, add suffix –LF (eg. MP2303DN–LF–Z) ABSOLUTE MAXIMUM RATINGS (1) Recommended Operating Conditions (2) Ambient Operating Temperature ... –40°C to +85°C Thermal Resistance (3) θJA θJC Notes: 1) Exceeding these ratings may damage the device. 2) The device is not guaranteed to function outside of its operating conditions. 3) Measured on approximately 1” square of 1 oz copper. ELECTRICAL CHARACTERISTICS (4) VIN = 12V, TA = +25°C, unless otherwise noted. Parameter Symbol Condition Min Typ (4) Max Units Shutdown Supply Current V EN = 0V 0.3 3.0 µA Supply Current V EN = 2.7V, VFB = 1.0V 1.3 1.5 mA 4.75V ≤ VIN ≤ 28V, TA = +25°C 0.780 0.800 0.820 V Feedback Voltage V FB –40°C ≤ TA ≤ +85°C 0.772 0.828 V OVP Threshold Voltage 0.90 0.95 1.00 V Error Amplifier Voltage Gain A EA 400 V/V Error Amplifier Transconductance G EA ∆IC = ±10µA 550 820 1100 µA/V High-Side Switch-On Resistance R DS(ON)1 120 m Ω Low-Side Switch-On Resistance R DS(ON)2 120 m Ω High-Side Switch Leakage Current V EN = 0V, VSW = 0V 0 10 µA Upper-Switch Current Limit 4.3 6.3 A Lower-Switch Current Limit From Drain to Source 1.25 A COMP to Current Sense Transconductance GCS 9 A/V TA = +25°C 300 340 380 KHz Oscillation Frequency F osc1 –40°C ≤ TA ≤ +85°C 270 400 KHz Short Circuit Oscillation Frequency F osc2 V FB = 0V 110 KHz Maximum Duty Cycle D MAX V FB = 0.7V 90 % Minimum On-Time 220 ns EN Shutdown Threshold Voltage V EN Rising 1.1 1.5 2.0 V BS IN SW GND SS EN COMP FB TOP VIEW MP2303_PD01_SOIC8N

MP2303 – 3A, 28V, 340KHz SYNCHRONOUS RECTIFIED, STEP-DOWN CONVERTER INITIAL RELEASE – SPECIFICATIONS SUBJECT TO CHANGE MP2303 Rev. 0.91 www.MonolithicPower.com 3 3/10/2006 MPS Proprietary Information. Unaut horized Photocopy and Duplication Prohibited. © 2006 MPS. All Rights Reserved. TM ELECTRICAL CHARACTERISTICS (4) (continued) VIN = 12V, TA = +25°C, unless otherwise noted. Parameter Symbol Condition Min Typ (4) Max Units EN Shutdown Threshold Voltage Hysteresis 220 mV 2.2 2.5 2.7 V EN Lockout Threshold Voltage EN Lockout Hysteresis 210 mV VIN rising, TA = +25°C 3.8 4.05 4.30 V Input Under Voltage Lockout Threshold UVLO Input Under Voltage Lockout Threshold Hysterisis 210 mV Soft-Start Current V SS = 0V 6 µA Thermal Shutdown 160 °C Note: 4) 100% production test at +25°C. Spec ifications over the temperature range are guaranteed by design and characterization. PIN FUNCTIONS Pin # Name Description 1 BS High-Side Gate Drive Boost Input. BS supplies the drive for the high-side N-Channel MOSFET switch. Connect a 0.01µF or greater capacitor from SW to BS to power the high side switch. 2 IN Power Input. IN supplies the power to the IC, as well as the step-down converter switches. Drive IN with a 4.75V to 28V power source. Bypass IN to GND with a suitably large capacitor to eliminate noise on the input to the IC. See Input Capacitor. 3 SW Power Switching Output. SW is the switching node that supplies power to the output. Connect the output LC filter from SW to the output load. Note that a capacitor is required from SW to BS to power the high-side switch. 4 GND Ground (Connect Exposed Pad to Pin 4). 5 FB Feedback Input. FB senses the output voltage to regulate that voltage. Drive FB with a resistive voltage divider from the output voltage. The feedback reference voltage is 0.8V. See Setting the Output Voltage.

6 COMP

Compensation Node. COMP is used to compensate the regulation control loop. Connect a series RC network from COMP to GND to compensate the regulation control loop. In some cases, an additional capacitor from COMP to GND is required. See Compensation Components. 7 EN Enable Input. EN is a digital input that turns the regulator on or off. Drive EN higher than 2.7V to turn on the regulator, drive it lower than 1.1V to turn it off. Pull up to the IN pin with 100kΩ resistor for automatic startup. 8 SS Soft-start Control Input. SS controls the soft-start period. Connect a capacitor from SS to GND to set the soft-start period. See Soft-Start Capacitor.

MP2303 – 3A, 28V, 340KHz SYNCHRONOUS RECTIFIED, STEP-DOWN CONVERTER INITIAL RELEASE – SPECIFICATIONS SUBJECT TO CHANGE MP2303 Rev. 0.91 www.MonolithicPower.com 4 3/10/2006 MPS Proprietary Information. Unaut horized Photocopy and Duplication Prohibited. © 2006 MPS. All Rights Reserved. TM TYPICAL PERFORMANCE CHARACTERISTICS VIN = 12V, VO = 3.3V, L = 10µH, CIN = 10µF, COUT = 22µF x 2, TA = +25°C, unless otherwise noted. MP2303-TPC01 Feeback Voltage vs. Temperature MP2303-TPC02 UVLO Rising vs. Temperature MP2303-TPC04 Oscillator Frequency 0.810 0.805 0.800 0.795 0.790 0.7850 0.780 4.5 4.4 4.3 4.2 4.1 4.0 3.9 3.8 3.7 -40 -20 02 0 40 60 80 -40 -20 02 0 40 60 80 FEEDBACK VOLTAGE (V) FREQUENCY (KHz) TEMPERATURE (oC) 345 340 335 330 325 -40 -20 02 0 40 60 80 TEMPERATURE (oC) TEMPERATURE (oC) UVLO THRESHOLD (V) VIN = 4.75V VIN = 12V VIN = 28V MP2303-TPC03 Enable Lockout Threshold vs. Temperature 2.70 2.65 2.60 2.55 2.50 2.45 2.40 2.35 2.30 -40 -20 02 0 40 60 80 ENABLE VOLTAGE (V) TEMPERATURE (oC) EFFICIENCY (%) LOAD CURRENT (A) MP2303-EC02 Efficiency vs Load Current VIN = 12V VIN = 24V VOUT = 2.5V

MP2303 – 3A, 28V, 340KHz SYNCHRONOUS RECTIFIED, STEP-DOWN CONVERTER INITIAL RELEASE – SPECIFICATIONS SUBJECT TO CHANGE MP2303 Rev. 0.91 www.MonolithicPower.com 5 3/10/2006 MPS Proprietary Information. Unaut horized Photocopy and Duplication Prohibited. © 2006 MPS. All Rights Reserved. TM TYPICAL PERFORMANCE CHARACTERISTICS (continued) VIN = 12V, VO = 3.3V, L = 10µH, CIN = 10µF, COUT = 22µF x 2, TA = +25°C, unless otherwise noted. VIN 200mV/div. VOUT AC Coupled 10mV/div. IL 500mA/div. MP2303-TPC07 Steady State Test VIN = 12V, VOUT = 3.3V, IOUT = 1A VOUT 1V/div. IL 1A/div. 4ms/div. MP2303-TPC05 VOUT 1V/div. VSW 10V/div. VEN 5V/div. IL 1A/div. MP2303-TPC06 Power Off through Enable VIN = 24V, VOUT = 3.3V, IOUT = 2A VOUT 100mV/div. VSW 20V/div. VCOMP 200mV/div. IL 1A/div. MP2303-TPC08 Load Transient Test VIN = 24V, VOUT = 3.3V, IOUT = 0A-1A step with CFF = 470pF VOUT 1V/div. VCOMP 1V/div. IL 2A/div. MP2303-TPC09 Short Circuit Protection VIN = 24V, VOUT = 3.3V, IOUT = 0A

MP2303 – 3A, 28V, 340KHz SYNCHRONOUS RECTIFIED, STEP-DOWN CONVERTER INITIAL RELEASE – SPECIFICATIONS SUBJECT TO CHANGE MP2303 Rev. 0.91 www.MonolithicPower.com 6 3/10/2006 MPS Proprietary Information. Unaut horized Photocopy and Duplication Prohibited. © 2006 MPS. All Rights Reserved. TM OPERATION MP2303_BD01 LOCKOUT COMPARATOR INTERNAL REGULATORS IN EN ERROR AMPLIFIER 1.2V OVP RAMP CLK 0.8V 0.3V CURRENT COMPARATOR CURRENT SENSE AMPLIFIER0.95V SHUTDOWN COMPARATOR COMP 6 SS 8 FB 5 GND4 OSCILLATOR 340KHz S R Q SW3 BS1 IN OVP IN < 4.05V EN OK Q 1.5V 2.5V + Figure 1—Functional Block Diagram The MP2303 is a synchronous rectified, current-mode, step-down regulator. It regulates input voltages from 4.75V to 28V down to an output voltage as low as 0.8V, and supplies up to 3A of load current. The MP2303 uses current-mode control to regulate the output voltage. The output voltage is measured at FB through a resistive voltage divider and amplified through the internal transconductance error amplifier. The voltage at COMP pin is compared to the switch current measured internally to control the output voltage. The converter uses internal N-Channel MOSFET switches to step-down the input voltage to the regulated output voltage. Since the high side MOSFET requires a gate voltage greater than the input voltage, a boost capacitor connected between SW and BS is needed to drive the high side gate. The boost capacitor is charged from the internal 5V rail when SW is low. When the MP2303 FB pin exceeds 20% of the nominal regulation voltage of 0.8V, the over voltage comparator is tripped; the COMP pin and the SS pin are discharged to GND, forcing the high-side switch off.

MP2303 – 3A, 28V, 340KHz SYNCHRONOUS RECTIFIED, STEP-DOWN CONVERTER INITIAL RELEASE – SPECIFICATIONS SUBJECT TO CHANGE MP2303 Rev. 0.91 www.MonolithicPower.com 7 3/10/2006 MPS Proprietary Information. Unaut horized Photocopy and Duplication Prohibited. © 2006 MPS. All Rights Reserved. TM APPLICATIONS INFORMATION COMPONENT SELECTION Setting the Output Voltage The output voltage is set using a resistive voltage divider from the output voltage to FB pin. The voltage divider divides the output voltage down to the feedback voltage by the ratio: 2R1R 2RVV OUTFB += Thus the output voltage is: 2R1R8.0VOUT +×= Where VFB is the feedback voltage and V OUT is the output voltage. A typical value for R2 can be as high as 100k Ω, but a typical value is 10kΩ. Using that value, R1 is determined by: )k)(8.0V(5.121R OUT Ω−×= For example, for a 3.3V output voltage, R2 is 10kΩ, and R1 is 31.3kΩ. Inductor The inductor is required to supply constant current to the output load while being driven by the switched input voltage. A larger value inductor will result in less ripple current that will result in lower output ripple voltage. However, the larger value inductor will have a larger physical size, higher series resistance, and/or lower saturation current. A good rule for determining the inductance to use is to allow the peak-to-peak ripple current in the inductor to be approximately 30% of the maximum switch current limit. Also, make sure that the peak inductor current is below the maximum switch current limit. The inductance value can be calculated by: ⎛ −××= IN OUT S OUT V V1∆If VL Where VIN is the input voltage, f S is the 340KHz switching frequency, and ∆IL is the peak-to- peak inductor ripple current. Choose an inductor that will not saturate under the maximum inductor peak current. The peak inductor current can be calculated by: IN OUT S OUT LOADLP V V1Lf2 VII Where ILOAD is the load current. Optional Schottky Diode During the transition between high-side switch and low-side switch, the body diode of the low- side power MOSFET conducts the inductor current. The forward voltage of this body diode is high. An optional Schottky diode may be paralleled between the SW pin and GND pin to improve overall efficiency. Table 2 lists example Schottky diodes and their Manufacturers. Table 2—Diode Selection Guide Part Number Voltage/Current Rating Vendor B130 30V, 1A Diodes, Inc. SK13 30V, 1A Diodes, Inc. MBRS130 30V, 1A International Rectifier Input Capacitor The input current to the step-down converter is discontinuous, therefore a capacitor is required to supply the AC current to the step-down converter while maintaining the DC input voltage. Use low ESR capacitors for the best performance. Ceramic capacitors are preferred, but tantalum or low-ESR electrolytic capacitors may also suffice. Choose X5R or X7R dielectrics when using ceramic capacitors. Since the input capacitor (C1) absorbs the input switching current it requires an adequate ripple current rating. The RMS current in the input capacitor can be estimated by: × −×= IN OUT IN OUTLOAD1C V V1V VII The worst-case condition occurs at V IN = 2VOUT, where: II LOAD 1C =

MP2303 – 3A, 28V SYNCHRONOUS RECTIFIED, STEP-DOWN CONVERTER INITIAL RELEASE – SPECIFICATIONS SUBJECT TO CHANGE MP2303 Rev. 0.91 www.MonolithicPower.com 8 3/10/2006 MPS Proprietary Information. Unaut horized Photocopy and Duplication Prohibited. © 2006 MPS. All Rights Reserved. For simplification, choose the input capacitor whose RMS current rating greater than half of the maximum load current. The input capacitor can be electrolytic, tantalum or ceramic. When using electrolytic or tantalum capacitors, a small, high quality ceramic capacitor, i.e. 0.1µF, should be placed as close to the IC as possible. When using ceramic capacitors, make sure that they have enough capacitance to provide sufficient charge to prevent excessive voltage ripple at input. The input voltage ripple caused by capacitance can be estimated by: IN OUT IN OUT S LOAD IN V V1V V 1Cf IV Output Capacitor The output capacitor is required to maintain the DC output voltage. Ceramic, tantalum, or low ESR electrolytic capacitors are recommended. Low ESR capacitors are preferred to keep the output voltage ripple low. The output voltage ripple can be estimated by: 1RV V1Lf VV S ESR IN OUT S OUT OUT Where C2 is the output capacitance value and RESR is the equivalent series resistance (ESR) value of the output capacitor. In the case of ceramic capacitors, the impedance at the switching frequency is dominated by the capacitance. The output voltage ripple is mainly caused by the capacitance. For simplification, the output voltage ripple can be estimated by: ⎛ −× ××× IN OUT S OUT OUT V 2CLf8 V∆V In the case of tantalum or electrolytic capacitors, the ESR dominates the impedance at the switching frequency. For simplification, the output ripple can be approximated to: ESRIN OUT S OUT OUT RV V1Lf V∆V ×⎟⎟ ⎛ −××= The characteristics of the output capacitor also affect the stability of the regulation system. The MP2303 can be optimized for a wide range of capacitance and ESR values. Compensation Components MP2303 employs current mode control for easy compensation and fast transient response. The system stability and transient response are controlled through the COMP pin. COMP pin is the output of the internal transconductance error amplifier. A series capacitor-resistor combination sets a pole-zero combination to control the characteristics of the control system. The DC gain of the voltage feedback loop is given by: OUT FB VEACSLOADVDC V VAGRA ×××= Where A VEA is the error amplifier voltage gain, 400V/V; G CS is the current sense transconductance, 7.0A/V; R LOAD is the load resistor value. The system has 2 poles of importance. One is due to the compensation capacitor (C3) and the output resistor of error amplifier, and the other is due to the output capacitor and the load resistor. These poles are located at: VEA EA 1P A3C2 Gf ××π= LOAD 2P R2C2 1f ××π= Where, G EA is the error amplifier transconductance, 820µA/V, and RLOAD is the load resistor value. The system has one zero of importance, due to the compensation capacitor (C3) and the compensation resistor (R3). This zero is located at: 3R3C2 1f 1Z ××π= The system may have another zero of importance, if the output capacitor has a large capacitance and/or a high ESR value. The zero, due to the ESR and capacitance of the output capacitor, is located at: ESR ESR R2C2 1f ××π=

MP2303 – 3A, 28V, 340KHz SYNCHRONOUS RECTIFIED, STEP-DOWN CONVERTER INITIAL RELEASE – SPECIFICATIONS SUBJECT TO CHANGE MP2303 Rev. 0.91 www.MonolithicPower.com 9 3/10/2006 MPS Proprietary Information. Unaut horized Photocopy and Duplication Prohibited. © 2006 MPS. All Rights Reserved. TM In this case, a third pole set by the optional compensation capacitor (C6) and the compensation resistor (R3) is used to compensate the effect of the ESR zero on the loop gain. This pole is located at: 3R6C2 1f 3P ××π= The goal of compensation design is to shape the converter transfer function to get a desired loop gain. The system crossover frequency where the feedback loop has the unity gain is important. Lower crossover frequencies result in slower line and load transient responses, while higher crossover frequencies could cause system instability. A good rule of thumb is to set the crossover frequency to approximately one-tenth of the switching frequency. Switching frequency for the MP2303 is 340KHz, so the desired crossover frequency is 34KHz. Table 3 lists the typical values of compensation components for some standard output voltages with various output capacitors and inductors. The values of the compensation components have been optimized for fast transient responses and good stability at given conditions. Table 3—Compensation Values for Typical Output Voltage/Capacitor Combinations VOUT L C2 R3 C3 C6 1.8V 4.7µH 100µF Ceramic 5.6kΩ 5.6nF None 2.5V 4.7µH - 6.8µH 47µF Ceramic 3.65k Ω 8.2nF None 3.3V 6.8µH - 10µH 22µFx2 Ceramic 4.42kΩ 4.7nF None 5V 10µH - 15µH 22µFx2 Ceramic 6.98kΩ 3.3nF None 12V 15µH - 22µH 22µFx2 Ceramic 16.5kΩ 1.8nF None 1.8 4.7µH 100µF/100m Ω SP-CAP 8.4kΩ 2.2nF None 2.5V 4.7µH - 6.8µH 47µF SP-CAP 5.6kΩ 3.3nF None 3.3V 6.8µH - 10µH 47µF SP-CAP 6.8kΩ 2.2nF None 5V 10µH - 15µH 47µF SP CAP 10kΩ 2.2nF None 2.5V 4.7µH - 6.8µH 560µF Al. 30mΩ ESR 10kΩ 12nF 1.8nF 3.3V 6.8µH - 10µH 560µF Al 30mΩ ESR 10kΩ 10nF 1.5nF 5V 10µH - 15µH 470µF Al. 30mΩ ESR 15kΩ 8.2nF 1nF 12V 15µH - 22µH 220µF Al. 30mΩ ESR 15kΩ 10nF 390pF

MP2303 – 3A, 28V, 340KHz SYNCHRONOUS RECTIFIED, STEP-DOWN CONVERTER INITIAL RELEASE – SPECIFICATIONS SUBJECT TO CHANGE MP2303 Rev. 0.91 www.MonolithicPower.com 10 3/10/2006 MPS Proprietary Information. Unaut horized Photocopy and Duplication Prohibited. © 2006 MPS. All Rights Reserved. TM To optimize the compensation components for conditions not listed in Table 2, the following procedure can be used. 1. Choose the compensation resistor (R3) to set the desired crossover frequency. Determine the R3 value by the following equation: FB OUT CSEA C V V GG f2C23R ×× ××π= Where f C is the desired crossover frequency, 34KHz. 2. Choose the compensation capacitor (C3) to achieve the desired phase margin. For applications with typical inductor values, setting the compensation zero, f Z1, below one forth of the crossover frequency provides sufficient phase margin. Determine the C3 value by the following equation: Cf3R2 43C ××π> 3. Determine if the second compensation capacitor (C6) is required. It is required if the ESR zero of the output capacitor is located at less than half of the 340KHz switching frequency, or the following relationship is valid: f R2C2 1 S ESR <××π If this is the case, then add the optional compensation capacitor (C6) to set the pole f P3 at the location of the ESR zero. Determine the C6 value by the equation: R2C6C ESR×= Soft-Start Capacitor To reduce input inrush current during startup, a programmable soft-start is provided by connecting a capacitor (C4) from pin SS to GND. The soft-start time is given by: V8.04CtSS µ×= To reduce the susceptibility to noise, do not leave SS pin open. Use a capacitor with small value if you do not need soft-start function. External Bootstrap Diode It is recommended that an external bootstrap diode be added when the system has a 5V fixed input or the power supply generates a 5V output. This helps improve the efficiency of the regulator. The bootstrap diode can be a low cost one such as IN4148 or BAT54. MP2303 SW BS 10nF MP2303_F02 Figure 2—External Bootstrap Diode This diode is also recommended for high duty cycle operation ( IN OUT V V >65%) and high output voltage (VOUT>12V) applications.

MP2303 – 3A, 28V, 340KHz SYNCHRONOUS RECTIFIED, STEP-DOWN CONVERTER INITIAL RELEASE – SPECIFICATIONS SUBJECT TO CHANGE NOTICE: The information in this document is subject to change wi thout notice. Please contact MPS for current specifications. Users should warrant and guarantee that third party Intellectual Property rights ar e not infringed upon when integrating MPS products into any application. MPS will not assume any legal responsibility for any said applications. MP2303 Rev. 0.91 www.MonolithicPower.com 12 3/10/2006 MPS Proprietary Information. Unaut horized Photocopy and Duplication Prohibited. © 2006 MPS. All Rights Reserved. TM

PACKAGE INFORMATION

SOIC8N (EXPOSED PAD) NOTE: 1) Control dimension is in inches. Dimension in bracket is millimeters. Recommended Solder Board Area: 2.80mm x 3.82mm = 10.7mm 2 (16.6mil2) 0.016(0.410) 0.050(1.270) 0o-8o DETAIL "A" 0.011(0.280) 0.020(0.508) x 45o SEE DETAIL "A" 0.0075(0.191) 0.0098(0.249) 0.229(5.820) 0.244(6.200) SEATING PLANE 0.001(0.030) 0.004(0.101) 0.189(4.800) 0.197(5.004) 0.053(1.350) 0.068(1.730) 0.049(1.250) 0.060(1.524) 0.150(3.810) 0.157(4.000) PIN 1 IDENT. 0.050(1.270)BSC 0.013(0.330) 0.020(0.508) NOTE 2