MC44604

MC44604 ONSEMI | Alldatasheet

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Technical content

 Semiconductor Components Industries, LLC, 2000 April, 2000 – Rev. 2

1 Publication Order Number:

/C0077/C0067/C0052/C0052/C0054/C0048/C0052 /C0065/C0100/C0118/C0097/C0110/C0099/C0101 /C0073/C0110/C0102/C0111/C0114/C0109/C0097/C0116/C0105/C0111/C0110 /C0072/C0105/C0103/C0104 /C0083/C0097/C0102/C0101/C0116/C0121 /C0080/C0117/C0108/C0115/C0101/C0100 /C0077/C0111/C0100/C0101 /C0083/C0116/C0097/C0110/C0100/C0098/C0121 /C0071/C0114/C0101/C0101/C0110/C0076/C0105/C0110/C0101 /C0080/C0087/C0077 /C0067/C0111/C0110/C0116/C0114/C0111/C0108/C0108/C0101/C0114 The MC44604 is an enhanced high performance controller that is specifically designed for off–line and dc–to–dc converter applications. Its high current totem pole output is ideally suited for driving a power MOSFET. The MC44604 is an evolution of the MC44603A. Like the MC44603A, the MC44604 has been optimized to operate with universal ac mains voltage from 80 V to 280 V . It also offers enhanced safety and reliable power management thanks to its protection features (foldback, overvoltage detection, soft–start, accurate demagnetization detection). In addition, the MC44604 offers a new efficient way to reduce the standby operating power by means of a so–called pulsed mode standby operation of the converter, significantly reducing the converter consumption in standby mode. Current Mode Controller

• Operation Up to 250 kHz Output Switching Frequency
• Inherent Feed Forward Compensation
• Latching PWM for Cycle–by–Cycle Current Limiting
• Oscillator with Precise Frequency Control High Flexibility
• Externally Programmable Reference Current
• Secondary or Primary Sensing
• High Current Totem Pole Output
• Undervoltage Lockout with Hysteresis Safety/Protection Features
• Overvoltage Protection Facility Against Open Loop
• Protection Against Short Circuit on Oscillator Pin
• Fully Programmable Foldback
• Soft–Start Feature
• Accurate Maximum Duty Cycle Setting
• Demagnetization (Zero Current Detection) Protection
• Internally Trimmed Reference GreenLine Controller
• Low Start–Up and Operating Current
• Pulsed Mode Standby for Low Standby Losses
• Low dV/dT for Low EMI This document contains information on a new product. Specifications and information herein are subject to change without notice. Device Package Shipping

ORDERING INFORMATION

MC44604P PDIP–16 25 Units/Rail http://onsemi.com PDIP–16 P SUFFIX CASE 648 MARKING DIAGRAM A = Assembly Location WL, L = Wafer Lot YY, Y = Year WW, W = Work Week PIN CONNECTIONS 11 6 (Top View) VCC VC Output Overvoltage Protection Current Sense Input Demagnetization Detection Input Rref Standby Current Set Gnd Foldback Input CT Soft–Start/Dmax/ Voltage Mode Clamp Error Amp Input Error Amp Output

14 Error Amp Input

http://onsemi.com Block Diagram PWM Q Reset Set Latch Supply Error InitializationReference Block Buffer Oscillator 115 AMP Stand–by (lpk)max Programmation Current Sense Dmax & Soft–Start Control V C OUTPUT GND Overvoltage Protection (OVP) Demagnetization Detection Stand–by Management Thermal Shutdown Clamp Error Ampllifier Input C T Stand–by Management Voltage Feedback Input E/A Output Foldback Input Stand–by Current Current Sense Soft–Start MC44604 V stby V CC enable UVLO1 UVLO2 V ref V ccR ref V demag out UVLO1 UVLO2 V stby 18 V V stby iref iref Iref V stby V ref V ref Iref V CC enable

4.7 V V ref

V Dis(stby–latched) V stby Set Input (Css)/Dmax Voltage Mode Control V CC enable V CC Dis(stby–latched) Dis(stby) Dis(stby) osc prot V OSC Block V cs Foldback Demagnetization Management Overvoltage Management

http://onsemi.com MAXIMUM RATINGS Rating Pin # Symbol Value Unit Total Power Supply and Zener Current (ICC + IZ) 30 mA Output Supply Voltage with Respect to Ground 2 VC VCC 18 V Output Current* 3 mA Source IO(Source) –750 Sink IO(Sink) 750 Output Energy (Capacitive Load per Cycle) W 5.0 µJ Soft–Start 11 VSS –0.3 to 2.2 V Clamp Error Amp Input 12 VCLEA –0.3 to 4.5 V Foldback Input, Stand–by Management –0.3 to VCC + 0.3 V Overvoltage Protection, Current Sense Input, Rref, Error Amp Input, Error Amp Output, CT, Stand–by Current Set Vin –0.3 to 5.5 V Demagnetization Detection Input Current 8 mA Source Idemag–ib (Source) –4.0 Sink Idemag–ib (Sink) 10 Error Amplifier Output Sink Current 13 IE/A (Sink) 20 mA Power Dissipation and Thermal Characteristics Maximum Power Dissipation at TA = 85°C PD 0.6 W Thermal Resistance, Junction–to–Air R θJA 100 °C/W Operating Junction Temperature TJ 150 °C Operating Ambient Temperature TA –25 to +85 °C *Maximum package power dissipation must be observed. ELECTRICAL CHARACTERISTICS (VCC and VC = 12 V [Note 1.], Rref = 10 kΩ , CT = 820 pF, for typical values TA = 25°C, for min/max values TA = –25° to +85°C [Note 2.], unless otherwise noted.) Characteristic Pin # Symbol Min Typ Max Unit OUTPUT SECTION (Note 3.) Output Voltage* 3 V Low Level Drop Voltage (ISink = 100 mA) (ISink = 500 mA) VOL – 1.0 1.4 1.2 2.0 High Level Drop Voltage (ISource = 200 mA) (ISource = 500 mA) VOH – 1.5 2.0 2.0 2.7 Output Voltage During Initialization Phase 3 VOL Vgg VCC = 0 to 1.0 V, ISink = 10 µA V 1 0 t 5 0 V I 100 A OL – – 1.0 10VCC = 1.0 to 5.0 V, ISink = 100 µA VCC =50t o1 3V ISink=10m A 0.1 1.0 10VCC = 5.0 to 13 V, ISink = 1.0 mA – 0.1 1.0 Output Voltage Rising Edge Slew–Rate (CL = 1.0 nF, TJ = 25°C) 3 dVo/dT – 300 – V/µs Output Voltage Falling Edge Slew–Rate (CL = 1.0 nF, TJ = 25°C) 3 dVo/dT – –300 – V/µs ERROR AMPLIFIER SECTION Voltage Feedback Input (VE/A out = 2.5 V) 14 VFB 2.4 2.5 2.6 V Input Bias Current (VFB = 2.5 V) 14 IFB–ib –2.0 –0.6 – µA Open Loop Voltage Gain (VE/A out = 2.0 V to 4.0 V) AVOL 65 70 – dB Unity Gain Bandwidth BW MHz TJ = 25°C – – – Voltage Feedback Input Line Regulation (VCC = 10 V to 15 V) 14 VFBline–reg –10 – 10 mV *VC must be greater than 5.0 V. 1. Adjust VCC above the start–up threshold before setting to 12 V. 2. Low duty cycle pulse techniques are used during test to maintain junction temperature as close to ambient as possible.

http://onsemi.com ELECTRICAL CHARACTERISTICS (VCC and VC = 12 V [Note 1.], Rref = 10 kΩ , CT = 820 pF, for typical values TA = 25°C, for min/max values TA = –25° to +85°C [Note 2.], unless otherwise noted.) Characteristic Pin # Symbol Min Typ Max Unit ERROR AMPLIFIER SECTION (continued) Output Current 13 mA Sink (VE/A out = 1.5 V, VFB = 2.7 V) TA = –25° to +85°C ISink 2.0 12 – Source (VE/A out = 5.0 V, VFB = 2.3 V) TA = –25° to +85°C ISource –2.0 – –0.2 Output Voltage Swing 13 V Low State (IE/A out (sink) = 0.33 mA, VFB = 2.7 V) VOL – 1.0 1.1 REFERENCE SECTION Reference Output Voltage (VCC = 10 V to 15 V) 16 Vref 2.4 2.5 2.6 V Reference Current Range (Iref = Vref/Rref, R = 5.0 k to 25 kΩ ) 16 Iref –500 – –100 µA Reference Voltage Over Iref Range ΔVref –40 – 40 mV OSCILLATOR SECTION Frequency FOSC kHz TA = 0° to +70°C 40.5 46 48.5 TA = –25° to +85°C 40 – 49 Frequency Change with Voltage (VCC = 10 V to 15 V) ΔFOSC /ΔV – 0.05 – %/V Frequency Change with Temperature (TA = –25° to +85°C) ΔFOSC /ΔT – 0.05 – %/°C Oscillator Voltage Swing (Peak–to–Peak) 10 VOSC(P–P) – 2.0 – V Ratio Charge Current/Reference Current (TA = –25° to +85°C) Icharge/Iref 0.35 – 0.43 – Fixed Maximum Duty Cycle = Idischarge/(Idischarge + Icharge) D 78 80 82 % UNDERVOLTAGE LOCKOUT SECTION Start–up Threshold 1 Vstup–th 13.6 14.5 15.4 V Disable Voltage After Threshold Turn–On 1 Vdisable1 V TA = 0° to +70°C 8.6 9.0 9.4 Disable Voltage After Threshold Turn–On 1 Vdisable2 7.0 7.5 8.0 V Delta VCC During Standby (Vstup–th –Vdisable2) (TA = –25°C to 85°C)

1 Vstup–th

–Vdisable2 1.8 2.0 2.2 V DEMAGNETIZATION DETECTION SECTION Demagnetization Detect Input 8 Demagnetization Comparator Threshold (Vpin8 Decreasing) Vdemag–th 50 65 80 mV Propagation Delay (Input to Output, Low to High) – – 0.25 – µs Input Bias Current (Vdemag = 65 mV) Idemag–lb –0.5 – – µA Negative Clamp Level (Idemag = –2.0 mA) C L(neg) – –0.38 – V Positive Clamp Level (Idemag = +2.0 mA) C L(pos) – 0.72 – V SOFT–START SECTION Ratio Charge Current/Iref Iss(ch)/Iref – TA = 0° to +70°C 0.37 0.4 0.43 Discharge Current (Vsoft–start = 1.0 V) 11 Idischarge 1.5 5.0 – mA Clamp Level Vss(CL) 2.2 2.4 2.6 V Duty Cycle (Rsoft–start = 12 kΩ ) Duty Cycle (Vsoft–start (pin11) = 0.1 V) D soft–start 12k D soft–start 1. Adjust VCC above the start–up threshold before setting to 12 V. 2. Low duty cycle pulse techniques are used during test to maintain junction temperature as close to ambient as possible.

http://onsemi.com ELECTRICAL CHARACTERISTICS (VCC and VC = 12 V [Note 1.], Rref = 10 kΩ , CT = 820 pF, for typical values TA = 25°C, for min/max values TA = –25° to +85°C [Note 2.], unless otherwise noted.) Characteristic Pin # Symbol Min Typ Max Unit CURRENT SENSE SECTION Maximum Current Sense Input Threshold (VFeedback (pin14) = 2.3 V and Vfoldback (pin6) = 1.2 V) 7 Vcs–th 0.93 0.96 1.00 V Input Bias Current 7 Ics–ib –10 –2.0 – µA Propagation Delay* in Normal Mode in Standby Mode tCS–NM tCS–stby 120 120 200 200 ns *Current Sense Input to Output at VTH of MOS transistor = 3.0 V. OVERVOLTAGE SECTION Protection Threshold Level on VOVP 6 VOVP–th 2.42 2.5 2.58 V Propagation Delay (VOVP > 2.58 V to Vout Low) 1.0 – 3.0 µs Protection Level on VCC VCC prot V TA = 0° to +70°C 16.1 17 17.9 Input Resistance – kΩ TA = 0° to +70°C 1.5 2.0 3.0 FOLDBACK SECTION (Note 3.) Current Sense Voltage Threshold (Vfoldback (pin5) = 0.9 V) 5 Vcs–th 0.84 0.88 0.89 V Foldback Input Bias Current (Vfoldback (pin5) = 0 V) 5 Ifoldback–lb –6.0 –2.0 – µA CLAMP ERROR AMPLIFIER INPUT Clamp Level (@ l = 30 mA) 12 Vcl 4.5 4.7 4.9 V STANDBY PULSED MODE SECTION Standby Initialization Current Ratio (S1 closed) 15 Iinit/Iref 126 140 154 – Minimum Initialization Current Pulse Width* Tinit – – 1.0 µs Standby On Detection Current Ratio 15 Idet/Iref 0.34 0.38 0.42 – Standby Regulation Current Ratio 15 Ireg/Iref 18 20.5 23 – Standby Bias Current (S1 and S2 open;

0 V /C0116 Vpin15 /C0116 Vstup–th)**

15 Istby–ib –1.0 – 2.0 µA * This is the minimum time during which the pin 15 current must be higher than Iinit to enable the detection of the transition normal to standby mode. **Tested using VCC = 6.0 V, 9.0 V, 13.5 V, the MC44604 being off. STANDBY CURRENT SET Peak Standby Current Setting Ratio 9 – TA = 0° to +70°C Ipk–stby/Iref 0.37 0.4 0.43 Standby Current Sense Threshold Ratio* 7 Vpin9/Vcs–st 2.4 2.6 2.9 – TOTAL DEVICE Power Supply Current ICC mA Startup* – 0.3 0.45 Operating TA = –25° to +85°C (Note 2.) 16 20 24 Power Supply Zener Voltage (ICC = 25 mA) VZ 18.5 – – V Thermal Shutdown – – 155 – °C *Tested using VCC = 6.0 V, 9.0 V, 13.5 V, the MC44604 being off. 1. Adjust VCC above the start–up threshold before setting to 12 V. 2. Low duty cycle pulse techniques are used during test to maintain junction temperature as close to ambient as possible. 3. This function can be inhibited by connecting pin 5 to VCC .

http://onsemi.com Pin Name Pin Description 1 VCC This pin is the positive supply of the IC. 2 VC The output high state, VOH , is set by the voltage applied to this pin. With a separate connection to the power source, it gives the possibility to set by means of an external resistor the output source current at a different value than the sink current. 3 Output The output current capability is suited for driving a power MOSFET. A Bipolar transistor can also be driven for low power applications. The maximum on–time of the duty cycle can last up to 80% of the switching period.

4 Gnd The ground pin is a single return typically connected back to the power

source, it is used as control and power ground. 5 Foldback Input The foldback function ensures an overload protection. Feeding the foldback input with a portion of the VCC voltage (1 V max) establishes on the system control loop a foldback characteristic allowing a smoother start–up and a sharper overload protection. The foldback action performs an active current sense clamping reduction. Above 1 V the foldback input is no more active.

6 Overvoltage Protection When the overvoltage protection pin receives a voltage greater than 17 V

the device gets disabled and requires a complete restart sequence. The overvoltage level is programmable.

7 Current Sense Input A voltage proportional to the current flowing into the power switch is

connected to this input. The PWM latch uses this information to terminate the conduction of the output buffer when operating in current mode. A maximum level of 1 V allows to limit the inductor current either in current or voltage mode of operation.

8 Demagnetization Detection A voltage delivered by an auxiliary transformer winding provides to the

demagnetization pin an indication of the magnetization state of the flyback energy reservoir. A zero voltage detection corresponds to a complete core demagnetization. The demagnetization detection ensures a discontinuous mode of operation. This function can be inhibited by connecting Pin 8 to GND.

9 Standby Current Set Using an external resistor connected to this pin, the standby burst mode

peak current can be adjusted.

10 C T The normal mode oscillator frequency is programmed by the capacitor CT

choice together with the Rref resistance value. CT, connected between pin 10 and GND, generates the oscillator sawtooth.

11 Soft–Start/Dmax /Voltage–Mode A capacitor or a resistor or a voltage source connected to this pin can

temporary or permanently control the effective switching duty–cycle. This pin can be used as a voltage mode control input. By connecting pin 11 to Ground, the MC44604 can be shut down.

12 Clamp Error Amplifier Input In normal mode, the current drawn from this pin, is used by the Error

Amplifier to perform the regulation. A 4.7 V zener diode clamps the voltage of this pin. 13 E/A Out The error amplifier output is made available for loop compensation. 14 Voltage Feedback This is the inverting input of the Error Amplifier. It uses a voltage that is built up using the current drawn from the pin 12. 15 Standby Management This block is designed to detect the standby mode. It particularly determines if the circuit must work in standby or in normal mode at each start–up. For that, it uses an information given by an external arrangement consisting of an opto–coupler. In standby mode, this block makes the circuit work in the standby configuration, and the current injected in the pin 15 is used to perform the regulation. In normal mode, this pin is internally connected to the pin 12.

16 R REF The RREF values fixes the internal reference current which is used to

perform the precise oscillator waveform. The current range goes from 100 µA up to 500 µA.

Figure 24. Switching Off Behavior

Figure 25. Starting Behavior and Overvoltage

Figure 28. Error Amplifier Compensation error amplifier arrangement. during the appropriate oscillator cycle. Figure 29. Output Totem Pole

7 C R S

The oscillator is a very accurate sawtooth generator.

http://onsemi.com The Sawtooth Generation In the steady state, the oscillator voltage varies between about 1.6 V and 3.6 V . Indeed, the sawtooth is obtained by charging and discharging an external capacitor CT (Pin 10), using two distinct current sources = Icharge and Idischarge. In fact, CT is permanently connected to the charging current source (0.4 Iref) and so, the discharge current source has to be higher than the charge one to be able to decrease the CT voltage. This condition is performed, its value being (2 Iref). Two comparators are used to generate the sawtooth. They compare the CT voltage to the oscillator valley and peak values. The comparison to the low value enables to detect the end of the discharge phase while the comparison to the high value determines when the charge cycle must be stopped. A latch (LDISCH ) memorizes the oscillator state.Figure 30. Oscillator C T 1 V Vref

0.4 IREF

1.6 V Q

R S LOSC 3.6 V Q S R DISCH Vdemag out C T< 1.6 V DISCHARGE IDISCHARGE Now, in addition to the charge and discharge cycles, a third state can exist. This phase can be produced when at the end of the discharge phase, the oscillator has to wait for a demagnetization pulse before re–starting. During this delay, the CT voltage must remain equal to the oscillator valley value (/C00881.6 V). So, a third regulated current source IREGUL controlled by COSC REGUL , is connected to CT in order to perfectly compensate the (0.4 Iref) current source that permanently supplies CT. On–time is only allowed during the oscillator capacitor charge. So, the maximum duty cycle is 80%. (Note 1) The demagnetization condition is taken into account by a second latch (Losc). (Refer to demagnetization § for further details.) Oscillator Frequency The oscillator frequency can be deducted using the following equations: Tcharge/C0043C T • /C0068V /C0324Icharge Tdischarge/C0043C T • /C0068V/C0324Idischarge where: Tcharge is the oscillator charge time /C0068V is the oscillator peak to peak value Icharge is the oscillator charge current and Tdischarge is the oscillator discharge time Idischarge is the oscillator discharge current So, as: fosc = 1 /(Tcharge + T discharge) if the REGUL arrangement is not activated, the following equation can be obtained: fosc /C00880·395 Rref• C T Demagnetization Block (Note 2) To enable the output, the Losc latch complementary output must be low. Now, this latch reset is activated by the LDISCH output during the discharge phase. So, to restart, the Losc has to be set (refer to Figure 30). To perform this, the demagnetization signal must be low. In a fly–back, a good means to detect the demagnetization consists in using the VCC winding voltage. Indeed this voltage is: — negative during the on–time, — positive during the off–time, — equal to zero for the dead–time with generally a ringing (refer to Figure 31). That is why, the MC44604 demagnetization detection consists of a comparator that can compare the VCC winding voltage to a reference that is typically equal to 65 mV . Note 1. The output is disabled by the signal Vosc prot when VCT is lower than 1 V . (Refer to Figure 29 and Figure 30.) Note 2. The demagnetization detection can be inhibited by connecting pin 8 to the ground.

Figure 31. Demagnetization Detection level is sufficient to avoid the substrate diode switching on. very accurate demagnetization detection. demagnetization phase (refer to Figure 29). Figure 32. Demagnetization Block Figure 33. Dmax and Soft–Start Block Diagram Figure 34. Maximum Duty Cycle Control when a resistor is connected). start–up phase and thus, to perform a soft–start.

has started to allow the reference Vref to stabilize. Figure 38. VCC Management

7.5 V or

before allowing operation of the system. sources required by the system. capacitor as the soft–start pin is maintained short circuited). V disable1) and so the minimum hysteresis is 4.2 V . to drastically reduce the power consumption. flyback configuration as depicted in Figure 39. Figure 39. Standby Flyback Configuration level, Vstby is the standby µP supply voltage. drastically reduced by a ratio in the range of 10. eliminated, without having to disconnect the loads. is performed at each start–up.

http://onsemi.com Application Schematic RFI Filter

185 Vac

270 Vac

D1 ... D4 1N4007 CS 1nF11kV 2.5 kΩ VCC 117.5 kΩ 4.7 kΩ 4.7 kΩ 150 Ω MC44604P C4....C7 100 nF MTP6N60E Laux RS

4.7 MΩ1 nF/1000 V

1 Ω 15 W /C0109P Lp 100 /C0109F

68 K/C0087

(2W) 100 /C0109F VCC C16 100 pF 27 k/C0087R19 10 k/C0087 C9 1 nF C10 1/C0109F R15 1 k/C008722 k/C0087 C11 1/C0109F R16 k/C0087 R19 10 k/C0087 C13 100 nF R11 100 /C0087 R26 20 /C0087 R8 15 k/C0087 R9 180 k/C0087 C14 4.7 nF R14 0.47 /C0087 (1W) R13 1 k/C0087 (5W) MR856 C18 2.2 nF MR856 220 pF MR856 100 pF 0.1 /C0109F 120/0.5 A 47 k 120 pF 1N4148 1N4937 MCR22–6 220 pF 220 pF 220 pF 28V/1A 100 /C0109F 0.1 /C0109F 15V/1A 1000 /C0109F 0.1 /C0109F MR856 MR852 4700 /C0109F 0.1 /C0109F MR852 4.7 kΩ 270 Ω22 Ω TL431 8.2 k 47 Ω 100 nF BC237B BC237B 220 kΩ 8V/1A 1 kΩ BC237B MOC8104 1 /C0109H1N4148 1.2 k1 nF 1 k/C0087 12 V 22 k/C0087 (5W) 47 nF 1N4148 4.7 k

http://onsemi.com Notes

http://onsemi.com Notes

http://onsemi.com PACKAGE DIMENSIONS PDIP–16 P SUFFIX CASE 648–08 ISSUE R NOTES: 1. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. 2. CONTROLLING DIMENSION: INCH. 3. DIMENSION L TO CENTER OF LEADS WHEN FORMED PARALLEL. 4. DIMENSION B DOES NOT INCLUDE MOLD FLASH. 5. ROUNDED CORNERS OPTIONAL. –A– B F C S H G D J L M 16 PL SEATING 916 K PLANE–T– MAM0.25 (0.010) T DIM MIN MAX MIN MAX MILLIMETERSINCHES A 0.740 0.770 18.80 19.55 B 0.250 0.270 6.35 6.85 C 0.145 0.175 3.69 4.44 D 0.015 0.021 0.39 0.53 F 0.040 0.70 1.02 1.77 G 0.100 BSC 2.54 BSC H 0.050 BSC 1.27 BSC J 0.008 0.015 0.21 0.38 K 0.110 0.130 2.80 3.30 L 0.295 0.305 7.50 7.74 M 0 10 0 10 S 0.020 0.040 0.51 1.01 /C0095/C0095/C0095/C0095 ON Semiconductor and are trademarks of Semiconductor Components Industries, LLC (SCILLC). SCILLC reserves the right to make changes without further notice to any products herein. SCILLC makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does SCILLC assume any liability arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation special, consequential or incidental damages. “Typical” parameters which may be provided in SCILLC data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including “Typicals” must be validated for each customer application by customer’s technical experts. SCILLC does not convey any license under its patent rights nor the rights of others. SCILLC products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other applications intended to support or sustain life, or for any other application in which the failure of the SCILLC product could create a situation where personal injury or death may occur. Should Buyer purchase or use SCILLC products for any such unintended or unauthorized application, Buyer shall indemnify and hold SCILLC and its officers, employees, subsidiaries, affiliates, and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges that SCILLC was negligent regarding the design or manufacture of the part. SCILLC is an Equal Opportunity/Affirmative Action Employer. PUBLICATION ORDERING INFORMATION CENTRAL/SOUTH AMERICA: Spanish Phone: 303–308–7143 (Mon–Fri 8:00am to 5:00pm MST) Email: ONlit–spanish@hibbertco.com ASIA/PACIFIC: LDC for ON Semiconductor – Asia Support Phone : 303–675–2121 (Tue–Fri 9:00am to 1:00pm, Hong Kong Time) Toll Free from Hong Kong & Singapore: 001–800–4422–3781 Email: ONlit–asia@hibbertco.com JAPAN : ON Semiconductor, Japan Customer Focus Center 4–32–1 Nishi–Gotanda, Shinagawa–ku, Tokyo, Japan 141–0031 Phone : 81–3–5740–2745 Email: r14525@onsemi.com ON Semiconductor Website: http://onsemi.com For additional information, please contact your local Sales Representative. MC44604/D NORTH AMERICA Literature Fulfillment: Literature Distribution Center for ON Semiconductor P.O. Box 5163, Denver, Colorado 80217 USA Phone : 303–675–2175 or 800–344–3860 Toll Free USA/Canada Fax: 303–675–2176 or 800–344–3867 Toll Free USA/Canada Email: ONlit@hibbertco.com Fax Response Line: 303–675–2167 or 800–344–3810 Toll Free USA/Canada N. American Technical Support: 800–282–9855 Toll Free USA/Canada EUROPE: LDC for ON Semiconductor – European Support German Phone : (+1) 303–308–7140 (M–F 1:00pm to 5:00pm Munich Time) Email: ONlit–german@hibbertco.com French Phone : (+1) 303–308–7141 (M–F 1:00pm to 5:00pm Toulouse Time) Email: ONlit–french@hibbertco.com English Phone: (+1) 303–308–7142 (M–F 12:00pm to 5:00pm UK Time) Email: ONlit@hibbertco.com EUROPEAN TOLL–FREE ACCESS*: 00–800–4422–3781 *Available from Germany, France, Italy, England, Ireland GreenLine is a trademark of Motorola, Inc.