MC13142

MC13142 MOTOROLA | Alldatasheet

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/C0077/C0067/C0049/C0051/C0049/C0052/C0050 SEMICONDUCTOR TECHNICAL DATA LOW POWER DC – 1.8 GHz LNA, MIXER and VCO Order this document By MC13142/D D SUFFIX PLASTIC PACKAGE CASE 751B (SO–16) Device Operating Temperature Range Package

ORDERING INFORMATION

MC13142D T A = –40° to +85°C SO–16 1MOTOROLA RF/IF DEVICE DATA /C0065/C0100/C0118/C0097/C0110/C0099/C0101 /C0073/C0110/C0102/C0111/C0114/C0109/C0097/C0116/C0105/C0111/C0110 /C0076/C0111/C0119 /C0080/C0111/C0119/C0101/C0114 /C0068/C0067 /C0045 /C0049/C0046/C0056 /C0071/C0072/C0122 /C0076/C0078/C0065/C0044 /C0077/C0105/C0120/C0101/C0114 /C0097/C0110/C0100 /C0086/C0067/C0079 The MC13142 is intended to be used as a first amplifier, voltage controlled oscillator and down converter for RF applications. It features wide band operation, low noise, high gain and high linearity while maintaining low current consumption. The circuit consists of a Low Noise Amplifier (LNA), a Voltage Controlled Oscillator (VCO), a buffered oscillator output, a mixer, an Intermediate Frequency amplifier (IFamp ) and a dc control section. The wide mixer IF bandwidth allows this part also to be used as an up converter and exciter amplifier.

• Wide RF Bandwidth: DC–1.8 GHz
• Wide LO Bandwidth: DC–1.8 GHz
• Wide IF Bandwidth: DC–1.8 GHz
• Low Power: 13 mA @ VCC = 2.7 – 6.5 V
• High Mixer Linearity: Pi1.0 dB = 3.0 dBm
• Linearity Adjustment Increases IP3in Up to 20 dBm
• Single–Ended 50 Ω Mixer Input
• Double Balanced Mixer Operation
• Open Collector Mixer Output
• Single Transistor Oscillator with Collector, Base and Emitter Pinned Out
• Buffered Oscillator Output PIN CONNECTIONS EN VEE 14 VEE SO–16 RF in Osc E Osc C, VCC Osc B Buff IF– IF+ RF m Mix Lin Cont VCC RF out

9 VEEVCC

This device contains 176 active transistors. This document contains information on a new product. Specifications and information herein are subject to change without notice.  Motorola, Inc. 1998 Rev 1

2 MOTOROLA RF/IF DEVICE DATA

MAXIMUM RATINGS (TA = 25°C, unless otherwise noted.) Rating Symbol Value Unit Power Supply Voltage VCC(max) 7.0 Vdc Operating Supply Voltage Range VCC 2.7 to 6.5 Vdc NOTE: ESD data available upon request. ELECTRICAL CHARACTERISTICS (VCC = 3.0 V, TA = 25°C, LOin = –10 dBm @ 950 MHz, IF @ 50 MHz.) Characteristic Symbol Min Typ Max Unit Supply Current (Disable) ICC_Total –230 – 230 APin 15 with Pin 1 @ 0 V ICC_15 –110 – 110 µAPin 10 and 11 with Pin 1 @ 0 V ICC_Mix –20 – 20 µA Pin 6 with Pin 1 @ 0 V ICC_6 –100 – 100 Supply Current (Enable) ICC_Total 8.25 13.5 26 Pin 6 with Pin 1 @ 3.0 V ICC_6 6.0 – 14 Amplifier Gain (50 Ω Insertion Gain) S21 6.5 12 13 dB Amplifier Reverse Isolation S12 – –33 – dB Amplifier Input Match Γin amp – –10 – dB Amplifier Output Match Γout amp – –15 – dB Amplifier 1.0 dB Gain Compression Pin–1.0 dB –18 –15 –8.0 dBm Amplifier Input Third Order Intercept IP3in – –5.0 – dBm Amplifier Noise Figure (Application Circuit) NF 1.0 1.8 4.0 dB Amplifier Gain @ N.F. G NF – 17 – dB Mixer Voltage Conversion Gain (RP = RL = 800 Ω) VG C – 9.0 – dB Mixer Power Conversion Gain (RP = RL = 800 Ω ) PG C –7.0 –3.0 –2.0 dB Mixer Input Match Γin M – –20 – dB Mixer SSB Noise Figure NF SSBM – 12 – dB Mixer 1.0 dB Gain Compression Pin–1.0 dBM – 3.0 – dBm Mixer Input Third Order Intercept IP3InM – –1.0 – dBm Oscillator Buffer Drive (50 Ω ) PVCO –19.5 –16 –12 dBm Oscillator Phase Noise @ 25 kHz Offset N Φ – –90 – dBc/Hz RF in Feedthrough to RFm PRFin–RFm – –35 – dB RF out Feedthrough to RFm PRFout–RFm – –35 – dB LO Feedthrough to IF PLO–IF – –35 – dBm LO Feedthrough to RFin PLO–RFin – –35 – dBm LO Feedthrough to RFm PLO–RFm – –35 – dBm Mixer RF Feedthrough to IF PRFm–IF – –25 – dB Mixer RF Feedthrough to RFin PRFm–RFin – –25 – dB

3MOTOROLA RF/IF DEVICE DATA CIRCUIT DESCRIPTION General The MC13142 is a low power LNA, double–balanced Mixer, and VCO. This device is designated for use as the frontend section in analog and digital FM systems such as Digital European Cordless Telephone (DECT), PHS, PCS, Cellular, UHF and 800 MHz Special Mobile Radio (SMR), UHF Family Radio Services and 902 to 928 MHz cordless telephones. It features a mixer linearity control to preset or auto program the mixer dynamic range, an enable function and a wideband IF so the IC may be used either as a down converter or an up converter. Further details are covered in the Pin by Pin Description which shows the equivalent internal circuit and external circuit requirements. Current Regulation/Enable Temperature compensating voltage independent current regulators are controlled by the enable function in which “high” powers up the IC. Low Noise Amplifier (LNA) The LNA is internally biased at low supply current (approximately 2.0 mA emitter current) for optimal noise figure and gain. The LNA output is biased internally with a 600 Ω resistor to VCC . Input and output matching may be achieved at various frequencies using few external components. Matching the LNA for Maximum stable gain (MSG) yields noise performance within a few tenths of a dB of the minimum noise figure. Mixer The mixer is a double–balanced four quadrant multiplier biased class AB allowing for programmable linearity control via an external current source. An input third order intercept point of 20 dBm may be achieved. All 3 ports of the mixer are designed to work up to 1.8 GHz. The mixer has a 50 Ω single–ended RF input and open collector differential IF outputs. An on–board Local Oscillator transistor has the emitter, base and collector pinned out to implement a low phase noise VCO in various configurations. Additionally, a buffered LO output is provided for operation with a frequency synthesizer. The linear gain of the mixer is approximately 0 dB with a SSB noise figure of 12 dB in the IF output circuit configuration shown in the application example. Local Oscillator The on–chip transistor operates with coaxial transmission line or LC resonant elements to over 2.0 GHz. Biasing is done with a temperature compensated current source in the emitter and a collector to base internal resistor of 7.6 kΩ ; however, an RFC from VCC to base is recommended. The application circuit shows a voltage controlled Clapp oscillator operating at center frequency of 975 MHz.

4 MOTOROLA RF/IF DEVICE DATA

16 Pin

Equivalent Internal Circuit (20 Pin LQFP) Description ÁÁÁÁÁ Á ÁÁÁ Á Á ÁÁÁ Á Á ÁÁÁ Á Á ÁÁÁ Á Á ÁÁÁ Á Á ÁÁÁ Á Á ÁÁÁ Á Á ÁÁÁ Á Á ÁÁÁ Á Á ÁÁÁ Á ÁÁÁÁÁ ÁÁÁÁ Á ÁÁ Á Á ÁÁ Á Á ÁÁ Á Á ÁÁ Á Á ÁÁ Á Á ÁÁ Á Á ÁÁ Á Á ÁÁ Á Á ÁÁ Á Á ÁÁ Á ÁÁÁÁ EN VCC VCC

2.0 VBE

ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Enable, E Osc In SO–16, both enables, (for the Oscillator/LO Buffer and LNA/Mixer) are bonded to Pin 1. Enable by pulling up to VCC or to greater than 2.0 VBE . ÁÁÁÁÁ Á ÁÁÁ Á Á ÁÁÁ Á ÁÁÁÁÁ ÁÁÁÁ Á ÁÁ Á Á ÁÁ Á ÁÁÁÁ RF in VCC RF out Vref2 600 ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ RF Input The input is the base of an NPN low noise amplifier. Minimum external matching is required to optimize the input return loss and gain. ÁÁÁÁÁ Á ÁÁÁ Á Á ÁÁÁ Á Á ÁÁÁ Á ÁÁÁÁÁ ÁÁÁÁ Á ÁÁ Á Á ÁÁ Á Á ÁÁ Á ÁÁÁÁ VEE RF out RF VEE Vref3 Vref2 ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ VEE – Negative Supply VEE pin is taken to an ample dc ground plane through a low impedance path. The path should be kept as short as possible. A two sided PCB is implemented so that ground returns can be easily made through via holes. ÁÁÁÁÁ Á ÁÁÁ Á Á ÁÁÁ Á ÁÁÁÁÁ ÁÁÁÁ Á ÁÁ Á Á ÁÁ Á ÁÁÁÁ RF out RF in VEE 2.0 mA ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ RF Output The output is from the collector of the LNA; it is internally biased with a 600 Ω resistor to VCC . As shown in the 926 MHz application receiver the output is conjugately matched with a shunt L, and series L and C network. ÁÁÁÁÁ Á ÁÁÁ Á Á ÁÁÁ Á Á ÁÁÁ Á Á ÁÁÁ Á Á ÁÁÁ Á Á ÁÁÁ Á ÁÁÁÁÁ ÁÁÁÁ Á ÁÁ Á Á ÁÁ Á Á ÁÁ Á Á ÁÁ Á Á ÁÁ Á Á ÁÁ Á ÁÁÁÁ Osc E Osc B Osc C Osc C Osc B Osc E 1.5 mA VEE 7.6 k ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ On–Board VCO Transistor The transistor has the emitter, base and collector + VCC pins available. Internal biasing which is compensated for stability over temperature is provided. It is recommended that the base pin is pulled up to VCC through an RFC chosen for the particular oscillator center frequency. The application circuit shows a modified Colpitts or Clapp oscillator configuration and its design is discussed in detail in the application section. ÁÁÁÁÁ Á ÁÁÁ Á Á ÁÁÁ Á Á ÁÁÁ Á Á ÁÁÁ Á Á ÁÁÁ Á ÁÁÁÁÁ ÁÁÁÁ Á ÁÁ Á Á ÁÁ Á Á ÁÁ Á Á ÁÁ Á Á ÁÁ Á ÁÁÁÁ VCC VCC Osc C VCC VEE LO Buf VCC ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Supply Voltage (VCC ) Two VCC pins are provided for the Local Oscillator and LO Buffer Amplifier. The operating supply voltage range is from 2.7 Vdc to 6.5 Vdc. In the PCB layout, the VCC trace must be kept as wide as feasible to minimize inductive reactances along the trace. VCC should be decoupled to VEE at the IC pin as shown in the component placement view. ÁÁÁÁÁ Á ÁÁÁ Á Á ÁÁÁ Á Á ÁÁÁ Á Á ÁÁÁ Á ÁÁÁÁÁ ÁÁÁÁ Á ÁÁ Á Á ÁÁ Á Á ÁÁ Á Á ÁÁ Á ÁÁÁÁ LO Buff VEE LO Buf VCC 1.0 mA ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Local Oscillator Buffer This is a buffered output providing –16 dBm (50 Ω termination) to drive the fin pin of a PLL synthesizer. Impedance matching to the synthesizer may be necessary to deliver the optimal signal and to improve the phase noise performance of the VCO.

5MOTOROLA RF/IF DEVICE DATA PIN FUNCTION DESCRIPTION (continued) Pin

Description

Equivalent Internal Circuit (20 Pin LQFP)Symbol Equivalent Internal Circuit (20 Pin LQFP)Symbol ÁÁÁÁÁ Á ÁÁÁ Á Á ÁÁÁ Á Á ÁÁÁ Á ÁÁÁÁÁ 9, 12 ÁÁÁÁ Á ÁÁ Á Á ÁÁ Á Á ÁÁ Á ÁÁÁÁ VEE VCC VCC IF– VEE ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ VEE , Negative Supply These pins are VEE supply for the mixer IF output. In the application PC board these pins are tied to a common VEE trace with other VEE pins. ÁÁÁÁÁ Á ÁÁÁ Á Á ÁÁÁ Á Á ÁÁÁ Á Á ÁÁÁ Á Á ÁÁÁ Á ÁÁÁÁÁ 10, 11 ÁÁÁÁ Á ÁÁ Á Á ÁÁ Á Á ÁÁ Á Á ÁÁ Á Á ÁÁ Á ÁÁÁÁ IF–, IF+ IF+ VEE ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ IF Output The IF is a differential open collector configuration which designed to use over a wide frequency range for up conversion as well as down conversion. Differential to single–ended circuit configuration and matching options are discussed in the application section. 6.0 dB of additional Mixer gain can be achieved by conjugately matching at the desired IF frequency. ÁÁÁÁÁ Á ÁÁÁ Á Á ÁÁÁ Á Á ÁÁÁ Á Á ÁÁÁ Á Á ÁÁÁ Á Á ÁÁÁ Á ÁÁÁÁÁ ÁÁÁÁ Á ÁÁ Á Á ÁÁ Á Á ÁÁ Á Á ÁÁ Á Á ÁÁ Á Á ÁÁ Á ÁÁÁÁ RF m VCC Vref1 VEE ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Mixer RF Input The mixer input impedance is broadband 50 Ω for applications up to 1.8 GHz. It easily interfaces with a RF ceramic filter as shown in the application schematic. ÁÁÁÁÁ Á ÁÁÁ Á Á ÁÁÁ Á Á ÁÁÁ Á Á ÁÁÁ Á Á ÁÁÁ Á Á ÁÁÁ Á Á ÁÁÁ Á Á ÁÁÁ Á ÁÁÁÁÁ ÁÁÁÁ Á ÁÁ Á Á ÁÁ Á Á ÁÁ Á Á ÁÁ Á Á ÁÁ Á Á ÁÁ Á Á ÁÁ Á Á ÁÁ Á ÁÁÁÁ Mix Lin Cont 14 Mix Lin Cont RF m 400 µA ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á Á ÁÁÁÁÁÁÁÁÁÁÁÁÁ Á ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ Mixer Linearity Control The mixer linearity control circuit accepts approximately 0 to 2.3 mA control current to set the dynamic range of the mixer. An Input Third Order Intercept Point, IIP3 of 20 dBm may be achieved at 2.3 mA of control current (approximately 7.0 mA of additional supply current).

15 VCC

VCC , Power Supply

6 MOTOROLA RF/IF DEVICE DATA

used across the entire useful frequency range of this device. circuit side (see Circuit Side Component Placement View). Figure 1. Application Circuit NOTE: *50 Ω Microstrip Transmission Line; length shown in Figure 2.

Figure 2. 900 MHz Circuit Side Component Placement View In the component placement shown above, the 926.5 MHz dielectric type image filter is used (Toko Part # 4DFA–926A10). handset frequencies. Recommended manufacturers are Siemens and Murata. VEE ground. The PCB is modified as shown to do this. 16:1 broadband impedance transformer is mini circuits part #TX16–R3T; it is in the leadless surface mount “TX” package.

8 MOTOROLA RF/IF DEVICE DATA

selected based on cost, size and performance tradeoffs. is 14 dB with a 3.3 dB noise figure. Figure 3. Frontend Subsystem Block Diagram for Noise Analysis

Figure 4. Circuit Side View NOTES: Critical dimensions are 50 mil centers lead to lead in SO–16 footprint. Also line widths to labeled ports excluding VCC are 50 mil (0.050 inch).

10 MOTOROLA RF/IF DEVICE DATA

Figure 5. Ground Side View

1.9 GHz FRONT–END FOR WIRELESS SYSTEMS

same basic performance characteristic as the test circuit. reflects about a 200 Ω source impedance to the device. with some added shunt. A 2.4 pF with Toko 4DFA 2 pole filter. LNA output and has little effect on tuning. surface such as a ground plane. could replace the resistor at a somewhat increased cost.

11MOTOROLA RF/IF DEVICE DATA current sources to the Cell and can be programmed (via Pin 15) for more current. The current is often adjusted for minimum third order response. In this Fixture it is fixed biased for most conversion gain. The Mixer circuit is balanced where both oscillator and RF are suppressed. This provides IF signals at Pins 9 and 10 which are equal in amplitude and 180 degrees out of phase. To realize a positive gain one needs to reflect a higher impedance from the load impedance (50 Ω for this fixture) to the Mixer output or outputs. Maximum signal transfer would require a balance to unbalance network. Center tapped tuned transformers can perform this function but are quite expensive. If one can afford 3.0 dB less signal, a simple LC circuit at one of the outputs will work well. The other output is unused and bypassed to ground. The most gain is realized when no shunt capacity is added and L4 is selected to resonate with the terminal capacity. Adding shunt capacity will lower the gain and increase the circuit’s bandwidth. A small value series capacitor C4 to the 50 Ω output will control the reflected impedance and complete the circuit. L4 and C4 will vary in value depending on the IF frequency. VCO The base of the device is the source for driving both the Gilbert cell and prescaler buffer stages. Because of this, the oscillator device will operate and drive the Mixer only in the grounded collector configuration. Additional dc bias is added through a 1.3 kΩ resistor (tapped for minimum VCO loading) to reduce the off–set between base and supply. The external circuit is a modified Colpitts where the capacitance between base and emitter (Pins 4 and 5), along with a capacitor from emitter to ac ground, forms the circuit capacity and the feedback that sustains oscillations. The effective circuit inductance (looking from the top of the circuit, the transistor base) consist of L3 in series with varactor diode D1 and a blocking capacitor. This circuit must appear inductive for the VCO to operate properly. If the capacity is too small, the feedback ratio is reduced and the VCO can cease oscillating. When it becomes to large, it will not vary the frequency due to the limiting effect of the series loop capacitance. In this application, the VCO is not required to cover a large tuning range. Limiting the tuning range to no more than is required to cover the band (making allowance for temperature and aging effects) will result in a VCO less susceptible to on board noise sources. To assure oscillation while controlling the tuning range the varactor (plus series capacitor) minimum capacity is chosen to be about equal to the capacity from Pin 5 (transistor base) to RF ground. The maximum tuning ratio could be no greater than 1.41 because the circuit capacity could only double whatever the upper value capacity the varactor attained. An upper limit on the varactor capacity along with the effects of the series capacitor reduces the VCO tuning range to about 1.2 times. The varactors chosen for the test fixtures were Loral KV2111. The VCO buffer, as most emitter follower circuits, has the potential of generating a parasitic oscillation. When a collector is RF bypassed, a tuned LC circuit is formed consisting of the bypass capacitor, bond wire plus package pin inductance and the device effective output capacity. If the base is low impedance, there is normally enough distributive collector to emitter capacity for the device to oscillate in the common base mode. A simple fix without affecting the buffer otherwise, is to place a small value series resistor in the collector lead. This will lower the Q of the circuit where it cannot sustain oscillations. Without the series resistor at Pin 8 or some other damping element, the buffer will oscillate. PLL A phase lock loop is added to the test board to evaluate the VCO. The MC12179 multiplies the crystal reference frequency by 256 to obtain lock. In a frequency agile system, the MC12210 would control the VCO and its reference derived from a crystal. The crystal frequency would be selected to coincide with the required VCO frequencies and channels spacing requirements. Expected Performance As stated earlier, the MC13142 performance in any of the systems should mirror the performance obtained in the test fixture. Fixture power gains of 15 dBm and noise figures of 5.5 dB are typical. The Mixer current can be varied to enhances battery life as well as alter its output characteristic for peak performance of a desired or undesired response.

12 MOTOROLA RF/IF DEVICE DATA

Figure 6. 1.9 GHz Circuit Component Placement View

Figure 7. 1.9 GHz Application Circuit

14 MOTOROLA RF/IF DEVICE DATA

CASE 751B–05 (SO–16) ISSUE J OUTLINE DIMENSIONS NOTES: 1. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. 2. CONTROLLING DIMENSION: MILLIMETER. 3. DIMENSIONS A AND B DO NOT INCLUDE MOLD PROTRUSION. 4. MAXIMUM MOLD PROTRUSION 0.15 (0.006) PER SIDE. 5. DIMENSION D DOES NOT INCLUDE DAMBAR PROTRUSION. ALLOWABLE DAMBAR PROTRUSION SHALL BE 0.127 (0.005) TOTAL IN EXCESS OF THE D DIMENSION AT MAXIMUM MATERIAL CONDITION. 16 9 SEATING PLANE F JM R X 45/C0095 G

8 PLP–B–

–A– M0.25 (0.010) B S –T– D K C 16 PL SBM0.25 (0.010) A ST DIM MIN MAX MIN MAX INCHESMILLIMETERS A 9.80 10.00 0.386 0.393 B 3.80 4.00 0.150 0.157 C 1.35 1.75 0.054 0.068 D 0.35 0.49 0.014 0.019 F 0.40 1.25 0.016 0.049 G 1.27 BSC 0.050 BSC J 0.19 0.25 0.008 0.009 K 0.10 0.25 0.004 0.009 M 0 7 0 7 P 5.80 6.20 0.229 0.244 R 0.25 0.50 0.010 0.019 /C0095/C0095/C0095/C0095

15MOTOROLA RF/IF DEVICE DATA Motorola reserves the right to make changes without further notice to any products herein. Motorola makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does Motorola assume any liability arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation consequential or incidental damages. “Typical” parameters which may be provided in Motorola data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including “Typicals” must be validated for each customer application by customer’s technical experts. Motorola does not convey any license under its patent rights nor the rights of others. Motorola products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other applications intended to support or sustain life, or for any other application in which the failure of the Motorola product could create a situation where personal injury or death may occur. Should Buyer purchase or use Motorola products for any such unintended or unauthorized application, Buyer shall indemnify and hold Motorola and its officers, employees, subsidiaries, affiliates, and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges that Motorola was negligent regarding the design or manufacture of the part. Motorola and are registered trademarks of Motorola, Inc. Motorola, Inc. is an Equal Opportunity/Affirmative Action Employer.

16 MOTOROLA RF/IF DEVICE DATA

Mfax is a trademark of Motorola, Inc. How to reach us: USA / EUROPE / Locations Not Listed: Motorola Literature Distribution;JAPAN : Nippon Motorola Ltd.: SPD, Strategic Planning Office, 141, P.O. Box 5405, Denver, Colorado 80217. 1–303–675–2140 or 1–800–441–2447 4–32–1 Nishi–Gotanda, Shagawa–ku, Tokyo, Japan. 03–5487–8488 Customer Focus Center: 1–800–521–6274 Motorola Fax Back System – US & Canada ONLY 1–800–774–1848 51 Ting Kok Road, Tai Po, N.T., Hong Kong. 852–26629298 – http://sps.motorola.com/mfax/ HOME PAGE : http://motorola.com/sps/ MC13142/D◊