LT1111-12

LT1111 LINER | Alldatasheet

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22µH LT1111 • TA01 µ MBRS120T3 100mA GND SW2 SW1 LIMI INV LT1111CS8-5 SENSE 3V INPUT

10 F*µ

*OPTIONAL Micropower DC/DC Converter Adjustable and Fixed 5V, 12V All Surface Mount 3V to 5V Step-Up Converter D UESCRIPTIOSFEATURE USA OPPLICATI Typical Load Regulation LOAD CURRENT (mA) OUTPUT VOLTAGE (V) 50 100 150 200 LT1111 • TA02 25 75 125 175 VIN = 2V 2.2 2.4 2.6 2.8 3V n Operates at Supply Voltages from 2V to 30V n 72kHz Oscillator n Works with Surface Mount Inductors n Only Three External Components Required n Step-Up or Step-Down Mode n Low-Battery Detector Comparator On-Chip n User Adjustable Current Limit n Internal 1A Power Switch n Fixed or Adjustable Output Voltage Versions n Space Saving 8-Pin MiniDIP or SO-8 Package n 3V to 5V, 5V to 12V Converters n 9V to 5V, 12V to 5V Converters n Remote Controls n Peripherals and Add-On Cards n Battery Backup Supplies n Uninterruptible Supplies n Laptop and Palmtop Computers n Cellular Telephones n Portable Instruments n Flash Memory VPP Generators UA OPPLICATITYPICAL The LT1111 is a versatile micropower DC/DC converter. The device requires only three external components to deliver a fixed output of 5V or 12V. Supply voltage ranges from 2V to 12V in step-up mode and to 30V in step-down mode. The LT1111 functions equally well in step-up, step- down, or inverting applications. The LT1111 oscillator is set at 72kHz, optimizing the device to work with off-the-shelf surface mount inductors. The device can deliver 5V at 100mA from a 3V input in step-up mode or 5V at 200mA from a 12V input in step- down mode. Switch current limit can be programmed with a single resistor. An auxiliary open-collector gain block can be configured as a low-battery detector, linear post regulator, undervoltage lock-out circuit, or error amplifier. For input sources of less than 2V use the LT1110.

A UGWA WU WARBSOLUTEX I T I S Operating Temperature Range WU UPACKAGE/ORDER I FOR ATIO TJMAX = 150°C, θJA = 120°C/W (J) TJMAX = 90°C, θJA = 130°C/W (N) ORDER PART NUMBER LT1111CN8 LT1111CN8-5 LT1111CN8-12 LT1111MJ8 LT1111MJ8-5 LT1111MJ8-12 TOP VIEW ILIM VIN SW1 SW2 FB (SENSE)* SET GND N8 PACKAGE 8-LEAD PLASTIC DIP *FIXED VERSIONS J8 PACKAGE 8-LEAD CERAMIC DIP LT1111CS8 LT1111CS8-5 LT1111CS8-12 TJMAX = 90°C, θJA = 150°C/W ORDER PART NUMBER 1111 11115 11111 S8 PART MARKING SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS IQ Quiescent Current Switch OFF 300 400 µA VIN Input Voltage Step-Up Mode l 2.0 12.6 V Step-Down Mode l 30.0 V Comparator Trip Point Voltage LT1111 (Note 1) l 1.20 1.25 1.30 V VOUT Output Sense Voltage LT1111-5 (Note 2) l 4.75 5.00 5.25 V LT1111-12 (Note 2) l 11.40 12.00 12.60 V Comparator Hysteresis LT1111 l 8 12.5 mV Output Hysteresis LT1111-5 l 32 50 mV LT1111-12 l 75 120 mV fOSC Oscillator Frequency 54 72 88 kHz DC Duty Cycle: Step-Up Mode Full Load 43 50 59 % Step-Down Mode 24 34 50 % tON Switch ON Time: Step-Up Mode I LIM Tied to VIN 579 µs Step-Down Mode V OUT, = 5V, VIN = 12V 3.3 5 7.8 µs VSAT SW Saturation Voltage, Step-Up Mode V IN = 3.0V, ISW = 650mA 0.5 0.65 V VIN = 5.0V, ISW = 1A 0.8 1.0 V SW Saturation Voltage, Step-Down Mode V IN = 12V, ISW = 650mA 1.1 1.5 V IFB Feedback Pin Bias Current LT1111, V FB = 0V l 70 120 nA ISET Set Pin Bias Current V SET = VREF l 70 300 nA VOL Gain Block Output Low I SINK = 300µA, VSET = 1.00V l 0.15 0.4 V ELECTRICAL C CHARA TERISTICS VIN = 3V, Military or Commercial Version Consult factory for Industrial grade parts TOP VIEW FB (SENSE)* SET GND I LIM VIN SW1 SW2 S8 PACKAGE 8-LEAD PLASTIC SO *FIXED VERSION

ELECTRICAL C CHARA TERISTICS VIN = 3V, Military or Commercial Version SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS Reference Line Regulation 5V ≤ VIN ≤ 30V l 0.02 0.075 %/V 2V ≤ VIN ≤ 5V 0.20 0.400 %/V AV Gain Block Gain R L = 100k (Note 3) l 1000 6000 V/V ILIM Current Limit 220 Ω from ILIM to VIN 400 mA Current Limit Temperature Coefficient l – 0.3 %/°C Switch OFF Leakage Current Measured at SW1 Pin, V SW1 = 12V 1 10 µA Maximum Excursion Below GND I SW1≤ 10µA, Switch OFF –400 –350 mV LT1111M SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS IQ Quiescent Current Switch OFF l 300 500 µA fOSC Oscillator Frequency l 45 72 100 kHz DC Duty Cycle: Step-Up Mode Full Load l 40 50 62 % Step-Down Mode l 20 55 % tON Switch ON Time: Step-Up Mode I LIM Tied to VIN l 57 1 1 µs Step-Down Mode V OUT = 5V, VIN = 12V l 39 µs Reference Line Regulation 2V ≤ VIN ≤ 5V, 25°C ≤ TA ≤ 125°C 0.2 0.4 %/V 2.4V ≤ VIN ≤ 5V, TA = –55 °C 0.8 %/V VSAT SW Saturation Voltage, Step-Up Mode 0 °C ≤ TA ≤ 125°C, ISW = 500mA, 0.5 0.65 V TA = –55 °C, ISW = 400mA SW Saturation Voltage, Step-Down Mode V IN = 12V, 0°C ≤ TA ≤ 125°C 1.5 V ISW = 500mA TA = –55 °C 2.0 V VIN = 3V, – 55°C ≤ TA ≤ 125°C unless otherwise noted. LT1111C SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS IQ Quiescent Current Switch OFF l 300 450 µA fOSC Oscillator Frequency l 54 72 95 kH DC Duty Cycle: Step-Up Mode Full Load l 43 50 59 % Step-Down Mode l 24 34 50 % tON Switch ON Time: Step-Up Mode I LIM Tied to VIN l 5.0 7 9.0 µs Step-Down Mode V OUT = 5V, VIN = 12V l 3.3 5 7.8 µs Reference Line Regulation 2V ≤ VIN ≤ 5V l 0.2 0.7 %/V VSAT SW Saturation Voltage, Step-Up Mode V IN = 3V, ISW = 650mA l 0.5 0.65 V SW Saturation Voltage, Step-Down Mode V IN = 12V, ISW = 650mA l 1.1 1.50 V VIN = 3V, 0°C ≤ TA ≤ 70°C unless otherwise noted. The l denotes specifications which apply over the full operating temperature range. Note 1: This specification guarantees that both the high and low trip points of the comparator fall within the 1.20V to 1.30V range. Note 2: The output voltage waveform will exhibit a sawtooth shape due to the comparator hysteresis. The output voltage on the fixed output versions will always be within the specified range. Note 3: 100k resistor connected between a 5V source and the A0 pin.

CCHARA TERISTICSUWATYPICALP E RFOR CE TEMPERATURE (°C) ON TIME (µs) –50 –25 0 25 LT111 • TPC03 50 75 100 125 9.5 9.0 8.5 8.0 7.5 7.0 6.5 6.0 5.5 5.0 Oscillator Frequency Oscillator Frequency Switch ON Time TEMPERATURE (°C) –50 OSCILLATOR FREQUENCY (KHz)50 100 –25 0 25 50 LT1111 • TPC01 75 100 125 INPUT VOLTAGE (V) FREQUENCY (KHz) 36 91 2 LT1111 • TPC02 15 18 21 24 27 30 Saturation Voltage Saturation Voltage Duty Cycle Step-Up Mode Step-Up Mode TEMPERATURE (°C) DUTY CYCLE (%) –50 –25 0 25 LT1111 • TPC04 50 75 100 125 SWITCH CURRENT (A) SATURATION VOLTAGE (V) 0 0.2 0.4 0.6 LT1111 • TPC06 0.8 1.0 1.2 1.6 1.4 1.2 1.0 0.8 0.6 0.4 0.2 1.4 VIN = 3V VIN = 2V VIN = 5V TEMPERATURE (°C) SATURATION VOLTAGE (V) –50 – 25 0 25 LT1111 • TPC05 50 75 100 125 1.0 0.9 0.8 0.7 0.6 0.5 0.4 0.3 0.2 0.1 VIN = 3V ISW = 650mA Switch ON Voltage Switch ON Voltage Minimum/Maximum Frequency Step-Down Mode Step-Down Mode vs ON Time SWITCH CURRENT (A) ON VOLTAGE (V) 0 0.2 0.4 0.6 LT1111 • TPC08 0.8 1.0 1.4 1.2 1.0 0.8 0.6 0.4 0.2 VIN = 12V TEMPERATURE (°C) ON VOLTAGE (V) –50 –25 0 25 LT1111 • TPC07 50 75 100 2.00 1.75 1.50 1.25 1.00 0.75 0.50 125 VIN = 12V ISW = 650mA SWITCH ON TIME (µs) OSCILLATOR FREQUENCY (KHz) 4 567 LT1111 • TPC09 100 10 11 12 –55°C ≤ TA ≤ 125°C 0°C ≤ TA ≤ 70°C

CCHARA TERISTICSUWATYPICALP E RFOR CE GND (Pin 5): Ground. A0 (Pin 6): Auxiliary Gain Block (GB) Output. Open collector, can sink 300µA. SET (Pin 7): GB Input. GB is an op amp with positive input connected to SET pin and negative input connected to 1.25V reference. FB/SENSE (Pin 8): On the LT1111 (adjustable) this pin goes to the comparator input. On the LT1111-5 and LT1111-12, this pin goes to the internal application resistor that sets output voltage. Maximum Switch Current Quiescent Current Quiescent Current vs R LIM INPUT VOLTAGE (V) QUIESCENT CURRENT (µA) LT1111 • TPC10 400 380 360 340 320 280 260 240 220 200 300 9 1 21 51 82 12 42 73 0 TEMPERATURE (°C) QUIESCENT CURRENT (µA) –50 LT1111 • TPC11 500 450 400 350 250 –25 150 100 200 300 0 25 50 75 100 125 TEMPERATURE (°C) BIAS CURRENT (nA) –50 LT1111 • TPC14 100 –25 0 25 50 75 100 125 ILIM (Pin 1): Connect this pin to VIN for normal use. Where lower current limit is desired, connect a resistor between ILIM and VIN. A 220Ω resistor will limit the switch current to approximately 400mA. VIN (Pin 2): Input Supply Voltage. SW1 (Pin 3): Collector of Power Transistor. For step-up mode connect to inductor/diode. For step-down mode connect to VIN. SW2 (Pin 4): Emitter of Power Transistor. For step-up mode connect to ground. For step-down mode connect to inductor/diode. This pin must never be allowed to go more than a Schottky diode drop below ground. PI UFU UC USOTI TEMPERATURE (°C) BIAS CURRENT (nA) –50 LT1111 • TPC13 100 –25 0 25 50 75 100 125 Set Pin Bias Current Feedback Bias Current RLIM (Ω ) SWITCH CURRENT (A) LT1111 • TPC12 100 1.5 1.4 1.3 1.2 1.1 0.9 0.8 1000 0.7 0.6 0.5 0.4 0.3 0.2 0.1 1.0 STEP-DOWN VIN = 12V STEP-UP 2V ≤ VIN ≤ 5V

Gain block A2 can serve as a low-battery detector. The negative input of A2 is the 1.25V reference. A resistor divider from VIN to GND, with the mid-point connected to the SET pin provides the trip voltage in a low-battery detector application. AO can sink 300 µA (use a 22k resistor pull-up to 5V). A resistor connected between the I LIM pin and V IN sets maximum switch current. When the switch current ex- ceeds the set value, the switch cycle is prematurely terminated. If current limit is not used, I LIM should be tied directly to VIN. Propagation delay through the current limit circuitry is approximately 1µs. In step-up mode the switch emitter (SW2) is connected to ground and the switch collector (SW1) drives the induc- tor; in step-down mode the collector is connected to VIN and the emitter drives the inductor. The LT1111-5 and LT1111-12 are functionally identical to the LT1111. The -5 and -12 versions have on-chip voltage setting resistors for fixed 5V or 12V outputs. Pin 8 on the fixed versions should be connected to the output. No external resistors are needed. ULT11 OATI1 1 OPER The LT1111 is a gated oscillator switcher. This type architecture has very low supply current because the switch is cycled when the feedback pin voltage drops below the reference voltage. Circuit operation can best be understood by referring to the LT1111 block diagram. Comparator A1 compares the feedback (FB) pin voltage with the 1.25V reference signal. When FB drops below 1.25V, A1 switches on the 72kHz oscillator. The driver amplifier boosts the signal level to drive the output NPN power switch. The switch cycling action raises the output voltage and FB pin voltage. When the FB voltage is suffi- cient to trip A1, the oscillator is gated off. A small amount of hysteresis built into A1 ensures loop stability without external frequency compensation. When the comparator output is low, the oscillator and all high current circuitry is turned off, lowering device quiescent current to just 300µA. The oscillator is set internally for 7µs ON time and 7µs OFF time, optimizing the device for circuits where V OUT and VIN differ by roughly a factor of 2. Examples include a 3V to 5V step-up converter or a 9V to 5V step-down converter. WIDA G R ABLOCK S LT1111 • BD01 INV GND SET A0A2 1.25V REFERENCE A1 OSCILLATOR DRIVER SW1 SW2 LIMI GAIN BLOCK/ ERROR AMP COMPARATOR FB LT1111-5/LT1111-12LT1111 LT1111 • BD02 INV GND SET A0A2 1.25V REFERENCE A1 OSCILLATOR DRIVER SW1 SW2 LIMI 220k SENSE LT1111-5: LT1111-12: R1 = 73.5k R1 = 25.5k GAIN BLOCK/ ERROR AMP COMPARATOR

Inductor Selection — General A DC/DC converter operates by storing energy as mag- netic flux in an inductor core, and then switching this energy into the load. Since it is flux, not charge, that is stored, the output voltage can be higher, lower, or oppo- site in polarity to the input voltage by choosing an appropriate switching topology. To operate as an efficient energy transfer element, the inductor must fulfill three requirements. First, the inductance must be low enough for the inductor to store adequate energy under the worst case condition of minimum input voltage and switch-on time. The inductance must also be high enough so maxi- mum current ratings of the LT1111 and inductor are not exceeded at the other worst case condition of maximum input voltage and ON time. Additionally, the inductor core must be able to store the required flux; i.e., it must not saturate. At power levels generally encountered with LT1111 based designs, small surface mount ferrite core units with saturation current ratings in the 300mA to 1A range and DCR less than 0.4Ω (depending on application) are adequate. Lastly, the inductor must have sufficiently low DC resistance so excessive power is not lost as heat in the windings. An additional consideration is Electro- Magnetic Interference (EMI). Toroid and pot core type inductors are recommended in applications where EMI must be kept to a minimum; for example, where there are sensitive analog circuitry or transducers nearby. Rod core types are a less expensive choice where EMI is not a problem. Minimum and maximum input voltage, output voltage and output current must be established before an inductor can be selected. Inductor Selection — Step-Up Converter In a step-up, or boost converter (Figure 4), power gener- ated by the inductor makes up the difference between input and output. Power required from the inductor is determined by: PV V V IL OUT D IN MIN OUT=+() ( ) ±( ) 01 where VD is the diode drop (0.5V for a 1N5818 Schottky). Energy required by the inductor per cycle must be equal or greater than: USA OPPLICATI WU UI FOR ATIO P fL OSC/( ) 02 in order for the converter to regulate the output. When the switch is closed, current in the inductor builds according to: It V R eL IN Rt L() ± ( ) = ′ 10 3 where R′ is the sum of the switch equivalent resistance (0.8Ω typical at 25 °C) and the inductor DC resistance. When the drop across the switch is small compared to VIN, the simple lossless equation: It V L tL IN() = ()04 can be used. These equations assume that at t = 0, inductor current is zero. This situation is called “discon- tinuous mode operation” in switching regulator parlance. Setting “t” to the switch-on time from the LT1111 speci- fication table (typically 7µs) will yield I PEAK for a specific “L” and VIN. Once IPEAK is known, energy in the inductor at the end of the switch-on time can be calculated as: EL IL PEAK= 1 2 052 () EL must be greater than PL/fOSC for the converter to deliver the required power. For best efficiency I PEAK should be kept to 1A or less. Higher switch currents will cause excessive drop across the switch resulting in reduced efficiency. In general, switch current should be held to as low a value as possible in order to keep switch, diode and inductor losses at a minimum. As an example, suppose 12V at 60mA is to be generated from a 4.5V to 8V input. Recalling equation (01), P V V V mA mWL =+() ( ) =12 0 5 4 5 60 480 06.± . ( ) Energy required from the inductor is P f mW kHz JL OSC ==480 72 67 0 7.( )µ

USA OPPLICATI WU UI FOR ATIO IOUT = output current VOUT = output voltage VIN = minimum input voltage VSW is actually a function of switch current which is in turn a function of VIN, L, time, and VOUT. To simplify, 1.5V can be used for VSW as a very conservative value. Once IPEAK is known, inductor value can be derived from: L VV V I tIN MIN SW OUT PEAK ON= −− × ()11 where tON = switch-on time (7µs). Next, the current limit resistor R LIM is selected to give IPEAK from the RLIM Step-Down Mode curve. The addition of this resistor keeps maximum switch current constant as the input voltage is increased. As an example, suppose 5V at 300mA is to be generated from a 12V to 24V input. Recalling Equation (10), I mA mAPEAK = () +  = 2 300 05 0 50 5 1 2 15 05 600 12. ±. . () Next, inductor value is calculated using Equation (11): L mA sH==12 1 5 5 Use the next lowest standard value (56µH). Then pick RLIM from the curve. For IPEAK = 600mA, RLIM = 56Ω . Inductor Selection — Positive-to-Negative Converter Figure 7 shows hookup for positive-to-negative conver- sion. All of the output power must come from the inductor. In this case, P L = (VOUT+ VD)(IOUT) (14) In this mode the switch is arranged in common collector or step-down mode. The switch drop can be modeled as a 0.75V source in series with a 0.65Ω resistor. When the Picking an inductor value of 47µH with 0.2Ω DCR results in a peak switch current of: I V em APEAK s  = ×45 10 1 623 08 10 7 . ±. ( ) Ω Ωµ µ Substituting IPEAK into Equation 04 results in: EH A JL = () ( ) =1 2 47 0 623 9 1 092µµ .. ( ) Since 9.1µJ > 6.7 µJ, the 47 µH inductor will work. This trial-and-error approach can be used to select the opti- mum inductor. Keep in mind the switch current maximum rating of 1.5A. If the calculated peak current exceeds this, consider using the LT1110. The 70% duty cycle of the LT1110 allows more energy per cycle to be stored in the inductor, resulting in more output power. A resistor can be added in series with the I LIM pin to invoke switch current limit. The resistor should be picked so the calculated IPEAK at minimum VIN is equal to the Maximum Switch Current (from Typical Performance Characteristic curves). Then, as V IN increases, switch current is held constant, resulting in increasing efficiency. Inductor Selection — Step-Down Converter The step-down case (Figure 5) differs from the step-up in that the inductor current flows through the load during both the charge and discharge periods of the inductor. Current through the switch should be limited to ~650mA in this mode. Higher current can be obtained by using an external switch (see Figure 6). The I LIM pin is the key to successful operation over varying inputs. After establishing output voltage, output current and input voltage range, peak switch current can be calculated by the formula: I I DC VV VV VPEAK OUT OUT D IN SW D = + 2 10± () where DC = duty cycle (0.50) VSW = switch drop in step-down mode VD = diode drop (0.5V for a 1N5818)

Table 2. Inductor Manufacturers

1250 Feehanville Drive

amplifier, low-battery detector or linear post regulator. positive input comes out on the SET pin. Table 3. Capacitor Manufacturers

1201 Sanyo Avenue

927 East State Parkway

Figure 12. Setting Low-Battery Detector Trip Point Table 1. Component Selection for Common Converters

3V to –22V LCD Bias Generator 9V to 5V Step-Down Converter 20V to 5V Step-Down Converter INV SW2 SW1 LT1111 • TA03 LIMI GND 100Ω LT1111 MBRS130T3 4.7µF L1* 27µH –22V OUTPUT 7mA AT 2V INPUT * L1 = SUMIDA CD54-270K FOR 5V INPUT CHANGE R1 TO 47Ω . CONVERTER WILL DELIVER –22V AT 40mA. 2 × 1.5V CELLS 3V FB 22µF 220k 0.1µF 1N4148 39.2k 732k MBRS130T3 INV SW2 SW1 LT1111 • TA04 LIMI SENSE GND 100 BATTERY LT1111-5 MBRS130T3 22µF L1* 15µH Ω 5V OUTPUT 150mA AT 9V INPUT 50mA AT 6.5V INPUT * L1 = SUMIDA CD54-150K INV SW2 SW1 LT1111 • TA06 LIMI SENSE GND 100 LT1111-5 MBRS130T3 47µF L1* 68µH Ω 5V OUTPUT 300mA * L1 = SUMIDA CD74-680M VIN 12V TO 28V

Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However, no responsibility is assumed for its use. Linear Technology Corporation makes no represen- tation that the interconnection of its circuits as described herein will not infringe on existing patent rights. 5V to –5V Converter LT1111 • TA20 LIMI FB GND LT1111 VIN 8V TO 18V BAT54 L1* 10µH, 3A 220µF 500mA 0.22Ω 51Ω2k 1N4148 40.2k 121k OPERATE STANDBY INV SW1 SW2 MTM20P08 MBRD320 * L1 = SUMIDA CDR105-100M 2N3904 High Power, Low Quiescent Current Step-Down Converter INV SW2 SW1 LT1111 • TA05 LIMI SENSE GND 100 LT1111-5 MBRS130T3 33µF L1* 33µH Ω –5V OUTPUT 75mA 22µF VIN 5V INPUT * L1 = SUMIDA CD54-330K Voltage Controlled Positive-to-Negative Converter LT1111 • TA07 FB GND 220Ω LT1111 * L1 = COILTRONICS CTX20-4 † ZETEX INC. 516-543-7100 VIN 5V TO 12V BAT54 220Ω L1* 20µH, 3A INV LT1006 47µF 39k 200k –V OUT = –5.13 × VC 2W MAXIMUM OUTPUT VC (0V TO 5V) 0.22Ω MBRD320 INV SW2 SW1 LIMI ZETEX† ZTX788A

Linear Technology Corporation 1630 McCarthy Blvd., Milpitas, CA 95035-7487 (408) 432-1900 l FAX: (408) 434-0507 l TELEX: 499-3977  LINEAR TECHNOLOGY CORPORA TION 1994 LT/GP 0594 5K REV C • PRINTED IN USA UPACKAGE DESCRIPTIO Dimensions in inches (millimeters) unless otherwise noted. 8-Lead Ceramic DIP 8-Lead Plastic DIP 0.290 – 0.320 (7.366 – 8.128) 0.008 – 0.018 0.385 ± 0.025 (9.779 ± 0.635) 0.005 (0.127) MIN 0.405 (10.287) MAX 0.220 – 0.310 (5.588 – 7.874) 12 3 4 87 65 0.025 (0.635) RAD TYP 0.045 – 0.068 (1.143 – 1.727) FULL LEAD OPTION 0.023 – 0.045 (0.584 – 1.143) HALF LEAD OPTION CORNER LEADS OPTION (4 PLCS) 0.014 – 0.026 (0.360 – 0.660) 0.200 (5.080) MAX 0.015 – 0.060 (0.381 – 1.524) 0.125 3.175 MIN0.100 ± 0.010 (2.540 ± 0.254) 0.045 – 0.068 (1.143 – 1.727) NOTE: LEAD DIMENSIONS APPLY TO SOLDER DIP OR TIN PLATE LEADS. 0.009 – 0.015 (0.229 – 0.381) 0.300 – 0.320 (7.620 – 8.128) 0.325 +0.025 –0.015 +0.635 –0.3818.255() 0.045 ± 0.015 (1.143 ± 0.381) 0.100 ± 0.010 (2.540 ± 0.254) 0.065 (1.651) TYP 0.045 – 0.065 (1.143 – 1.651) 0.130 ± 0.005 (3.302 ± 0.127) 0.020 (0.508) MIN 0.018 ± 0.003 (0.457 ± 0.076) 0.125 (3.175) MIN 12 3 4 87 6 5 0.250 ± 0.010 (6.350 ± 0.254) 0.400 (10.160) MAX 8-Lead Plastic SOIC SO8 0294 0.016 – 0.050 0.406 – 1.270 0.010 – 0.020 0°– 8° TYP 0.008 – 0.010 (0.203 – 0.254) 0.053 – 0.069 (1.346 – 1.752) 0.014 – 0.019 (0.355 – 0.483) 0.004 – 0.010 (0.101 – 0.254) 0.050 (1.270) BSC 1 2 3 4 0.150 – 0.157 (3.810 – 3.988) 8 7 6 5 0.189 – 0.197 (4.801 – 5.004) 0.228 – 0.244 (5.791 – 6.197) *THESE DIMENSIONS DO NOT INCLUDE MOLD FLASH OR PROTRUSIONS. MOLD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.006 INCH (0.15mm).