LT1107CS8

LT1107_02 LINER | Alldatasheet

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FEATURES

Adjustable and Fixed 5V, 12V Efficiency n Operates at Supply Voltages from 2V to 30V n Consumes Only 320mA Supply Current n Works in Step-Up or Step-Down Mode n Only Three External Components Required n Low-Battery Detector Comparator On-Chip n User Adjustable Current Limit n Internal 1A Power Switch n Fixed or Adjustable Output Voltage Versions n Space Saving 8-Pin MiniDIP or SO-8 Package The LT 1107 is a versatile micropower DC/DC converter. The device requires only three external components to deliver a fixed output of 5V or 12V. Supply voltage ranges from 2V to 12V in step-up mode and to 30V in step-down mode. The LT1107 functions equally well in step-up, step- down, or inverting applications. The LT1107 is pin-for-pin compatible with the LT1111, but has a duty cycle of 70%, resulting in increased output current in many applications. The LT1107 can deliver 150mA at 5V from a 2AA cell input and 5V at 300mA from 24V in step-down mode. Quiescent current is just 320mA, making the LT1107 ideal for power-conscious battery- operated systems. The 63kHz oscillator is optimized to work with surface mount inductors and capacitors. Switch current limit can be programmed with a single resistor. An auxiliary gain block can be configured as a low-battery detector, linear post regulator, undervoltage lock-out circuit, or error amplifier. n Palmtop Computers n 3V to 5V, 5V to 12V Converters n 24V to 5V, 12V to 5V Converters n LCD Bias Generators n Peripherals and Add-On Cards n Battery Backup Supplies n Cellular Telephones n Portable Instruments LOAD CURRENT (mA) EFFICIENCY (%) 10 100 400

1107 TA02

VIN = 3V VIN = 2.5V VIN = 2V 150mA MBRS120T3 L1* 33mH 47W 2 · AA ALKALINE CELLS 100mF SUMIDA CD54-330K COILCRAFT DT3316-473 ILIM VIN SENSE SW1 SW2GND 47mF LT1107-5

1107 TA01

+ + Palmtop Computer Logic Supply , LTC and LT are registered trademarks of Linear Technology Corporation

A UGWA WU WARBSOLUTEX I T I S Operating Temperature Range ELECTRICAL C CHARA TERISTICS The l denotes the specifications which apply over the full operating temperature range, VIN = 3V, military or commercial version, TA = 25°C, unless otherwise noted. SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS IQ Quiescent Current Switch OFF 320 450 mA Quiescent Current, Step-Up Mode Configuration No Load LT1107-5 360 mA LT1107-12 550 mA VIN Input Voltage Step-Up Mode l 2 12.6 V Step-Down Mode l 30.0 V Comparator Trip Point Voltage LT1107 (Note 2) l 1.2 1.25 1.3 V VOUT Output Sense Voltage LT1107-5 (Note 3) l 4.75 5 5.25 V LT1107-12 (Note 3) l 11.40 12 12.60 V Comparator Hysteresis LT1107 l 8 12.5 mV Output Hysteresis LT1107-5 l 32 50 mV LT1107-12 l 75 120 mV fOSC Oscillator Frequency 50 63 77 kHz Duty Cycle, Step-Up Mode Full Load 64 70 76 % tON Switch ON Time, Step-Up Mode I LIM Tied to VIN 8.8 11 12.7 ms WU UPACKAGE/ORDER I FOR ATIO ORDER PART NUMBER ORDER PART NUMBER LT1107CN8 LT1107CN8-5 LT1107CN8-12 LT1107CS8 LT1107CS8-5 LT1107CS8-12 LT1107IS8 TJMAX = 90°C, qJA = 130°C/W (N) TJMAX = 90°C, qJA = 150°C/W 1107 11075 110712 1107I S8 PART MARKING TOP VIEW ILIM VIN SW1 SW2 FB (SENSE)* SET AO GND N8 PACKAGE 8-LEAD PLASTIC DIP * FIXED VERSIONS TOP VIEW S8 PACKAGE 8-LEAD PLASTIC SO *FIXED VERSIONS ILIM VIN SW1 SW2 FB(SENSE)* SET AO GND Consult LTC Marketing for parts specified with wider operating temperature ranges. (Note 1) J8 PACKAGE 8-LEAD CERAMIC DIP TJMAX = 150°C, qJA = 120°C/W (J) LT1107MJ8 LT1107MJ8-5 LT1107MJ8-12 OBSOLETE PACKAGE Consider the N8 Package for Alternate Source

SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS IQ Quiescent Current Switch OFF l 450 mA fOSC Oscillator Frequency l 50 63 88 kHz DC Duty Cycle Step-Up Mode l 62 69 78 % Step-Down Mode, VIN = 12V l 50 60 70 % tON Switch ON Time Step-Up Mode l 8 11 13.5 ms Step-Down Mode, VIN = 12V l 6 9 12.0 ms Reference Line Regulation 2V £ VIN £ 5V l 0.2 0.7 %/V VSAT Switch Saturation Voltage, Step-Up Mode V IN = 3V, ISW = 650mA l 0.5 0.65 V Switch Saturation Voltage, Step-Down Mode V IN = 12V, ISW = 650mA l 1.1 1.5 V ELECTRICAL C CHARA TERISTICS The l denotes the specifications which apply over the full operating temperature range, VIN = 3V, – 55°C £ TA £ 125°C, unless otherwise noted. Note 1: Absolute Maximum Ratings are those values beyond which the life of a device may be impaired. Note 2: This specification guarantees that both the high and low trip points of the comparator fall within the 1.2V to 1.3V range. Note 3: The output voltage waveform will exhibit a sawtooth shape due to the comparator hysteresis. The output voltage on the fixed-output versions will always be within the specified range. Note 4: 100k resistor connected between a 5V source and the AO pin. The l denotes the specifications which apply over the full operating temperature range, VIN = 3V, military or commercial version, TA = 25°C, unless otherwise noted. The l denotes the specifications which apply over the full operating temperature range, VIN = 3V, 0°C £ TA £ 70°C, unless otherwise noted. SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS Feedback Pin Bias Current LT1107, V FB = 0V l 70 120 nA Set Pin Bias Current V SET = VREF l 70 300 nA VOL Gain Block Output Low I SINK = 300mA, VSET = 1V l 0.15 0.4 V Reference Line Regulation 5V £ VIN £ 30V l 0.02 0.075 %/V AV Gain Block Gain R L = 100k (Note 4) l 1000 6000 V/V Current Limit 220 W to ILIM to VIN 400 mA Current Limit Temperature Coefficient l –0.3 %/ °C Switch OFF Leakage Current Measured at SW1 Pin, V SW1 = 12V 1 10 mA VSW2 Maximum Excursion Below GND I SW1 £ 10mA, Switch OFF –400 –350 mV LT1107M SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS IQ Quiescent Current Switch OFF l 500 mA fOSC Oscillator Frequency l 40 63 95 kHz DC Duty Cycle Step-Up Mode l 56 69 81 % Step-Down Mode, VIN = 12V l 45 60 73 % tON Switch ON Time Step-Up Mode l 71 1 1 5 ms Step-Down Mode, VIN = 12V l 59 1 3 ms Reference Line Regulation 2V £ VIN £ 5V, 0°C £ TA £ 125°C 0.2 0.4 %/V 2.4V £ VIN £ 5V, TA = –55 °C 0.8 %/V VSAT Switch Saturation Voltage, Step-Up Mode 0 °C £ TA £ 125°C, ISW = 500mA 0.5 0.65 V TA = –55 °C, ISW = 400mA 0.5 0.65 V Switch Saturation Voltage, Step-Down Mode V IN = 12V, ISW = 500mA 0°C £ TA £ 125°C 1.5 V TA = –55 °C 2.0 V

CCHARA TERISTICSUWATYPICALP E RFOR CE Saturation Voltage, Step-Up Mode Switch ON Voltage, Step-Down (SW2 Pin Grounded) Mode (SW1 Pin Connected to V IN) Maximum Switch Current vs RLIM Quiescent Current Quiescent Current TEMPERATURE (°C) –55 FREQUENCY (kHz) –15 25 45 125

1107 G07

–35 5 65 85 105 100 Oscillator Frequency Switch ON Time Step-Down Mode TEMPERATURE (°C) –55 SWITCH ON TIME (ms) –15 25 45 125

1107 G10

–35 5 65 85 105 TEMPERATURE (°C) –55 DUTY CYCLE (%) –15 25 45 125

1107 G09

–35 5 65 85 105 Duty Cycle Step-Up Mode TEMPERATURE (°C) –55 QUIESCENT CURRENT (mA) –15 25 45 125

1107 G05

–35 5 65 85 105 400 350 300 250 200 150 100 TEMPERATURE (°C) –55 SWITCH ON TIME (ms) –15 25 45 125

1107 G08

–35 5 65 85 105 Switch ON Time Step-Up Mode INPUT VOLTAGE (V) QUIESCENT CURRENT (mA) 400 380 360 340 320 300 280 260 240 220 200

1107 G06

TA = 25°C RLIM (W ) SWITCH CURRENT (A)

1107 G03

1.5 1.4 1.3 1.2 1.1 0.9 0.8 1000 0.7 0.6 0.5 0.4 0.3 0.2 0.1 1.0 STEP-DOWN VIN = 12V STEP-UP 2V £ VIN £ 5V SWITCH CURRENT (A) SWITCH ON VOLTAGE (V) 0.6

1107 G02

0.2 0.4 0.8 1.4 1.3 1.2 1.1 1.0 0.9 0.8 0.7 0.1 0.3 0.5 0.7 SWITCH CURRENT (A) SATURATION VOLTAGE (V) 1.2 1.0 0.8 0.6 0.4 0.2 0.2 0.4 0.6 0.8

1107 G01

1.0 1.2 VIN = 3V VIN = 2V VIN = 5V

ILIM (Pin 1): Connect this pin to VIN for normal use. Where lower current limit is desired, connect a resistor between ILIM and VIN. A 220W resistor will limit the switch current to approximately 400mA. VIN (Pin 2): Input Supply Voltage. SW1 (Pin 3): Collector of Power Transistor. For step-up mode connect to inductor/diode. For step-down mode connect to V IN. SW2 (Pin 4): Emitter of Power Transistor. For step-up mode connect to ground. For step-down mode connect to inductor/diode. This pin must never be allowed to go more than a Schottky diode drop below ground. GND (Pin 5): Ground. AO (Pin 6): Auxiliary Gain Block (GB) Output. Open collector, can sink 300mA. SET (Pin 7): GB Input. GB is an op amp with positive input connected to SET pin and negative input connected to 1.25V reference. FB/SENSE (Pin 8): On the LT1107 (adjustable), this pin goes to the comparator input. On the LT1107-5 and LT1107-12, this pin goes to the internal application resistor that sets output voltage. PI UFU UC USOTI CCHARA TERISTICSUWATYPICALP E RFOR CE Minimum/Maximum Frequency Minimum/Maximum Frequency vs ON Time, Step-Down Mode vs ON Time, Step-Up Mode TEMPERATURE (°C) –55 DUTY CYCLE (%) –15 25 45 125

1107 G13

–35 5 65 85 105 TEMPERATURE (°C) –55 OUTPUT VOLTAGE (V) –15 25 45 125

1107 G16

–35 5 65 85 105 5.3 5.2 5.1 5.0 4.9 4.8 4.7 TEMPERATURE (°C) –55 OUTPUT VOLTAGE (V) –15 25 45 125

1107 G17

–35 5 65 85 105 12.20 12.15 12.10 12.05 12.00 11.95 11.90 11.85 11.80 LT1107-5 LT1107-12 LT1107 Output Voltage Output Voltage Feedback Voltage TEMPERATURE (°C) –55 TRIP POINT VOLTAGE (V) –15 25 45 125

1107 G18

–35 5 65 85 105 1.30 1.29 1.28 1.27 1.26 1.25 1.24 1.23 1.22 1.21 1.20 ON TIME (ms) FREQUENCY (kHz) 100 5 9 11

1107 G11

0°C £ TA £ 70°C –55°C £ TA £ 125°C ON TIME (ms) FREQUENCY (kHz) 100 7 11 13

1107 G12

0°C £ TA £ 70°C –55°C £ TA £ 125°C TA = 25°C Duty Cycle Step-Down Mode

The LT1107 is a gated oscillator switcher. This type architecture has very low supply current because the switch is cycled when the feedback pin voltage drops below the reference voltage. Circuit operation can best be understood by referring to the LT1107 block diagram. Comparator A1 compares the feedback (FB) pin voltage with the 1.25V reference signal. When FB drops below 1.25V, A1 switches on the 63kHz oscillator. The driver amplifier boosts the signal level to drive the output NPN power switch. The switch cycling action raises the output voltage and FB pin voltage. When the FB voltage is suffi- cient to trip A1, the oscillator is gated off. A small amount of hysteresis built into A1 ensures loop stability without external frequency compensation. When the comparator output is low, the oscillator and all high current circuitry is turned off, lowering device quiescent current to just 300mA. The oscillator is set internally for 11ms ON time and 5ms OFF time in step-up mode, optimizing the device for converters where V OUT » 3VIN. The combination of high duty cycle and the current limit feature enables continuous mode operation in many applications, increasing available output power. OSCILLATOR 1.25V REFERENCE VIN GND SENSE COMPARATOR DRIVER ILIM SW1 SW2 AO GAIN BLOCK/ ERROR AMP SET

1107 BD02

220k LT1107-5: R1 = 73.5k LT1107-12: R1 = 25.5k OSCILLATOR 1.25V REFERENCE VIN GND FB COMPARATOR DRIVER ILIM SW1 SW2 AO GAIN BLOCK/ ERROR AMP SET

1107 BD01

Gain block A2 can serve as a low-battery detector. The negative input of A2 is the 1.25V reference. A resistor divider from VIN to GND, with the mid-point connected to the SET pin provides the trip voltage in a low-battery detector application. AO can sink 300 mA (use a 22k resistor pull-up to 5V). A resistor connected between the I LIM pin and V IN sets maximum switch current. When the switch current ex- ceeds the set value, the switch cycle is prematurely terminated. If current limit is not used, ILIM should be tied directly to VIN. Propagation delay through the current limit circuitry is approximately 1ms. In step-up mode the switch emitter (SW2) is connected to ground and the switch collector (SW1) drives the induc- tor; in step-down mode the collector is connected to VIN and the emitter drives the inductor. The LT1107-5 and LT1107-12 are functionally identical to the LT1107. The -5 and -12 versions have on-chip voltage setting resistors for fixed 5V or 12V outputs. Pin 8 on the fixed versions should be connected to the output. No external resistors are needed.

Inductor Selection –– Step-Up Converter In a step-up, or boost converter (Figure 1), power gener- ated by the inductor makes up the difference between input and output. Power required from the inductor is determined by: where V D is the diode drop (0.5V for a 1N5818 Schottky). Energy required by the inductor per cycle must be equal or greater than: in order for the converter to regulate the output. When the switch is closed, current in the inductor builds according to: where R¢ is the sum of the switch equivalent resistance (0.8W typical at 25 °C) and the inductor DC resistance. When the drop across the switch is small compared to V IN, the simple lossless equation: As an example, suppose 12V at 60mA is to be generated from a 3V to 6V input. Recalling equation (1), Energy required from the inductor is: Picking an inductor value of 33mH with 0.2W DCR results in a peak switch current of: Substituting IPEAK into Equation 4 results in: Since 11.9mJ > 9.05mJ, the 33mH inductor will work. This trial-and-error approach can be used to select the opti- mum inductor. A resistor can be added in series with the ILIM pin to invoke switch current limit. The resistor should be picked so the calculated IPEAK at minimum VIN is equal to the Maximum Switch Current (from Typical Performance Characteristic curves). Then, as V IN increases, peak switch current is held constant, resulting in increasing efficiency. Inductor Selection –– Step-Down Converter The step-down case (Figure 2) differs from the step-up in that the inductor current flows through the load during both the charge and discharge periods of the inductor. Current through the switch should be limited to ~650mA in this mode. Higher current can be obtained by using an external switch (see LT1111 and LT1110 data sheets). The I LIM pin is the key to successful operation over varying inputs. After establishing output voltage, output current and input voltage range, peak switch current can be calculated by the formula: USA OPPLICATI WU UI FOR ATIO P fL OSC/( ) 2 It V R eL IN Rt L() ( )= æ Ł ç ç ö ł - ¢ It V L tL IN () = ()4 can be used. These equations assume that at t = 0, inductor current is zero. This situation is called “discon- tinuous mode operation” in switching regulator parlance. Setting “t” to the switch ON time from the LT1107 speci- fication table (typically 11ms) will yield I PEAK for a specific “L” and VIN. Once IPEAK is known, energy in the inductor at the end of the switch ON time can be calculated as: EL must be greater than PL/fOSC for the converter to deliver the required power. For best efficiency I PEAK should be kept to 1A or less. Higher switch currents will cause excessive drop across the switch resulting in reduced efficiency. In general, switch current should be held to as low a value as possible in order to keep switch, diode and inductor losses at a minimum. P f mW kHz JL OSC ==570 90 5 7.( )m EH A JL = () ( ) =1 3 3 08 5 1 19 1 92mm .. ( ) EL IL PEAK= 1 52 () PV V V m A m WL =+-() ( ) =12 0 5 3 60 570 6.( ) I V em APEAK s H=- æ Ł ç ç ö ł ÷ = 1 850 8 11 1 W W · m m PV V V IL OUT D IN MIN OUT=+ -æ Ł ö ł ()() ()1 I I DC VV VV V PEAK OUT OUT D IN SW D = + Ø º Œ Œ ø ß œ œ 2 10()

In this mode the switch is arranged in common collector or step-down mode. The switch drop can be modeled as a 0.75V source in series with a 0.65W resistor. When the switch closes, current in the inductor builds according to: where R¢ = 0.65W + DCR L VL = VIN – 0.75V As an example, suppose –5V at 50mA is to be generated from a 4.5V to 5.5V input. Recalling Equation (14), Energy required from the inductor is: Picking an inductor value of 100mH with 0.2W DCR results in a peak switch current of: Substituting IPEAK into Equation (04) results in: Since 5.28mJ > 3.82mJ, the 100mH inductor will work. With this relatively small input range, RLIM is not usually necessary and the ILIM pin can be tied directly to VIN. As in the step-down case, peak switch current should be limited to ~650mA. Step-Up (Boost Mode) Operation A step-up DC/DC converter delivers an output voltage higher than the input voltage. Step-up converters are not short-circuit protected since there is a DC path from input to output. P f mW kHz JL OSC ==275 44 1 7.( )m It V R eL L Rt L() = æ Ł ç ç ö ł - ¢ 11 5 () where DC = duty cycle (0.50 in step-down mode) VSW = switch drop in step-down mode VD = diode drop (0.5V for a 1N5818) IOUT = output current VOUT = output voltage VIN = minimum input voltage VSW is actually a function of switch current which is in turn a function of VIN, L, time, and VOUT. To simplify, 1.5V can be used for VSW as a very conservative value. Once IPEAK is known, inductor value can be derived from: where tON = switch ON time (7ms). Next, the current limit resistor R LIM is selected to give IPEAK from the Maximum Switch Current vs R LIM curve. The addition of this resistor keeps maximum switch cur- rent constant as the input voltage is increased. As an example, suppose 5V at 300mA is to be generated from a 12V to 24V input. Recalling Equation (10): Next, inductor value is calculated using Equation (11): L mA sH= -- =12 1 5 5 600 76 4 1 3. ()mm Use the next lowest standard value (56mH). Then pick RLIM from the curve. For IPEAK = 600mA, RLIM = 56W . Inductor Selection –– Positive-to-Negative Converter Figure 4 shows hookup for positive-to-negative conver- sion. All of the output power must come from the inductor. In this case, P (14)L =+() ()VV IOUT D OUT L VV V I t IN MIN SW OUT PEAK ON=

• () ()11 I mA mAPEAK = () + Ø º Œ Œ ø ß œ œ 2 300 05 0 50 5 1 2 15 05 600 12 I VV e mA PEAK s -() +() æ Ł ç ç ö ł -45 07 5 06 5 02 325 18 08 5 9 100.. WW Wm m EH A JL = () ( ) =1 100 0 325 5 28 192mm .. ( ) USA OPPLICATI WU UI FOR ATIO

VCESAT to appear across L1. A current then builds up in L1. Figure 2. Step-Down Mode Hookup

1107 F01

1107 F02

step-down converter is shown in Figure 2. Figure 1. Step-Up Mode Hookup resistance. This is taken into account in the “Inductor Selection” section.

voltages can be accommodated as in the prior section. polarity feedback information to the regulator. Figure 4. Negative-to-Positive Converter switch current, a feature not found on competing devices. when the device goes into continuous mode operation. Figure 6, keeping output ripple to a minimum.

1107 F04

1107 F03

Figure 3. Positive-to-Negative Converter

Figure 6. Current Limit Keeps Inductor Current Under Control Figure 5. No Current Limit Causes Large Inductor

1107 F05

1107 F06

the device will still maintain output regulation. amplifier, low-battery detector or linear post regulator. positive input comes out on the SET pin. OUT by only a few millivolts.

1107 F07

Figure 7. LT1107 Current Limit Circuitry

1107 F09

Figure 9. Output Ripple Reduction Using Gain Block Figure 8. Setting Low-Battery Detector Trip Point

1107 F08

8-Lead CERDIP (Narrow .300 Inch, Hermetic) (Reference LTC DWG # 05-08-1110) J8 1298 0.014 – 0.026 (0.360 – 0.660) 0.200 (5.080) MAX 0.015 – 0.060 (0.381 – 1.524) 0.125 3.175 MIN0.100 (2.54) BSC

0.300 BSC

(0.762 BSC) 0.008 – 0.018 0.005 (0.127) MIN 0.405 (10.287) MAX 0.220 – 0.310 (5.588 – 7.874) 12 3 4 87 65 0.025 (0.635) RAD TYP 0.045 – 0.068 (1.143 – 1.727) FULL LEAD OPTION 0.023 – 0.045 (0.584 – 1.143) HALF LEAD OPTION CORNER LEADS OPTION (4 PLCS) 0.045 – 0.065 (1.143 – 1.651)NOTE: LEAD DIMENSIONS APPLY TO SOLDER DIP/PLATE OR TIN PLATE LEADS OBSOLETE PACKAGE

8-Lead PDIP (Narrow .300 Inch) (Reference LTC DWG # 05-08-1510) UPACKAGE DESCRIPTIO N8 0502 .100 (2.54) BSC .065 (1.651) TYP .045 – .065 (1.143 – 1.651) .130 – .005 (3.302 – 0.127) .020 (0.508) MIN.018 – .003 (0.457 – 0.076) .125 (3.175) MIN 12 3 4 87 6 5 .255 – .015* (6.477 – 0.381) .400* (10.160) MAX .009 – .015 (0.229 – 0.381) .300 – .325 (7.620 – 8.255) .325 +.035 –.015 +0.889 –0.3818.255() NOTE: 1. DIMENSIONS ARE INCHES MILLIMETERS *THESE DIMENSIONS DO NOT INCLUDE MOLD FLASH OR PROTRUSIONS. MOLD FLASH OR PROTRUSIONS SHALL NOT EXCEED .010 INCH (0.254mm)

8-Lead Plastic Small Outline (Narrow .150 Inch) (Reference LTC DWG # 05-08-1610) UPACKAGE DESCRIPTIO Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However, no responsibility is assumed for its use. Linear Technology Corporation makes no represen- tation that the interconnection of its circuits as described herein will not infringe on existing patent rights. .016 – .050 (0.406 – 1.270) .010 – .020 0°– 8° TYP .008 – .010 (0.203 – 0.254) SO8 0502 .053 – .069 (1.346 – 1.752) .014 – .019 (0.355 – 0.483) TYP .004 – .010 (0.101 – 0.254) .050 (1.270) BSC N 2 3 4 N/2 .150 – .157 (3.810 – 3.988) NOTE 3 8 7 6 5 .189 – .197 (4.801 – 5.004) NOTE 3 .228 – .244 (5.791 – 6.197) .245 MIN N 1 2 3 N/2 .160 –.005 RECOMMENDED SOLDER PAD LAYOUT .045 –.005 .050 BSC .030 –.005 TYP INCHES (MILLIMETERS) NOTE: 1. DIMENSIONS IN 2. DRAWING NOT TO SCALE 3. THESE DIMENSIONS DO NOT INCLUDE MOLD FLASH OR PROTRUSIONS. MOLD FLASH OR PROTRUSIONS SHALL NOT EXCEED .006" (0.15mm)

Linear Technology Corporation 1630 McCarthy Blvd., Milpitas, CA 95035-7417 (408) 432-1900 l FAX: (408) 434-0507 l www.linear.com ª LINEAR TECHNOLOGY CORPORATION 1 993 LT/TP 1002 1K REV A • PRINTED IN USA UA OPPLICATITYPICAL 24V-to-5V Step-Down Converter 300mA 1N5818 150mH* 220W 22mF *COILTRONICS CTX150-4 ILIM VIN SENSE SW1 SW2GND 24VIN LT1107-5

1107 TA03

PART NUMBER DESCRIPTION COMMENTS LT1070/LT1070HV 5A I SW, 40kHz, High Efficiency V IN = 3V to 40V/60V, VOUT = 65V/75V, IQ = 6mA, ISD = <50mA, Can be Used for Switching Regulator Buck, Boost, Inverting Applications, TO220-5 Packages LT1071/LT1071HV 2.5A I SW, 40kHz, High Efficiency V IN = 3V to 40V/60V, VOUT = 65V/75V, IQ = 6mA, ISD = <50mA, Can be Used for Switching Regulator Buck, Boost, Inverting Applications, TO220-5 Package LT1072/LT1072HV 1.25A I SW, 40kHz, High Efficiency V IN = 3V to 40V/60V, VOUT = 65V/75V, IQ = 6mA, ISD = <50mA, Can be Used for Switching Regulator Buck, Boost, Inverting Applications, N8, S8, S16, TO220-5 Packages LT1082 1A I SW, 60kHz, High Efficiency V IN = 3V to 75V, VOUT = 100V, IQ = 4.5mA, ISD = <120mA, Can be Used for Switching Regulator Buck, Boost, Inverting Applications, DD, N8, TO220-5 Packages LT1111 1A I SW, 72kHz, High Efficiency V IN = 2V to 30V, VOUT = 34V, IQ = 300mA, Can be Used for Switching Regulator Buck, Boost, Inverting Applications, N8, S8 Packages LT1170/LT1170HV 5A I SW, 100kHz, High Efficiency V IN = 3V to 40V/60V, VOUT = 65V/75V, IQ = 6mA, ISD = <50mA, Can be Used for Switching Regulator Buck, Boost, Inverting Applications, DD, N8, S16, TO220-5 Packages LT1171/LT1171HV 2.5A I SW, 100kHz, High Efficiency V IN = 3V to 40V/60V, VOUT = 65V/75V, IQ = 6mA, ISD = <50mA, Can be Used for Switching Regulator Buck, Boost, Inverting Applications, DD, N8, S16, TO220-5 Packages LT1172/LT1172HV 1.25A I SW, 100kHz, High Efficiency V IN = 3V to 40V/60V, VOUT = 65V/75V, IQ = 6mA, ISD = <100mA, Can be Used for Switching Regulator Buck, Boost, Inverting Applications, N8, S16, DD, TO220-5 Packages LT1307/LT1307B 600mA I SW, 600kHz, High Efficiency V IN = 1V to 12V, VOUT = 28V, IQ = 50mA/1mA, ISD = <1mA Step-Up Switching Regulator Ideal for Single Cell Applications, Low Battery Detect, MS8, N8, S8 Packages LT1317/LT1317B 660mA I SW, 600kHz, High Efficiency V IN = 1.5V to 12V, VOUT = 28V, IQ = 100mA/4.8mA, ISD = <30mA/28mA Step-Up Switching Regulator Low Battery Detect, MS8, S8 Packages LT1370/LT1370HV 6A I SW, 500kHz, High Efficiency V IN = 2.7V to 30V, VOUT = 35V/42V, IQ = 4.5mA, ISD = <12mA, Can be Used for Switching Regulator Buck, Boost, Inverting Applications, DD, TO220-7 Packages LT1371/LT1371HV 3A I SW, 500kHz, High Efficiency V IN = 2.7V to 30V, VOUT = 35V/42V, IQ = 4mA, ISD = <12mA, Can be Used for Switching Regulator Buck, Boost, Inverting Applications, S20, DD, TO220-7 Packages