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www.ti.com SNOS011D –AUGUST 1999–REVISED APRIL 2013 LMC2001HighPrecision,6MHzRail-To-RailOutputOperationalAmplifier Check forSamples: LMC2001 1FEATURES DESCRIPTION The LMC2001 isa new precisionamplifierthatoffers 2• (Vs = 5V,R L = 10K toV+ /2,Typ.Unless Noted) unprecedentedaccuracyand stabilityatan affordable• Low SpecifiedVos 40µV priceand isofferedinminiature(SOT23-5)package.

  • en withNo 1/f85nV/√Hz Thisdeviceutilizespatentedtechniquesto measure and continuallycorrecttheinputoffseterrorvoltage.• High CMRR 120dB The resultisan amplifierwhich isultrastableover• High PSRR 120dB time,and temperature.Ithas excellentCMRR and
  • High A VOL 137dB PSRR ratings,and does not exhibitthe familiar1/f voltageand currentnoise increasethat plagues• Wide Gain-Bandwidth Product 6MHz traditionalamplifiers.The combination of the• High Slew Rate 5V/µs LMC2001 characteristicsmakes ita good choicefor• Low Supply Current750µA transduceramplifiers,highgainconfigurations,ADC bufferamplifiers,DAC I-Vconversion,and any other• Rail-To-RailOutput 30mV from EitherRail 5V applicationrequiringprecisionand/orstability.• No ExternalCapacitorsRequired Other usefulbenefitsof the LMC2001 are rail-to-rail APPLICATIONS output,low supplycurrentof 750µA, and wide gain- bandwidthproductof6MHz. The LMC2001 comes in• PrecisionInstrumentationAmplifiers 5 pin SOT23 and 8 pin SOIC. These extremely
  • Thermocouple Amplifiers versatilefeaturesfoundintheLMC2001 providehigh performanceand ease ofuse.• StrainGauge BridgeAmplifier Connection Diagrams Figure1.8-PinSOIC (Top View) Figure2.5-PinSOT23 (Top View) VOS Distribution Figure3. Pleasebe aware thatan importantnoticeconcerningavailability,standardwarranty,and use incriticalapplicationsof Texas Instrumentssemiconductorproductsand disclaimerstheretoappearsattheend ofthisdatasheet. 2Alltrademarksarethepropertyoftheirrespectiveowners. PRODUCTION DATA informationiscurrentas ofpublicationdate. Copyright© 1999–2013,Texas InstrumentsIncorporatedProductsconform to specificationsper the terms of the Texas Instrumentsstandardwarranty.Productionprocessingdoes not necessarilyincludetestingofallparameters.

SNOS011D –AUGUST 1999–REVISED APRIL 2013 www.ti.com These deviceshave limitedbuilt-inESD protection.The leadsshouldbe shortedtogetherorthedeviceplacedinconductivefoam duringstorageorhandlingtopreventelectrostaticdamage totheMOS gates. ABSOLUTE MAXIMUM RATINGS (1)(2) ESD Tolerance(3) Human Body Model 2000V Machine Model 100V DifferentialInputVoltage ± SupplyVoltage SupplyVoltage(V+ -V-) 5.6V CurrentAtInputPin 30mA CurrentAtOutputPin 30mA CurrentAtPower SupplyPin(4) 50mA Lead Temperature(soldering,10 sec) 260°C StorageTemperatureRange -65°C to150°C JunctionTemperature(TJ)(5) 150°C (1) AbsoluteMaximum Ratingsindicatelimitsbeyond whichdamage tothedevicemay occur.OperatingRatingsindicateconditionsfor whichthedeviceisintendedtobe functional,butspecificperformanceisnotensured.Forensuredspecificationsand testconditions, see theELECTRICAL CHARACTERISTICS . (2) IfMilitary/Aerospacespecifieddevicesarerequired,pleasecontacttheTexas InstrumentsSalesOffice/Distributorsforavailabilityand specifications. (3) Human body model,1.5kΩ inserieswith100pF.Machine model,200Ω inserieswith100pF. (4) Outputcurrentsinexcessof±30mA overlongtermmay adverselyaffectreliability. (5) The maximum power dissipationisa functionofTJ(max),θ JA,and TA.The maximum allowablepower dissipationatany ambient temperatureisPD = (TJ(max)-TA)/θ JA.Allnumbers applyforpackagessoldereddirectlyontoa PC board. OPERATING RATINGS (1) Supplyvoltage 4.75Vto5.25V TemperatureRange LMC2001AI -40°C ≤ TJ ≤ 85°C LMC2001AC 0°C ≤ TJ ≤ 70°C Thermalresistance(θ JA) D Package,8-pinSurfaceMount 180°C /W (1) AbsoluteMaximum Ratingsindicatelimitsbeyond whichdamage tothedevicemay occur.OperatingRatingsindicateconditionsfor whichthedeviceisintendedtobe functional,butspecificperformanceisnotensured.Forensuredspecificationsand testconditions, see theELECTRICAL CHARACTERISTICS . DC ELECTRICAL CHARACTERISTICS Unlessotherwisespecified,alllimitsensuredforT J = 25°C, V+ = 5V,V-= 0V,V CM = 2.5V,VO = 2.5Vand R L > 1M Ω.Boldface limitsapplyatthetemperatureextremes. Symbol Parameter Conditions Typ (1) Limit(2) Units VOS InputOffsetVoltage See (3) 0.5 40 μV 60 max OffsetCalibrationTime 5 30 ms TCV OS InputOffsetVoltage See (4) 0.015 μV/°C Long-Term OffsetDrift See (5) 0.006 μV/month LifetimeVOS drift See (5) 2.5 5 μV Max IIN InputCurrent See (6) -3 pA IOS InputOffsetCurrent 6 pA R IND InputDifferentialResistance 9 M Ω (1) Typicalvaluesrepresentthemost likelyparametricnorm. (2) Alllimitsarespecifiedby testingorstatisticalanalysis,unlessotherwisenoted. (3) The limitsaresetby theaccuracyofhighspeed automatictestequipment.ForthetypicalVOS distribution,see thecurve(Figure4). (4) Precisionbench measurement ofmore than300 units.More than65% ofunitshad lessthan15nV /°C VOS drift. (5) EnsuredVos Driftisbased on 280 devicesoperatedfor1000 hrsat150°C (equivalentto30 years@ 55ºC). (6) Specifiedby designonly.

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www.ti.com SNOS011D –AUGUST 1999–REVISED APRIL 2013 DC ELECTRICAL CHARACTERISTICS (continued) Unlessotherwisespecified,alllimitsensuredforT J = 25°C, V+ = 5V,V-= 0V,V CM = 2.5V,VO = 2.5Vand R L > 1M Ω.Boldface limitsapplyatthetemperatureextremes. Symbol Parameter Conditions Typ (1) Limit(2) Units CMRR Common Mode RejectionRatio 0V ≤ VCM ≤ 3.5V 120 100 dB min 0.1V≤ VCM ≤ 3.5V 110 90 dB min PSRR Power Supply 4.75V≤ V+ ≤ 5.25V 120 95 dB RejectionRatio 90 min AVOL LargeSignalVoltageGain(7) R L = 10kΩ 137 105 dB 100 min R L = 2kΩ 128 95 VO OutputSwing R L = 10kΩ to2.5V 4.975 4.955 V VIN(diff)= ±0.5V 4.955 min 0.030 0.060 V 0.060 max R L = 2kΩ to2.5V 4.936 V VIN(diff)= ±0.5V 0.075 V IO OutputCurrent Sourcing,VO = 0V 5.9 4.1 mA VIN(diff)= ±0.5V 1.5 min Sinking,VO = 5V 14.5 4.5 mA V IN(diff)= ±0.5V 1.5 min IS SupplyCurrent 0.75 1.0 mA 1.2 max AC ELECTRICAL CHARACTERISTICS TJ = 25°C, V+ = 5V,V -= 0V,VCM = 2.5V,VO = 2.5V,and R L > 1M Ω. Symbol Parameter Conditions Typ (1) Units SR Slew Rate AV = +1,VIN = 3.5Vpp 5 V/μs GBW Gain-BandwidthProduct 6 MHz θ m Phase Margin 75 Deg G m Gain Margin 12 dB en Input-ReferredVoltageNoise f= 0.1Hz 85 nV/√Hz enp-p Input-ReferredVoltageNoise R S = 100Ω,DC to10Hz 1.6 μVpp in Input-ReferredCurrentNoise f= 0.1Hz 180 fA/√Hz THD TotalHarmonicDistortion f= 1kHz,Av = -2 0.02 % R L = 10kΩ,VO = 4.5Vpp trec InputOverloadRecoveryTime 50 ms TS OutputSettlingtime See (2) 1% 250 ns AV = +1,1V step 0.1% 400 0.01% 3200 See (2) 1% 80 AV = −1,1V step 0.1% 860 0.01% 1400 (1) Typicalvaluesrepresentthemost likelyparametricnorm. (2) Settlingtimesshown correspondtotheworse case (positiveornegativestep)and does notincludeslewtime.See theApplicationNote sectionfortestschematic. Copyright© 1999–2013,Texas InstrumentsIncorporated SubmitDocumentationFeedback 3 ProductFolderLinks:LMC2001

SNOS011D –AUGUST 1999–REVISED APRIL 2013 www.ti.com TYPICAL PERFORMANCE CHARACTERISTICS TA=25C, VS= 5V unlessotherwisespecified. VOS Distribution VOS vs.VS Figure4. Figure5. VOS vs.VCM +IIN vs.VCM Figure6. Figure7. −IINvs.VCM eN vs.Frequency Figure8. Figure9.

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www.ti.com SNOS011D –AUGUST 1999–REVISED APRIL 2013 TYPICAL PERFORMANCE CHARACTERISTICS (continued) TA=25C, VS= 5V unlessotherwisespecified. CMRR vs.VCM CMRR vs.Frequency Figure10. Figure11. PSRR vs.Frequency VOUT + vs.VS Figure12. Figure13. VOUT + vs.VS VOUT − vs.VS Figure14. Figure15. Copyright© 1999–2013,Texas InstrumentsIncorporated SubmitDocumentationFeedback 5 ProductFolderLinks:LMC2001

SNOS011D –AUGUST 1999–REVISED APRIL 2013 www.ti.com TYPICAL PERFORMANCE CHARACTERISTICS (continued) TA=25C, VS= 5V unlessotherwisespecified. VOUT − vs.VS Gain-Phase vs.Temp Figure16. Figure17. Gain-Phase vs.VS Gain-Phase vs.R L Figure18. Figure19. Gain-Phase vs.C LOAD THD+N vs.Frequency Figure20. Figure21.

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www.ti.com SNOS011D –AUGUST 1999–REVISED APRIL 2013 TYPICAL PERFORMANCE CHARACTERISTICS (continued) TA=25C, VS= 5V unlessotherwisespecified. THD+N vs VOUT Isourcevs.VOUT Figure22. Figure23. Isinkvs.VOUT Isupplyvs VS Figure24. Figure25. Copyright© 1999–2013,Texas InstrumentsIncorporated SubmitDocumentationFeedback 7 ProductFolderLinks:LMC2001

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APPLICATION INFORMATION

The BenefitsofLMC2001 No 1/fNoise Using patentedmethods,the LMC2001 eliminatesthe 1/fnoisepresentinotheramplifiers.Thisnoisewhich increasesas frequencydecreasesisa major sourceof measurement errorinallDC coupledmeasurements. Low frequencynoiseappearsas a constantlychangingsignalinserieswithany measurement beingmade. As a result,even when themeasurement ismade rapidly,thisconstantlychangingnoisesignalwillcorrupttheresult. The valueof thisnoisesignalcan be surprisinglylarge.For example:Ifa conventionalamplifierhas a high frequencynoiselevelof10nV/√Hz and a noisecornerof10 Hz,theRMS noiseat0.001Hz is1µV/√Hz Thisisequivalenttoa 6µV peak-to-peakerror.Ina circuitwitha gainof1000,thisproducesa 6mV peak-to-peak outputerror.Thisnumber of 0.001 Hz mightappear unreasonablylow but when a data acquisitionsystem is operatingfor17 minutesithas been on longenough toincludethiserror.Inthissame time,theLMC2001 will onlyhave a 0.51mV outputerror.Thisismore than13.3timeslesserror. Keep inmind thatthis1/ferrorgetseven largeratlowerfrequencies. At theextreme,many peopletrytoreducethiserrorby integratingortakingseveralsamples ofthesame signal. Thisisalsodoomed tofailurebecause the1/fnatureofthisnoisemeans thattakinglongersamples justmoves themeasurement intolowerfrequencieswhere thenoiseleveliseven higher. The LMC2001 eliminatesthissourceof error.The noiselevelisconstantwithfrequencyso thatreducingthe bandwidthreducestheerrorscaused by noise. Anothersourceoferrorthatisrarelymentionedistheerrorvoltagescaused by theinadvertentthermocouples createdwhen thecommon “Kovar type” package leadmaterialsare solderedtoa copperprintedcircuitboard. These steelbased leadframematerialscan produceover35uV/°C when solderedontoa coppertrace.Thiscan resultinthermocouplenoisethatisequaltotheLMC2001 noisewhen thereisa temperaturedifferenceofonly 0.0014°C between theleadand theboard! For thisreason,theleadframeoftheLMC2001 ismade ofcopper.Thisresultsinequaland oppositejunctions which cancelthiseffect.The extremelysmallsizeoftheSOT-23 package resultsintheleadsbeingveryclose together.Thisfurtherreducestheprobabilityoftemperaturedifferencesand hence decreasesthermalnoise. Overload Recovery The LMC2001 recoversfrom inputoverloadmuch fasterthanmost chopperstabilizedopamps. Recovery,from drivingtheamplifierto2X thefullscaleoutput,onlyrequiresabout50ms. Most chopperstabilizedamplifierswill takefrom 250ms toseveralseconds torecoverfrom thissame overload.Thisisbecause largecapacitorsare used tostoretheunadjustedoffsetvoltage. The wide bandwidthoftheLMC2001 enhances performancewhen itisused as an amplifiertodriveloadsthat injecttransientsback intotheoutput.A toDs and multiplexersareexamples ofthistypeofload.To simulatethis typeofload,a pulsegeneratorproducinga 1V peak squarewave was connectedtotheoutputthrougha 10pF capacitor.(Figure26)The typicaltimefortheoutputtorecoverto1% oftheappliedpulseis80ns.To recoverto 0.1% requires860ns.Thisrapidrecoveryisdue tothewidebandwidthoftheoutputstageand largetotalGBW. Figure26. No ExternalCapacitorsRequired The LMC2001 does notneed externalcapacitors.Thiseliminatestheproblemscaused by capacitorleakageand dielectricabsorption,whichcan cause delaysofseveralsecondsfromturn-onuntiltheamplifierissettled.

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www.ti.com SNOS011D –AUGUST 1999–REVISED APRIL 2013 More Benefits The LMC2001 offersthebenefitsmentionedabove and more.Itisrail-to-railoutputand consumes only750µA of supplycurrentwhileprovidingexcellentDC and AC electricalperformance.In DC performance,the LMC2001 achieves120dB of CMRR, 120dB of PSRR and 137dB of open loopgain.In AC performance,the LMC2001 provides6MHz ofgain-bandwidthproductand 5V/µs ofslewrate. How theLMC2001 Works The LMC2001 uses new, patentedtechniquesto achievethe high DC accuracytraditionallyassociatedwith chopper stabilizedamplifierswithoutthe major drawbacks produced by chopping.The LMC2001 continuously monitorsthe inputoffsetand correctsthiserror.The conventionalchoppingprocessproduces many mixing products,bothsums and differences,between thechoppingfrequencyand theincomingsignalfrequency.This mixingcauses largeamounts of distortion,particularlywhen the signalfrequencyapproaches the chopping frequency.Even withoutan incomingsignal,thechopperharmonicsmix witheach othertoproduceeven more trash.Ifthissounds unlikelyor difficultto understand,lookat the plot(Figure27),of the outputof a typical (MAX432) chopperstabilizedopamp. Thisistheoutputwhen thereisno incomingsignal,justtheamplifierina gainof-10 withtheinputgrounded.The chopperisoperatingatabout150Hz, therestismixingproducts.Add an inputsignaland themess getsmuch worse.Compare thisplotwithFigure28 oftheLMC2001. Thisdatawas takenunder theexactsame conditions.The autozeroactionisvisibleatabout11kHz butnotetheabsence of mixingproductsatotherfrequencies.As a result,theLMC2001 has verylow distortionof0.02% and verylow mixingproducts. InputCurrents The LMC2001 inputcurrentisdifferentthan standardbipolaror CMOS inputcurrentsinthatitappears as a currentflowingin one inputand out the other.Under most operatingconditions,these currentsare in the picoamp leveland willhave littleorno effectinmost circuits.These currentsincreasetothenA levelwhen the common-mode voltageisnear theminus supply.(seetheTYPICAL PERFORMANCE CHARACTERISTICS ) At hightemperaturessuch as 85°C, theinputcurrentsbecome larger,0.5nA typical,and are bothpositiveexcept when theVcm isnearV−.Ifoperationisexpectedatlow common-mode voltagesand hightemperature,do not add resistanceinserieswiththeinputstobalancetheimpedances.Doing thiscan cause an increaseinoffset voltage. Figure27. Copyright© 1999–2013,Texas InstrumentsIncorporated SubmitDocumentationFeedback 9 ProductFolderLinks:LMC2001

SNOS011D –AUGUST 1999–REVISED APRIL 2013 www.ti.com Figure28. ThisStrain-Gauge(Figure29) amplifierprovideshighgain(1006 or 60 dB) withverylow offsetand drift.Using theresistorstoleranceas shown, theworstcase CMRR willbe greaterthan90 dB. The common-mode gainis directlyrelatedtotheresistormismatch and isindependentofthedifferentialgainthatissetby R3. The worst case common-mode gain is−54 dB. This gain becomes even lower,improvingCMRR, ifthe resistorratio matchingisimproved. (1) ExtendingSupply Voltagesand Output Swing by Using a Composite AmplifierConfiguration: Incases where substantiallyhigheroutputswing isrequiredwithhighersupplyvoltages,arrangementslikethe ones shown inFigure30,and Figure31 couldbe used (pinnumbers shown are forSOIC-8 package).These configurationsutilizetheexcellentDC performanceoftheLMC2001 whileatthesame timeallowthesuperior voltageand frequencycapabilitiesoftheLM6171 tosetthedynamic performanceoftheoverallamplifier.For example,itispossibletoachieve±12V outputswing with300MHz ofoverallGBW (Av=100)whilekeepingthe worstcase outputshiftdue toVos lessthan4mV. The LMC2001 outputvoltageiskeptataboutmid-pointofit's overallsupplyvoltageand it'sinputcommon mode voltagerange allowstheV- terminaltobe grounded inone case (Figure30, invertingoperation)and tiedto a smallnon-criticalnegativebiasinanother(Figure31, non- invertingoperation).Higherclosedloop gainsare alsopossiblewitha correspondingreductionin realizable bandwidth.Table 1 shows some otherclosedloopgainpossibilitiesalongwiththe measured performancein each case ApplicationCircuits Figure29. SingleSupply Strain-Gauge Amplifier

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www.ti.com SNOS011D –AUGUST 1999–REVISED APRIL 2013 Figure30. InvertingComposite Amplifier Figure31. Non-InvertingComposite Amplifier Copyright© 1999–2013,Texas InstrumentsIncorporated SubmitDocumentationFeedback 11 ProductFolderLinks:LMC2001

SNOS011D –AUGUST 1999–REVISED APRIL 2013 www.ti.com Table1.Composite AmplifierMeasured Performance Av R1 R2 C2 BW SR enpp (ohm) (ohm) (pF) (MHz) (V/us) (mVpp) 50 200 10K 8 3.3 178 37 100 100 10K 10 2.5 174 70 100 1K 100K 0.67 3.1 170 70 500 200 100K 1.75 1.4 96 250 1000 100 100K 2.2 0.98 64 400 In terms of the measured outputpeak-to-peaknoise,the followingrelationshipholdsbetween outputnoise voltage,enpp,fordifferentclosedloopgain,Av,settings,where -3dB BandwidthisBW: (2) Itshouldbe keptinmind thatinordertominimizetheoutputnoisevoltagefora givenclosedloopgainsetting, one couldminimizetheoverallbandwidth.As can be seen from Equation2 above,theimprovementinoutput noisehas a squarelawrelationshiptothereductioninBW. In the case of the invertingconfiguration,itisalsopossibleto increasethe inputimpedance of the overall amplifier,by raisingthevalueofR1, withouthavingtoincreasethefeedbackresistor,R2, toimpracticalvalues, by utilizinga “T”networkas feedback.See theLMC6442 datasheet(ApplicationNotes section)formore details on this. LMC2001 as ADC InputAmplifier The LMC2001 isa greatchoiceforan amplifierstageimmediatelybeforetheinputofan A/D converter(AC or DC coupled)see Figure32 and Figure33 because ofthefollowingimportantcharacteristics: a. Very low offsetvoltageand offsetvoltagedriftover timeand temperatureallowa highclosedloopgain settingwithoutintroducingany shorttermorlongtermerrors.For example,when settoa closedloopgainof 100 as theanaloginputamplifierofa 12 bitA/D converter,theoverallconversionerroroverfulloperation temperatureand 30 yearslifeofthepart(operatingat50°C) wouldbe lessthan5LSB. b. Fast largesignalsettlingtimeto 0.01% of finalvalue(1.4us) allows12 bitaccuracyat 100KHz or more samplingrate. c. No flicker(1/f)noisemeans unsurpasseddata accuracyover any measurement periodof time,no matter how long.Considerthefollowingopamp performance,based on a typicalcommerciallyavailabledevice,for comparison: Opamp flatbandnoise 8nV/√Hz 1/f0.94 cornerfrequency100Hz f(max) 100Hz Av 100 Measurement time100 sec The example above, willresultin about 3mVpp (2.5LSB)of outputnoisecontributiondue to the opamp alone,compared toabout420 uVpp (lessthan1LSB) when thatopamp isreplacedwiththeLMC2001 which has no 1/fcontribution.Ifthe measurement time isincreasedfrom 100 sec.to 1 hr.,the improvement realizedby usingtheLMC2001 would be a factorofabout44 times(18.5mVpp compared to420uV when LMC2001 isused)mainlybecause theLMC2001 accuracyisnotcompromised by increasingtheobservation time. d. Copper leadframeconstructionminimizesany thermocoupleeffectswhichwoulddegradelowlevel/highgain dataconversionapplicationaccuracy(seediscussionunder“The BenefitsofLMC2001 No 1/fNoise”section above). e. Rail-to-Railoutputswing maximized the ADC dynamic range in 5V singlesupplyconverterapplications. Below are some typicalblockdiagramsshowing the LMC2001 used as an ADC amplifier(Figure32 and Figure33).

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www.ti.com SNOS011D –AUGUST 1999–REVISED APRIL 2013 Figure32. Figure33. Copyright© 1999–2013,Texas InstrumentsIncorporated SubmitDocumentationFeedback 13 ProductFolderLinks:LMC2001

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REVISION HISTORY

Changes from RevisionC (April2013)toRevisionD Page

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