LM6211 TI | Alldatasheet

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FREQUENCY (Hz) 100 1000 100 VOLTAGE NOISE (nV/ Hz) VS = 5V, 24V - VCO INPUT CHARGE PUMP OUTPUT VS_PLL LM6211 www.ti.com SNOSAH2C –FEBRUARY 2006–REVISED MARCH 2013 LM6211LowNoise,RRO OperationalAmplifierwithCMOS Inputand24VOperation Check forSamples: LM6211 1FEATURES • Temperature Range -40°C to125°C 2(Typical24V Supply Unless OtherwiseNoted) • TotalHarmonic Distortion0.01% @ 1 kHz, 600Ω• Supply VoltageRange 5V to24V

  • Output ShortCircuitCurrent25 mA• InputReferredVoltageNoise 5.5nV/√Hz APPLICATIONS• UnityGain Bandwidth 20 MHz
  • PLL Loop Filters• 1/fCorner Frequency 400 Hz
  • Low Noise ActiveFilters• Slew Rate 5.6V/μs
  • StrainGauge Amplifiers• Supply Current1.05mA
  • Low Noise Microphone Amplifiers• Low InputCapacitance5.5pF

DESCRIPTION

The LM6211 isa wide bandwidth,low noiseop amp witha wide supplyvoltagerange and a low inputbias current.The LM6211 operateswitha singlesupplyvoltageof 5V to 24V, isunitygainstable,has a ground- sensingCMOS inputstage,and offersrail-to-railoutputswing. The LM6211 isdesignedtoprovideoptimalperformanceinhighvoltage,low noisesystems.The LM6211 has a unitygain bandwidthof 20 MHz and an inputreferredvoltagenoisedensityof 5.5 nV/√Hz at 10 kHz. The LM6211 achievesthesespecificationswitha low supplycurrentofonly1 mA. The LM6211 has a low inputbias currentof2.3pA, an outputshortcircuitcurrentof25 mA and a slewrateof5.6V/us.The LM6211 alsofeatures a low common-mode inputcapacitanceof5.5pF which makes itidealforuse inwide bandwidthand highgain circuits.The LM6211 iswellsuitedforlow noiseapplicationsthatrequirean op amp withverylow inputbias currentsand a largeoutputvoltageswing,likeactiveloop-filtersforwide-bandPLLs. A low totalharmonic distortion,0.01% at1 kHz withloadsas highas 600Ω,alsomakes theLM6211 idealforhighfidelityaudioand microphoneamplifiers. The LM6211 isavailablein the smallSOT-23 package,allowingthe user to implementultra-smalland cost effectiveboardlayouts. TypicalApplication These deviceshave limitedbuilt-inESD protection.The leadsshouldbe shortedtogetherorthedeviceplacedinconductivefoam duringstorageorhandlingtopreventelectrostaticdamage totheMOS gates. Pleasebe aware thatan importantnoticeconcerningavailability,standardwarranty,and use incriticalapplicationsof Texas Instrumentssemiconductorproductsand disclaimerstheretoappearsattheend ofthisdatasheet. 2Alltrademarksarethepropertyoftheirrespectiveowners. PRODUCTION DATA informationiscurrentas ofpublicationdate. Copyright© 2006–2013,Texas InstrumentsIncorporatedProductsconform to specificationsper the terms of the Texas Instrumentsstandardwarranty.Productionprocessingdoes not necessarilyincludetestingofallparameters.

SNOSAH2C –FEBRUARY 2006–REVISED MARCH 2013 www.ti.com AbsoluteMaximum Ratings(1)(2) ESD Tolerance(3) Human Body Model 2000V Machine Model 200V VIN Differential ±0.3V SupplyVoltage(VS = V+ – V−) 25V VoltageatInput/Outputpins V+ +0.3V,V− −0.3V StorageTemperatureRange −65°C to+150°C JunctionTemperature(4) +150°C SolderingInformation InfraredorConvection(20sec) 235°C Wave SolderingLead Temp. (10sec) 260°C (1) AbsoluteMaximum Ratingsindicatelimitsbeyond whichdamage tothedevicemay occur.OperatingRatingsindicateconditionsfor whichthedeviceisintendedtobe functional,butspecificperformanceisnotensured.Forensuredspecificationsand thetest conditions,see theElectricalCharacteristicsTables. (2) IfMilitary/Aerospacespecifieddevicesarerequired,pleasecontacttheTISalesOffice/Distributorsforavailabilityand specifications. (3) Human Body Model is1.5kΩ inserieswith100 pF.Machine Model is0Ω inserieswith200 pF. (4) The maximum power dissipationisa functionofTJ(MAX),θJA,and TA.The maximum allowablepower dissipationatany ambient temperatureisPD = (TJ(MAX) -TA)/θJA .Allnumbers applyforpackagessoldereddirectlyontoa PC board. OperatingRatings(1) TemperatureRange −40°C to+125°C SupplyVoltage(VS = V+ – V−) 5V to24V Package ThermalResistance(θJA (2)) 5-PinSOT-23 178°C/W (1) AbsoluteMaximum Ratingsindicatelimitsbeyond whichdamage tothedevicemay occur.OperatingRatingsindicateconditionsfor whichthedeviceisintendedtobe functional,butspecificperformanceisnotensured.Forensuredspecificationsand thetest conditions,see theElectricalCharacteristicsTables. (2) The maximum power dissipationisa functionofTJ(MAX),θJA,and TA.The maximum allowablepower dissipationatany ambient temperatureisPD = (TJ(MAX) -TA)/θJA .Allnumbers applyforpackagessoldereddirectlyontoa PC board. 5V ElectricalCharacteristics(1) Unlessotherwisespecified,alllimitsareensuredforTA = 25°C, V+ = 5V,V− = 0V,VCM = VO = V+/2.Boldfacelimitsapplyat thetemperatureextremes. Symbol Parameter Conditions Min (2) Typ (3) Max (2) Units VOS InputOffsetVoltage VCM = 0.5V 0.1 ±2.5 mV±2.8 TC VOS InputOffsetAverageDrift VCM = 0.5V(4) 2 μV/C IB InputBiasCurrent VCM = 0.5V(5)(6) 0.5 5 pA 10 nA IOS InputOffsetCurrent VCM = 0.5V 0.1 pA CMRR Common Mode RejectionRatio 0 V ≤ VCM ≤ 3V 83 98 dB0.4V ≤ VCM ≤ 2.3V 70 PSRR Power SupplyRejectionRatio V+ = 5V to24V,VCM = 0.5V 85 98 dB78 V+ = 4.5Vto25V,VCM = 0.5V 80 95 CMVR InputCommon-Mode Voltage CMRR ≥ 65 dB 0 3.3 VRange CMRR ≥ 60 dB 0 2.4 (1) Electricaltablevaluesapplyonlyforfactorytestingconditionsatthetemperatureindicated.Factorytestingconditionsresultinvery limitedself-heatingofthedevice. (2) Limitsare100% productiontestedat25°C. Limitsovertheoperatingtemperaturerangeareensuredthroughcorrelationsusingthe StatisticalQualityControl(SQC) method. (3) Typicalvaluesrepresentthemost likelyparametricnorm atthetimeofcharacterization. (4) Offsetvoltageaveragedriftisdeterminedby dividingthechange inVOS atthetemperatureextremesintothetotaltemperaturechange. (5) Positivecurrentcorrespondstocurrentflowingintothedevice. (6) Inputbiascurrentisensuredby design.

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www.ti.com SNOSAH2C –FEBRUARY 2006–REVISED MARCH 2013 5V ElectricalCharacteristics(1)(continued) Unlessotherwisespecified,alllimitsareensuredforTA = 25°C, V+ = 5V,V− = 0V,VCM = VO = V+/2.Boldfacelimitsapplyat thetemperatureextremes. Symbol Parameter Conditions Min (2) Typ (3) Max (2) Units AVOL LargeSignalVoltageGain VO = 0.35Vto4.65,R L = 2 kΩ toV+/2 82 110 dB VO = 0.25Vto4.75,R L = 10 kΩ toV+/2 85 110 VO OutputSwing High R L = 2 kΩ toV+/2 50 150 165 R L = 10 kΩ toV+/2 20 85 90 mV from railOutputSwing Low R L = 2 kΩ toV+/2 39 150 170 R L = 10 kΩ toV+/2 13 85 IOUT OutputShortCircuitCurrent SourcingtoV+/2 13 16 VID = 100 mV (7) 10 mA SinkingtoV+/2 20 30 VID = −100 mV (7) 10 IS SupplyCurrent 0.96 1.10 mA1.25 SR Slew Rate AV = +1,10% to90% (8) 5.5 V/μs GBW Gain BandwidthProduct 17 MHz en Input-ReferredVoltageNoise f= 10 kHz 5.5 nV/√Hz f= 1 kHz 6.0 in Input-ReferredCurrentNoise f= 1 kHz 0.01 pA/√Hz THD TotalHarmonicDistortion AV = 2,R L = 600Ω toV+/2 0.01 % (7) The deviceisshortcircuitprotectedand can sourceorsinkitslimitcurrentscontinuously.However,careshouldbe takensuch that when theoutputisdrivingshortcircuitcurrents,theinputsdo notsee more than±0.3Vdifferentialvoltage. (8) Slew rateistheaverageoftherisingand fallingslewrates. 24V ElectricalCharacteristics(1) Unlessotherwisespecified,alllimitsareensuredforTA = 25°C, V+ = 24V,V− = 0V,VCM = VO = V+/2.Boldfacelimitsapplyat thetemperatureextremes. Symbol Parameter Conditions Min (2) Typ (3) Max (2) Units VOS InputOffsetVoltage VCM = 0.5V 0.25 ±2.7 mV±3.0 TC VOS InputOffsetAverageDrift VCM = 0.5V(4) ±2 μV/C IB InputBiasCurrent VCM = 0.5V(5)(6) 2 25 pA 10 nA IOS InputOffsetCurrent VCM = 0.5V 0.1 pA CMRR Common Mode RejectionRatio 0 ≤ VCM ≤ 21V 85 105 dB0.4≤ VCM ≤ 20V 70 PSRR Power SupplyRejectionRatio V+ = 5V to24V,VCM = 0.5V 85 98 78 dB V+ = 4.5Vto25V,VCM = 0.5V 80 98 CMVR InputCommon-Mode Voltage CMRR ≥ 65 dB 0 21.5 VRange CMRR ≥ 60 dB 0 20.5 (1) Electricaltablevaluesapplyonlyforfactorytestingconditionsatthetemperatureindicated.Factorytestingconditionsresultinvery limitedself-heatingofthedevice. (2) Limitsare100% productiontestedat25°C. Limitsovertheoperatingtemperaturerangeareensuredthroughcorrelationsusingthe StatisticalQualityControl(SQC) method. (3) Typicalvaluesrepresentthemost likelyparametricnorm atthetimeofcharacterization. (4) Offsetvoltageaveragedriftisdeterminedby dividingthechange inVOS atthetemperatureextremesintothetotaltemperaturechange. (5) Positivecurrentcorrespondstocurrentflowingintothedevice. (6) Inputbiascurrentisensuredby design. Copyright© 2006–2013,Texas InstrumentsIncorporated SubmitDocumentationFeedback 3 ProductFolderLinks:LM6211

+ - LM6211 SNOSAH2C –FEBRUARY 2006–REVISED MARCH 2013 www.ti.com 24V ElectricalCharacteristics(1)(continued) Unlessotherwisespecified,alllimitsareensuredforTA = 25°C, V+ = 24V,V− = 0V,VCM = VO = V+/2.Boldfacelimitsapplyat thetemperatureextremes. Symbol Parameter Conditions Min (2) Typ (3) Max (2) Units AVOL LargeSignalVoltageGain VO = 1.5Vto22.5V,R L = 2 kΩ toV+/2 82 120 dB VO = 1V to23V,R L = 10 kΩ toV+/2 85 120 VO OutputSwing High R L = 2 kΩ toV+/2 212 400 520 R L = 10 kΩ toV+/2 48 150 165 mV from railOutputSwing Low R L = 2 kΩ toV+/2 150 350 420 R L = 10 kΩ toV+/2 38 150 170 IOUT OutputShortCircuitCurrent SourcingtoV+/2 20 25 VID = 100 mV (7) 15 mA SinkingtoV+/2 30 38 VID = −100 mV (7) 20 IS SupplyCurrent 1.05 1.25 mA1.40 SR Slew Rate AV = +1,VO = 18 VPP 5.6 V/μs 10% to90% (8) GBW Gain BandwidthProduct 20 MHz en Input-ReferredVoltageNoise f= 10 kHz 5.5 nV/√Hz f= 1 kHz 6.0 in Input-ReferredCurrentNoise f= 1 kHz 0.01 pA/√Hz THD TotalHarmonicDistortion AV = 2,R L = 2 kΩ toV+/2 0.01 % (7) The deviceisshortcircuitprotectedand can sourceorsinkitslimitcurrentscontinuously.However,careshouldbe takensuch that when theoutputisdrivingshortcircuitcurrents,theinputsdo notsee more than±0.3Vdifferentialvoltage. (8) Slew rateistheaverageoftherisingand fallingslewrates. Connection Diagram Figure1. 5-PinSOT-23 -Top View

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0 0.5 1 1.5 2 2.5 3 3.5 4 VCM (V) -1.5 -0.5 0.5 IBIAS (pA) -40° C 25° C VS = 5V 0 0.5 1 1.5 2 2.5 3 3.5 4 -2.5 2.5 IBIAS (nA) VCM (V) -1.5 -0.5 0.5 1.5

2 VS = 5V

125° C 0 0.5 1 1.5 2 2.5 3 3.5 -0.6 -0.2 0.4 0.6 VOS (mV) VCM (V) 0.8 0.2 -0.4 -0.8 125° C -40° C 25° C VS = 5V 0 2 4 6 16 18 20 22 VCM (V) -0.6 -0.4 -0.2 0.2 0.4 0.6 0.8 VOS (mV) 8 10 12 14 VS = 24V -40° C 25° C 125° C 5 7 9 11 13 15 17 19 21 23 0.5 0.6 0.8 1.1 1.2 1.4 SUPPLY CURRENT (mA) VS (V) 1.3 0.9 0.7 125° C 25° C -40° C 5 7 9 11 13 15 17 19 21 23 -0.6 -0.4 -0.2 0.2 0.4 0.8 VOS (mV) VS (V) 0.6 125° C 25° C -40° C LM6211 www.ti.com SNOSAH2C –FEBRUARY 2006–REVISED MARCH 2013 TypicalPerformance Characteristics Unlessotherwisespecified,TA = 25°C, VS = 24V,V+ = VS,V− = 0 V,VCM = VS/2. Supply Current VOS vs. vs. Supply Voltage Supply Voltage Figure2. Figure3. VOS VOS vs. vs. VCM VCM Figure4. Figure5. InputBias Current InputBias Current vs. vs. VCM VCM Figure6. Figure7. Copyright© 2006–2013,Texas InstrumentsIncorporated SubmitDocumentationFeedback 5 ProductFolderLinks:LM6211

4 6 8 10 12 14 16 18 20 22 24 VOUT FROM RAIL (mV) VS (V) R L = 10 k: 125° C -40° C 25° C 4 6 8 10 12 14 16 18 20 22 24 VOUT FROM RAIL (mV) VS (V) R L = 10 k: 125° C -40° C 25° C 4 6 8 10 12 14 16 18 20 22 24 VS (V) ISOURCE (mA) 125° C -40° C 25° C ISINK (mA) VS (V) 4 6 8 10 12 14 16 18 20 22 24 -40° C 25° C 125° C 25° C 0 2 4 6 8 10 12 14 16 18 20 IBIAS (pA) VCM (V) -40° C VS = 24V 0 2 4 6 8 10 12 14 16 18 20 IBIAS (nA) VCM (V) 125° C VS = 24V LM6211 SNOSAH2C –FEBRUARY 2006–REVISED MARCH 2013 www.ti.com TypicalPerformance Characteristics(continued) Unlessotherwisespecified,TA = 25°C, VS = 24V,V+ = VS,V− = 0 V,VCM = VS/2. InputBias Current InputBias Current vs. vs. VCM VCM Figure8. Figure9. Sourcing Current SinkingCurrent vs. vs. Supply Voltage Supply Voltage Figure10. Figure11. PositiveOutput Swing NegativeOutput Swing vs. vs. Supply Voltage Supply Voltage Figure12. Figure13.

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25° C 0 4 8 12 16 20 24 VOUT (V) ISOURCE (mA) 125° C -40° C VS = 24V -40° C 0 4 8 12 16 20 24 ISINK (mA) VOUT (V) VS = 24V 25° C 125° C 125° C 0 1 2 3 4 5 ISINK (mA) VOUT (V) VS = 5V -40° C 25° C 125° C 0 1 2 3 4 5 ISOURCE (mA) VOUT (V) VS = 5V -40° C 25° C 4 6 8 10 12 14 16 18 20 22 24 100 150 200 250 300 350 VOUT FROM RAIL (mV) VS (V) R L = 2 k: 125° C -40° C 25° C 4 6 8 10 12 14 16 18 20 22 24 100 150 200 250 VOUT FROM RAIL (mV) VS (V) -40° C R L = 2 k: 125° C 25° C LM6211 www.ti.com SNOSAH2C –FEBRUARY 2006–REVISED MARCH 2013 TypicalPerformance Characteristics(continued) Unlessotherwisespecified,TA = 25°C, VS = 24V,V+ = VS,V− = 0 V,VCM = VS/2. PositiveOutput Swing NegativeOutput Swing vs. vs. Supply Voltage Supply Voltage Figure14. Figure15. Sourcing Current SinkingCurrent vs. vs. Output Voltage Output Voltage Figure16. Figure17. Sourcing Current SinkingCurrent vs. vs. Output Voltage Output Voltage Figure18. Figure19. Copyright© 2006–2013,Texas InstrumentsIncorporated SubmitDocumentationFeedback 7 ProductFolderLinks:LM6211

0.001 0.01 0.1 1 10 OUTPUT AMPLITUDE (V) 0.0001 0.001 0.01 0.1 THD+N (%) R L = 600: R L = 100 k: VS = 5V 0.001 0.1 100 OUTPUT AMPLITUDE (V) 0.0001 0.01 THD+N (%) 1010.01 0.1 0.001 R L = 100 k: R L = 600: Vs = 24V 1 10 1k 10k 100k FREQUENCY (Hz) 100 1000 100 VOLTAGE NOISE (nV/ Hz) VS = 5V, 24V 10 100 1k 10k 100k FREQUENCY (Hz) 0.0001 0.001 0.01 0.1 THD+N (%) R L = 600:, VS = 5V R L = 600:, VS = 24V R L = 100 k:, VS = 24V R L = 100 k:, VS = 5V 100 10k 1M 100M FREQUENCY (Hz) -40 100 180 GAIN (dB) 10M100k1k 160 140 120 -20 -40 100 180 160 140 120 -20 PHASE (° ) GAIN PHASE 100 10k 1M 100M FREQUENCY (Hz) -40 100 180 GAIN (dB) 10M100k1k 160 140 120 -20 -40 100 180 160 140 120 -20 PHASE (° ) GAIN PHASE C L = 20 pF C L = 50 pF CL = 100 pF C L = 20 pF, 50 pF, 100 pF LM6211 SNOSAH2C –FEBRUARY 2006–REVISED MARCH 2013 www.ti.com TypicalPerformance Characteristics(continued) Unlessotherwisespecified,TA = 25°C, VS = 24V,V+ = VS,V− = 0 V,VCM = VS/2. Open Loop Gain and Phase withResistiveLoad Open Loop Gain and Phase withCapacitiveLoad Figure20. Figure21. InputReferredVoltageNoise THD+N vs. vs. Frequency Frequency Figure22. Figure23. THD+N THD+N vs. vs. Output Amplitude Output Amplitude Figure24. Figure25.

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CAPACITIVE LOAD (pF) 10 100 10000 PHASE MARGIN (° ) VS = 5V R L = 2 k: R L = 10 k: R L = 10 M: CAPACITIVE LOAD (pF) 10 100 10000 PHASE MARGIN (° ) VS = 24V R L = 2 k: R L = 10 k: R L = 10 M: 0 1 2 3 4 5 6 7 8 9 10 -0.015 -0.01 -0.005 0.005 0.01 0.015 VOUT (V) TIME (Ps) VS = 24V C L = 10 pF 0 1 2 3 4 5 6 7 8 9 10 VOUT (V) TIME (Ps) VS = 24V C L = 10 pF 5 7 9 11 13 15 17 19 21 23 25 4.4 4.6 4.8 5.2 5.4 5.6 5.8 SLEW RATE (V/ Ps) VS (V) FALLING EDGE RISING EDGE 15 25 35 45 55 OVERSHOOT AND UNDERSHOOT (%) CAPACITIVE LOAD (pF) OVERSHOOT % UNDERSHOOT % LM6211 www.ti.com SNOSAH2C –FEBRUARY 2006–REVISED MARCH 2013 TypicalPerformance Characteristics(continued) Unlessotherwisespecified,TA = 25°C, VS = 24V,V+ = VS,V− = 0 V,VCM = VS/2. Slew Rate Overshoot and Undershoot vs. vs. Supply Voltage CapacitiveLoad Figure26. Figure27. Small SignalTransientResponse Large SignalTransientResponse Figure28. Figure29. Phase Margin Phase Margin vs. vs. CapacitiveLoad (Stability) CapacitiveLoad (Stability) Figure30. Figure31. Copyright© 2006–2013,Texas InstrumentsIncorporated SubmitDocumentationFeedback 9 ProductFolderLinks:LM6211

FREQUENCY (Hz) -120 -80 CMRR (dB) 100k10k100 -20 -60 -100 -40 VS = 5V VS = 24V 10 1k 100k 10M FREQUENCY (Hz) 0.001 0.1 100 ZOUT (:) 1M10k100 0.01 VS = 5V VS = 24V 10 1k 100k 10M FREQUENCY (Hz) -120 -40 PSRR (dB) 1M10k100 -20 -60 -80 -100 VS = 5V, -PSRR VS = 5V, +PSRR VS = 24V, -PSRR VS = 24V, +PSRR LM6211 SNOSAH2C –FEBRUARY 2006–REVISED MARCH 2013 www.ti.com TypicalPerformance Characteristics(continued) Unlessotherwisespecified,TA = 25°C, VS = 24V,V+ = VS,V− = 0 V,VCM = VS/2. Closed Loop Output Impedance PSRR vs. vs. Frequency Frequency Figure32. Figure33. CMRR vs. Frequency Figure34.

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www.ti.com SNOSAH2C –FEBRUARY 2006–REVISED MARCH 2013 APPLICATION NOTES ADVANTAGES OF THE LM6211 High Supply Voltage,Low Power Operation The LM6211 has performanceensured at supplyvoltagesof 5V and 24V. The LM6211 is ensured to be operationalat allsupplyvoltagesbetween 5V and 24V. In thislargerange of operation,the LM6211 draws a fairlyconstantsupplycurrentof1 mA, whileprovidinga wide bandwidthof20 MHz. The wide operatingrange makes the LM6211 a versatilechoicefora varietyof applicationsrangingfrom portableinstrumentationto industrialcontrolsystems. Low InputReferredNoise The LM6211 has verylow flatbandinputreferredvoltagenoise,5.5nV/√Hz. The 1/fcornerfrequency,alsovery low,isabout400 Hz. The CMOS inputstageallowsforan extremelylow inputcurrent(2 pA) and a verylow inputreferredcurrentnoise(0.01pA/√Hz).ThisallowstheLM6211 tomaintainsignalfidelityand makes itideal foraudio,wirelessorsensorbased applications. Low InputBias Currentand High InputImpedance The LM6211 has a CMOS inputstage,whichallowsittohave veryhighinputimpedance,verysmallinputbias currents(2 pA) and extremelylow inputreferredcurrentnoise(0.01pA/√Hz).This levelof performanceis essentialforop amps used insensorapplications,which dealwithextremelylow currentsoftheorderofa few nanoamperes.Inthiscase,theop amp isbeingdrivenby a sensor,whichtypicallyhas a sourceimpedance of tensofM Ω.Thismakes itessentialfortheop amp tohave a much higherimpedance. Low InputCapacitance The LM6211 has a comparativelysmall inputcapacitancefor a high voltageCMOS design.Low input capacitanceisverybeneficialintermsofdrivinglargefeedbackresistors,requiredforhigherclosedloopgain. Usually,highvoltageCMOS inputstageshave a largeinputcapacitance,which when used ina typicalgain configuration,interactswiththefeedbackresistancetocreatean extrapole.The extrapolecauses gain-peaking and can compromise thestabilityoftheop amp. The LM6211 can,however,be used withlargerresistorsdue to itssmallerinputcapacitance,and hence providemore gainwithoutcompromisingstability.Thisalsomakes the LM6211 idealforwideband transimpedanceamplifiers,whichrequirea wide bandwidth,low inputreferrednoise and lowinputcapacitance. RRO, Ground Sensing and CurrentLimiting The LM6211 has a rail-to-railoutputstage,whichprovidesthemaximum possibleoutputdynamic range.Thisis especiallyimportantforapplicationsrequiringa largeoutputswing,likewideband PLL synthesizerswhich need an activeloopfiltertodrivea wide frequencyrangeVCO. The inputcommon mode rangeincludesthenegative supplyrailwhich allowsdirectsensingat ground ina singlesupplyoperation.The LM6211 alsohas a short circuitprotectioncircuitwhich limitstheoutputcurrenttoabout25 mA sourcingand 38 mA sinking,and allows the LM6211 to driveshortcircuitloadsindefinitely.However, whiledrivingshortcircuitloadscare shouldbe takento preventthe inputsfrom seeingmore than ±0.3V differentialvoltage,which isthe absolutemaximum differentialinputvoltage. Small Size The smallfootprintof the LM6211 package saves space on printedcircuitboards,and enablesthe designof smallerand more compact electronicproducts.Long tracesbetween thesignalsourceand theop amp make the signalpathsusceptibletonoise.By usinga physicallysmallerpackage,theLM6211 can be placedclosertothe signalsource,reducingnoisepickupand enhancingsignalintegrity Copyright© 2006–2013,Texas InstrumentsIncorporated SubmitDocumentationFeedback 11 ProductFolderLinks:LM6211

+VIN R F C F R IN R LC L R S UNSTABLE ROC = 40 dB/decade STABLE ROC ± 20 dB/decade FREQUENCY (Hz) GAIN LM6211 SNOSAH2C –FEBRUARY 2006–REVISED MARCH 2013 www.ti.com STABILITY OF OP AMP CIRCUITS Stabilityand CapacitiveLoading The LM6211 isdesignedto be unitygain stableformoderate capacitiveloads,around 100 pF. That is,if connectedina unitygainbufferconfiguration,the LM6211 willresistoscillationunlessthe capacitiveloadis higherthanabout100 pF.For highercapacitiveloads,thephase marginoftheop amp reducessignificantlyand ittendstooscillate.Thisisbecause an op amp cannotbe designedtobe stableforhighcapacitiveloadswithout eithersacrificingbandwidthor supplyinghighercurrent.Hence, fordrivinghighercapacitiveloads,theLM6211 needs tobe externallycompensated. Figure35. Gain vs.Frequency foran Op Amp An op amp, ideally,has a dominantpoleclosetoDC, whichcauses itsgaintodecay attherateof20 dB/decade withrespectto frequency.Ifthisrateof decay, also known as the rateof closure(ROC), remains at 20 dB/decade attheunitygainbandwidthoftheop amp, theop amp isstable.If,however,a largecapacitanceis added totheoutputoftheop amp, itcombines withtheoutputimpedance oftheop amp tocreateanotherpole initsfrequencyresponsebeforeitsunitygainfrequency(Figure35).ThisincreasestheROC to40 dB/decade and causesinstability. Insuch a case a number oftechniquescan be used torestorestabilitytothecircuit.The ideabehindallthese schemes isto modifythe frequencyresponsesuch thatitcan be restoredto a ROC of 20 dB/decade,which ensuresstability. IntheLoop Compensation Figure36 illustratesa compensationtechnique,known as ‘in the loop’ compensation,thatemploys an RC feedback circuitwithinthe feedback loop to stabilizea non-invertingamplifierconfiguration.A smallseries resistance,R S,isused toisolatetheamplifieroutputfromtheloadcapacitance,C L,and a smallcapacitance,C F, isinsertedacrossthefeedbackresistortobypassC L athigherfrequencies. Figure36. IntheLoop Compensation

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C F = ¨¨ R F + 2RIN RF 2 C LR OUT R S = ROUT R IN R F LM6211 www.ti.com SNOSAH2C –FEBRUARY 2006–REVISED MARCH 2013 The valuesforR S and C F aredecidedby ensuringthatthezeroattributedtoC F liesatthesame frequencyas the poleattributedtoC L.Thisensuresthattheeffectofthesecond poleon thetransferfunctioniscompensated for by thepresenceofthezero,and thattheROC ismaintainedat20 dB/decade.For thecircuitshown inFigure36 thevaluesofR S and C F are givenby Equation1.Table1 shows differentvaluesofR S and C F thatneed tobe used formaintainingstabilitywithdifferentvaluesofC L,as wellas thephase marginstobe expected.R F and R IN areassumed tobe 10 kΩ,R L istakenas 2 kΩ,whileR OUT istakentobe 60Ω. (1) Table1. C L (pF) R S (Ω) C F (pF) Phase Margin(°) 250 60 4.5 39.8 300 60 5.4 49.5 500 60 9 53.1 Althoughthismethodologyprovidescircuitstabilityforany loadcapacitance,itdoes so atthepriceofbandwidth. The closedloopbandwidthofthecircuitisnow limitedby R S and C F. Compensation by ExternalResistor Insome applicationsitisessentialtodrivea capacitiveloadwithoutsacrificingbandwidth.Insuch a case,inthe loopcompensationisnotviable.A simplerscheme forcompensationisshown inFigure37.A resistor,R ISO,is placedinseriesbetween theloadcapacitanceand theoutput.T110hisintroducesa zerointhecircuittransfer function,whichcounteractstheeffectofthepoleformedby theloadcapacitance,and ensuresstability. Figure37. Compensation By IsolationResistor The valueof R ISO to be used shouldbe decideddependingon the sizeof C L and the levelof performance desired.Valuesrangingfrom5Ω to50Ω areusuallysufficienttoensurestability.A largervalueofR ISO willresult ina system withlesserringingand overshoot,butwillalsolimittheoutputswingand theshortcircuitcurrentof thecircuit. Stabilityand InputCapacitance In certainapplications,forexample I-Vconversion,transimpedancephotodiodeamplificationand bufferingthe outputof current-outputDAC, capacitiveloadingat the inputof the op amp can endanger stability.The capacitanceofthesourcedrivingtheop amp, theop amp inputcapacitanceand theparasitic/wiringcapacitance contributetotheloadingoftheinput.Thiscapacitance,C IN,interactswiththefeedbacknetworktointroducea peakingintheclosedloopgainofthecircuit,and hence causesinstability. Copyright© 2006–2013,Texas InstrumentsIncorporated SubmitDocumentationFeedback 13 ProductFolderLinks:LM6211

  • VCO INPUT CHARGE PUMP OUTPUT VS_PLL C IN R 1 R 2 VOUT VIN C F LM6211 SNOSAH2C –FEBRUARY 2006–REVISED MARCH 2013 www.ti.com Figure38. Compensating forInputCapacitance Thispeakingcan be eliminatedby addinga feedbackcapacitance,C F,as shown inFigure38.Thisintroducesa zero inthe feedbacknetwork,and hence a poleinthe closedloopresponse,and thusmaintainsstability.An optimalvalueof C F isgivenby Equation2. A simplerapproach isto selectC F = (R1/R2)CIN fora 90° phase margin.Thisapproach,however,limitsthebandwidthexcessively. TypicalApplications ACTIVE LOOP FILTER FOR PLLs A typicalphase lockedloop,or PLL, functionsby creatinga negativefeedbackloopintermsofthephase ofa signal.A simplePLL consistsofthreemain components:a phase detector,a loopfilterand a voltagecontrolled oscillator(VCO).The phase detectorcompares thephase oftheoutputofthePLL withthatofa referencesignal, and feedsthe errorsignalintothe loopfilter,thusperformingnegativefeedback.The loopfilterperformsthe importantfunctionofaveraging(orlow-passfiltering)theerrorand providingtheVCO witha DC voltage,which allowstheVCO tomodifyitsfrequencysuch thattheerrorisminimized.The performanceoftheloopfilteraffects a number ofspecificationsofthePLL,likeitsfrequencyrange,lockingtimeand phase noise. Sincea loopfilterisa verynoisesensitiveapplication,itisusuallysuggestedthatonlypassivecomponents be used initsdesign.Any activedevices,likediscretetransistorsorop amps, would add significantlytothenoiseof the circuitand would hence worsen the in-bandphase noiseof the PLL. But newer and fasterPLLs, likeTI’s LMX2430, have a power supplyvoltageoflessthan3V, which limitsthephase-detectoroutputofthePLL. Ifa passiveloopfilterisused withsuch circuits,thentheDC voltagethatcan be providedtotheVCO islimitedto coupleof volts.Thislimitsthe range of frequenciesforwhich the VCO, and hence the PLL, isfunctional.In certainapplicationsrequiringa wideroperatingrange of frequenciesforthe PLL, likeset-topboxes or base stations,thislevelofperformanceisnotadequateand requiresactiveamplification,hence theneed foractive loopfilters. An activeloopfiltertypicallyconsistsofan op amp, whichprovidesthegain,accompaniedby a threeorfourpole RC filter.The non-invertinginputoftheop amp isbiasedtoa fixedvalue,usuallythemid-supplyofthePLL, whilea feedbacknetworkprovidesthe gain as wellas one, or two,polesforlow pass filtering.Figure39 illustratesa typicalactiveloopfilter. Figure39. A TypicalActiveLoop Filter

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OFFSET FREQUENCY (Hz) -1.0 0.0 1.0 2.0 3.0 4.0 ADDED PHASE NOISE (dB) ACTIVE LOOP FILTER WITH LM6211 PASSIVE LOOP FILTER LM6211 www.ti.com SNOSAH2C –FEBRUARY 2006–REVISED MARCH 2013 Certainperformancecharacteristicsareessentialforan op amp ifitistobe used ina PLL loopfilter.Low input referredvoltageand currentnoiseareessential,as theydirectlyaffectthenoiseofthefilterand hence thephase noiseofthePLL. Low inputbiascurrentisalsoimportant,as biascurrentaffectsthelevelof‘referencespurs’, artifactsin the frequencyspectrum of the PLL caused by mismatch or leakageat the outputof the phase detector.A largeinputand outputswingisbeneficialintermsofincreasingtheflexibilityinbiasingtheop amp. The op amp can thenbe biasedsuch thattheoutputrangeofthePLL ismapped efficientlyontotheinputrange oftheVCO. With a CMOS input,ultralow inputbiascurrents(2 pA) and low inputreferredvoltagenoise(5.5nV/√Hz),the LM6211 isan idealop amp forusingina PLL activeloopfilter.The LM6211 has a groundsensinginputstage,a rail-to-railoutputstage,and an operatingsupplyrange of 5V - 24V, which makes ita versatilechoiceforthe designofa widevarietyofactiveloopfilters. Figure41 shows the LM6211 used withthe LMX2430 to createan RF frequencysynthesizer.The LMX2430 detectsthe PLL output,compares itwithitsinternalreferenceclockand outputsthe phase errorinterms of currentspikes.The LM6211 isused tocreatea loopfilterwhichaveragestheerrorand providesa DC voltageto theVCO. The VCO generatesa sinewave ata frequencydeterminedby theDC voltageatitsinput.Thiscircuit can provideoutputsignalfrequenciesas highas 2 GHz, much higherthan a comparativepassiveloopfilter. Compared toa similarpassiveloopfilter,theLM6211 doesn’tadd significantlytothephase noiseofthePLL, exceptattheedge oftheloopbandwidth,as shown inFigure40.A peakingofloopgainisexpected,sincethe loopfilterisdeliberatelydesignedtohave a wide bandwidthand a low phase marginso as tominimizelocking time. Figure40. EffectofLM6211 on Phase Noise ofPLL Copyright© 2006–2013,Texas InstrumentsIncorporated SubmitDocumentationFeedback 15 ProductFolderLinks:LM6211

FL0_RF GND LE FIN_IF V S CE FINB_RF D 0_IF OSC_EN OSC_OUT/FL 0_IF OSC_IN FIN_RF GND D 0_RF GND C 26 0.01 PF C 27 100 pF IF_PLL I/O's RF_PLL PROGRAMMING INPUTS C 13 0.01 PF C 14 100 pF C 10 0.01 PF C 11 100 pF C 5 100 pF C 1 C 2 C 4 R 2 C 6 100 pF VS_PLL R 46 100 k: R 45 100 k: C 37 0.1 PF C 39 R 47 C 38 R 50 10: C 41 0.1 PF VS_OP AMP RF OUT VCCV+ 0.01 PF VS_RF 100 pF V586ME04 R 5 18: R 7 18: C 7 100 pF RF_OUT R 6 18: C 40 100 pF VS_PLL R 3 R 41 C 36C 3 VS_PLL VS_PLL LM6211 LMX2430 LM6211 SNOSAH2C –FEBRUARY 2006–REVISED MARCH 2013 www.ti.com Figure41. LM6211 intheActiveLoop FilterforLMX2430 ADC INPUT DRIVER A typicalapplicationfora high performanceop amp isas an ADC driver,which deliversthe analog signal obtainedfrom sensorsand actuatorsto ADCs forconversionto the digitaldomain and furtherprocessing. Importantrequirementsinthisapplicationare a slew ratehighenough to drivethe ADC inputand low input referredvoltageand currentnoise.Ifan op amp isused withan ADC, itiscriticalthattheop amp noisedoes not affectthedynamic rangeoftheADC. The LM6211, withlow inputreferredvoltageand currentnoise,providesa greatsolutionforthisapplication.For example,theLM6211 can be used todrivean ADS121021, a 12-bitADC fromTI.Ifitprovidesa gainof10 toa maximum inputsignalamplitudeof100 mV, fora bandwidthas wide as 100 kHz, theaveragenoiseseen attheinputoftheADC isonly44.6µVrms. Hence thedynamic range ofthe ADC, measured inEffectiveNumber ofBitsor ENOB, isonlyreducedby 0.3bits,despiteamplifyingtheinput signalby a gainof10.Low inputbiascurrentsand highinputimpedance alsohelpas theypreventtheloadingof thesensorand allowthemeasurement systemtofunctionovera largerange. Figure42 shows a circuitformonitoringfluidpressureina hydraulicsystem,inwhich the LM6211 isused to sense the errorvoltagefrom the pressuresensor.Two LM6211 amplifiersare used to make a difference amplifierwhichsenses theerrorsignal,amplifiesitby a gainof100,and deliversittotheADC input.The ADC convertsthe errorvoltageintoa pressurereadingto be displayedand drivesthe DAC, which changes the voltagedrivingtheresistancebridgesensor.Thisisused tocontrolthegainofthepressuremeasurement circuit, such thattherangeofthesensorcan be modifiedtoobtainthebestresolutionpossible.

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0.1 PF VS VS +IN -IN

0.1 PF 1 PF

+5V 1,2 7,8

7 SCLK

6 DOUT

6 SYNC

5 SCLK

4 DOUT

4.096V 1VOUT 120 pF +5V 100 k: 0.2 PF 180: 100 k: 0.2 PF 470 pF 470 pF 1 8 2.048V VREF +5V +5V AV = 100 180: 2.02 k: PRESSURE SENSOR 0.2 mV/Volt/PSI A1, A2 = LM6211 B1 = LM4140ACM-2.0 C1 = DAC081S101 C2 = ADC121S625 LM6211 www.ti.com SNOSAH2C –FEBRUARY 2006–REVISED MARCH 2013 Figure42. HydraulicPressureMonitoringSystem DAC OUTPUT AMPLIFIER Op amps areoftenused toimprovea DAC's outputdrivingcapability.Highperformanceop amps arerequiredas I-Vconvertersat the outputsof highresolutioncurrentoutputDACs. Since most DACs operatewitha single supplyof5V, a rail-to-railoutputswingisessentialforthisapplication.A low offsetvoltageisalsonecessaryto preventoffseterrorsinthewaveform generated.Also,theoutputimpedance ofDACs isquitehigh,more thana few kΩ insome cases,so itisalsoadvisablefortheop amp tohave a low inputbiascurrent.An op amp witha highinputimpedance alsopreventstheloadingoftheDAC, and hence,avoidsgainerrors.The op amp should alsohave a slewratewhichisfastenough tonotaffectthesettlingtimeoftheDAC output. The LM6211, witha CMOS inputstage,ultralow inputbiascurrent,a wide bandwidth(20MHz) and a rail-to-rail outputswing fora supplyvoltageof24V isan idealop amp forsuch an application.Figure43 shows a typical circuitforthisapplication.The op amp isusuallyexpectedtoadd anothertimeconstanttothesystem,which worsens thesettlingtime,butthewide bandwidthoftheLM6211 (20 MHz) allowsthesystem performanceto improvewithoutany significantdegradationofthesettlingtime. Figure43. DAC DriverCircuit Copyright© 2006–2013,Texas InstrumentsIncorporated SubmitDocumentationFeedback 17 ProductFolderLinks:LM6211

AV = 1 + R 2 R 1 -VIN R 1 1 k: R 2 10 k: VOUT = 11 C C1 VOUT C F VIN R B1 R B2 C C2 R 2 R 1 AV = - = -10 R 2 10 k: R 1 1 k: LM6211 SNOSAH2C –FEBRUARY 2006–REVISED MARCH 2013 www.ti.com AUDIO PREAMPLIFIER Withlow inputreferredvoltagenoise,low supplyvoltageand low supplycurrent,and low harmonicdistortion,the LM6211 isidealforaudioapplications.Itswide unitygainbandwidthallowsittoprovidelargegainovera wide frequencyrange and itcan be used todesigna preamplifiertodrivea loadofas low as 600Ω withlessthan 0.001% distortion.Two amplifiercircuitsare shown in Figure44 and Figure45. Figure44 is an inverting amplifier,witha 10 kΩ feedbackresistor,R 2,and a 1 kΩ inputresistor,R 1,and hence providesa gainof−10. Figure45 isa non-invertingamplifier,usingthesame valuesforR 1 and R 2,and providesa gainof11.Ineitherof thesecircuits,thecouplingcapacitorC C1 decidesthelowerfrequencyatwhich thecircuitstartsprovidinggain, whilethefeedbackcapacitorC F decidesthefrequencyatwhichthegainstartsdroppingoff.Figure46 shows the frequencyresponseofthecircuitinFigure44 withdifferentvaluesofC F. Figure44. InvertingAudio Amplifier Figure45. Non-InvertingAudio Preamplifier

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  • RF = C IN = CD + CCM 1 100 10k 1M FREQUENCY (Hz) -20 GAIN (dB) 100k1k10 -10 -15 C F = 10 pF C F = 100 pF C F = 1 nF LM6211 www.ti.com SNOSAH2C –FEBRUARY 2006–REVISED MARCH 2013 Figure46. Frequency Response oftheNon-InvertingPreamplifier TRANSIMPEDANCE AMPLIFIER A transimpedanceamplifierconvertsa smallinputcurrentintoa voltage.Thiscurrentisusuallygeneratedby a photodiode.The transimpedancegain,measured as the ratioof the outputvoltageto the inputcurrent,is expectedtobe largeand wide-band.Sincethecircuitdealswithcurrentsintherange ofa few nA, low noise performanceisessential.The LM6211, beinga CMOS inputop amp, providesa wide bandwidthand low noise performancewhiledrawingverylowinputbiascurrent,and ishence idealfortransimpedanceapplications. A transimpedanceamplifierisdesignedon thebasisofthecurrentsourcedrivingtheinput.A photodiodeisa very common capacitivecurrentsource,which requirestransimpedancegain fortransformingitsminiscule currentintoeasilydetectablevoltages.The photodiodeand amplifier’s gain are selectedwithrespectto the speed and accuracyrequiredofthecircuit.A fastercircuitwould requirea photodiodewithlessercapacitance and a fasteramplifier.A more sensitivecircuitwould requirea sensitivephotodiodeand a highgain.A typical transimpedanceamplifierisshown inFigure47. The outputvoltageof the amplifierisgivenby the equation VOUT = −IINR F. Since the outputswing of the amplifierislimited,R F shouldbe selectedsuch thatallpossible valuesofIIN can be detected. The LM6211 has a largegain-bandwidthproduct(20MHz), whichenableshighgainsatwide bandwidths.A rail- to-railoutputswingat24V supplyallowsdetectionand amplificationofa wide rangeofinputcurrents.A CMOS inputstagewithnegligibleinputcurrentnoiseand low inputvoltagenoiseallowsthe LM6211 to providehigh fidelityamplificationforwide bandwidths.These propertiesmake theLM6211 idealforsystems requiringwide- band transimpedanceamplification. Figure47. Photodiode Transimpedance Amplifier The followingparametersare used todesigna transimpedanceamplifier:theamplifiergain-bandwidthproduct, A0;theamplifierinputcapacitance,C CM ;thephotodiodecapacitance,C D ;thetransimpedancegainrequired,R F; and theamplifieroutputswing.Once a feasibleR F isselectedusingtheamplifieroutputswing,thesenumbers can be used to design an amplifierwiththe desiredtransimpedancegain and a maximallyflatfrequency response.The inputcommon-mode capacitancewithrespecttoVCM fortheLM6211 isgiveinFigure48. Copyright© 2006–2013,Texas InstrumentsIncorporated SubmitDocumentationFeedback 19 ProductFolderLinks:LM6211

IF RA < < RF C Fc = ¨ §1 + R B R A R A C Fc R B R FC INA0 C F = 2SR FA0 1 + 1 + 4S C IN (pF) 0 4 8 12 16 18 22 24 VCM (V) 20141062 VS = 5V VS = 24V LM6211 SNOSAH2C –FEBRUARY 2006–REVISED MARCH 2013 www.ti.com Figure48. InputCommon-Mode Capacitancevs.VCM An essentialcomponent forobtaininga maximallyflatresponseisthefeedbackcapacitor,C F.The capacitance seen at the inputof the amplifier,C IN, combined withthe feedbackresistor,R F, generatesa phase lagwhich causes gain-peakingand can destabilizethecircuit.C IN isusuallyjustthesum ofC D and C CM .The feedback capacitorC F createsa pole,fP inthenoisegainofthecircuit,which neutralizesthezerointhenoisegain,fZ, createdby thecombinationofR F and C IN.Ifproperlypositioned,thenoisegainpolecreatedby C F can ensure thattheslopeofthegainremainsat20 dB/decadetilltheunitygainfrequencyoftheamplifierisreached,thus ensuringstability.As shown inFigure50,fP ispositionedsuch thatitcoincideswiththepointwhere thenoise gain intersectsthe op amp ’s open loop gain.In thiscase, fP is also the overall3 dB frequencyof the transimpedanceamplifier.The valueof C F needed to make itso isgivenby Equation2. A largervalueof C F causes excessivereductionof bandwidth,whilea smallervaluefailsto preventgain peakingand maintain stability. (2) CalculatingC F from Equation2 can sometimes returnunreasonablysmallvalues(<1 pF),especiallyforhigh speed applications.In thesecases,itisoftenmore practicalto use the circuitshown inFigure49 inorderto allowmore reasonablevalues.In thiscircuit,the capacitanceC F'is(1+ R B/RA) timesthe effectivefeedback capacitance,C F.A largercapacitorcan now be used inthiscircuittoobtaina smallereffectivecapacitance. Figure49. ModifyingC F For example,ifa C F of0.5pF isneeded,whileonlya 5 pF capacitorisavailable,R B and R A can be selected such thatR B/RA = 9.Thiswould converta C F'of5 pF intoa C F of0.5pF.Thisrelationshipholdsas longas R A << R F

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VIN = KI IR RADIATION INTENSITY, I VOUT RA K(RA + R B)I = IR SENSOR R B OP AMP OPEN LOOP GAIN NOISE GAIN WITH NO C F NOISE GAIN WITH CF fZ fP A0 fZ = 2SR FC IN fP = 2S R F(CIN+C F) GAIN FREQUENCY LM6211 www.ti.com SNOSAH2C –FEBRUARY 2006–REVISED MARCH 2013 Figure50. Method forC F selection SENSOR INTERFACES The low inputbiascurrentand low inputreferrednoiseoftheLM6211 make itidealforsensorinterfaces.These circuitsarerequiredtosense voltagesoftheorderofa few μV, and currentsamountingtolessthana nA, and hence theop amp needs tohave low voltagenoiseand low inputbiascurrent.Typicalapplicationsincludeinfra- red (IR)thermometry,thermocoupleamplifiersand pH electrodebuffers.Figure51 isan example of a typical circuitused formeasuringIR radiationintensity,oftenused forestimatingthetemperatureofan objectfrom a distance.The IR sensorgeneratesa voltageproportionaltoI,whichistheintensityoftheIR radiationfallingon it.As shown inFigure51,K istheconstantofproportionalityrelatingthevoltageacrosstheIR sensor(VIN)tothe radiationintensity,I.The resistancesR A and R B areselectedtoprovidea highgaintoamplifythisvoltage,while C F isadded tofilteroutthehighfrequencynoise. Figure51. IR RadiationSensor Copyright© 2006–2013,Texas InstrumentsIncorporated SubmitDocumentationFeedback 21 ProductFolderLinks:LM6211

SNOSAH2C –FEBRUARY 2006–REVISED MARCH 2013 www.ti.com

REVISION HISTORY

Changes from RevisionB (March 2013)toRevisionC Page

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www.ti.com 23-May-2025 PACKAGING INFORMATION Orderable part number Status (1) Material type (2) Package | Pins Package qty | Carrier RoHS (3) Lead finish/ Ball material (4) MSL rating/ Peak reflow (5) Op temp (°C) Part marking (6) LM6211 MDC Active Production DIESALE (Y) | 0 400 | NOT REQUIRED Yes Call TI Level-1-NA-UNLIM -40 to 85 LM6211-MDC.A Active Production DIESALE (Y) | 0 400 | NOT REQUIRED Yes Call TI Level-1-NA-UNLIM -40 to 85 LM6211MF/NOPB Active Production SOT-23 (DBV) | 5 1000 | SMALL T&R Yes SN Level-1-260C-UNLIM -40 to 125 AT1A LM6211MF/NOPB.A Active Production SOT-23 (DBV) | 5 1000 | SMALL T&R Yes SN Level-1-260C-UNLIM -40 to 125 AT1A LM6211MFX/NOPB Active Production SOT-23 (DBV) | 5 3000 | LARGE T&R Yes SN Level-1-260C-UNLIM -40 to 125 AT1A LM6211MFX/NOPB.A Active Production SOT-23 (DBV) | 5 3000 | LARGE T&R Yes SN Level-1-260C-UNLIM -40 to 125 AT1A (1) Status: For more details on status, see our product life cycle. (2) Material type: When designated, preproduction parts are prototypes/experimental devices, and are not yet approved or released for full production. Testing and final process, including without limitation quality assurance, reliability performance testing, and/or process qualification, may not yet be complete, and this item is subject to further changes or possible discontinuation. If available for ordering, purchases will be subject to an additional waiver at checkout, and are intended for early internal evaluation purposes only. These items are sold without warranties of any kind. (3) RoHS values: Yes, No, RoHS Exempt. See the TI RoHS Statement for additional information and value definition. (4) Lead finish/Ball material: Parts may have multiple material finish options. Finish options are separated by a vertical ruled line. Lead finish/Ball material values may wrap to two lines if the finish value exceeds the maximum column width. (5) MSL rating/Peak reflow: The moisture sensitivity level ratings and peak solder (reflow) temperatures. In the event that a part has multiple moisture sensitivity ratings, only the lowest level per JEDEC standards is shown. Refer to the shipping label for the actual reflow temperature that will be used to mount the part to the printed circuit board. (6) Part marking: There may be an additional marking, which relates to the logo, the lot trace code information, or the environmental category of the part. Multiple part markings will be inside parentheses. Only one part marking contained in parentheses and separated by a "~" will appear on a part. If a line is indented then it is a continuation of the previous line and the two combined represent the entire part marking for that device. Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals. TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for release. In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis. Addendum-Page 1

www.ti.com 23-May-2025 Addendum-Page 2

PACKAGE MATERIALS INFORMATION www.ti.com 18-Oct-2024 TAPE AND REEL INFORMATION Reel Width (W1) REEL DIMENSIONS A0B0K0WDimension designed to accommodate the component lengthDimension designed to accommodate the component thicknessOverall width of the carrier tapePitch between successive cavity centersDimension designed to accommodate the component width TAPE DIMENSIONSK0 P1B0WA0Cavity QUADRANT ASSIGNMENTS FOR PIN 1 ORIENTATION IN TAPE Pocket QuadrantsSprocket HolesQ1Q1Q2Q2Q3Q3Q4Q4User Direction of Feed P1ReelDiameter *All dimensions are nominal Device Package Type Package Drawing Pins SPQ Reel Diameter (mm) Reel Width W1 (mm) (mm) (mm) (mm) (mm) W (mm) Pin1 Quadrant Pack Materials-Page 1

PACKAGE MATERIALS INFORMATION www.ti.com 18-Oct-2024 TAPE AND REEL BOX DIMENSIONS Width (mm) W LH *All dimensions are nominal Device Package Type Package Drawing Pins SPQ Length (mm) Width (mm) Height (mm) LM6211MF/NOPB SOT-23 DBV 5 1000 208.0 191.0 35.0 LM6211MFX/NOPB SOT-23 DBV 5 3000 208.0 191.0 35.0 Pack Materials-Page 2

www.ti.com PACKAGE OUTLINE C 0.22

0.08 TYP

0.25 3.0 2.6 2X 0.95 1.9 1.45 0.90 0.15

0.00 TYP

5X 0.5 0.3 0.6

0.3 TYP

0 TYP

1.9 (0.1) (0.15) 4X 0 -15 4X 4 -15 A 3.05 2.75 B1.75 1.45 (1.1) SOT-23 - 1.45 mm max heightDBV0005A SMALL OUTLINE TRANSISTOR 4214839/K 08/2024 NOTES: 1. All linear dimensions are in millimeters. Any dimensions in parenthesis are for reference only. Dimensioning and tolerancing per ASME Y14.5M. 2. This drawing is subject to change without notice. 3. Refernce JEDEC MO-178. 4. Body dimensions do not include mold flash, protrusions, or gate burrs. Mold flash, protrusions, or gate burrs shall not exceed 0.25 mm per side. 5. Support pin may differ or may not be present.

0.2 C A B

0.1 C SCALE 4.000

www.ti.com EXAMPLE BOARD LAYOUT

0.07 MAX

0.07 MIN

5X (1.1) 5X (0.6) (2.6) (1.9) 2X (0.95) (R0.05) TYP 4214839/K 08/2024 SOT-23 - 1.45 mm max heightDBV0005A SMALL OUTLINE TRANSISTOR NOTES: (continued) 6. Publication IPC-7351 may have alternate designs. 7. Solder mask tolerances between and around signal pads can vary based on board fabrication site. SYMM LAND PATTERN EXAMPLE EXPOSED METAL SHOWN SCALE:15X PKG 3 4 SOLDER MASK OPENING METAL UNDER SOLDER MASK SOLDER MASK DEFINED EXPOSED METAL METALSOLDER MASK OPENING NON SOLDER MASK DEFINED (PREFERRED) SOLDER MASK DETAILS EXPOSED METAL

www.ti.com EXAMPLE STENCIL DESIGN (2.6) (1.9) 2X(0.95) 5X (1.1) 5X (0.6) (R0.05) TYP SOT-23 - 1.45 mm max heightDBV0005A SMALL OUTLINE TRANSISTOR 4214839/K 08/2024 NOTES: (continued) 8. Laser cutting apertures with trapezoidal walls and rounded corners may offer better paste release. IPC-7525 may have alternate design recommendations. 9. Board assembly site may have different recommendations for stencil design. SOLDER PASTE EXAMPLE BASED ON 0.125 mm THICK STENCIL SCALE:15X SYMM PKG 3 4

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