LM2900

LM2900 NSC | Alldatasheet

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Y Wide single supply voltage 4 V DC to 32 V DC Range or dual supplies g2V DC to g16 V DC Y Supply current drain independent of supply voltage Y Low input biasing current 30 nA Y High open-loop gain 70 dB Y Wide bandwidth 2.5 MHz (unity gain) Y Large output voltage swing (V a b 1) Vp-p Y Internally frequency compensated for unity gain Y Output short-circuit protection Schematic and Connection Diagrams TL/H/7936–1 Dual-In-Line and S.O. TL/H/7936–2 Top View Order Number LM2900N, LM3900M, LM3900N or LM3301N See NS Package Number M14A or N14A C1995 National Semiconductor Corporation RRD-B30M115/Printed in U. S. A.

If Military/Aerospace specified devices are required, please contact the National Semiconductor Sales Office/ Distributors for availability and specifications. LM2900/LM3900 LM3301 Supply Voltage 32 V DC 28 V DC g16 V DC g14 V DC Power Dissipation (T A e 25§C) (Note 1) Molded DIP 1080 mW 1080 mW S.O. Package 765 mW Input Currents, I IN a or I IN b 20 mA DC 20 mA DC Output Short-Circuit DurationÐOne Amplifier Continuous Continuous TA e 25§C (See Application Hints) Operating Temperature Range b40§Ct o a85§C LM2900 b40§Ct o a85§C LM3900 0 §Ct o a70§C Storage Temperature Range b65§Ct o a150§C b65§Ct o a150§C Lead Temperature (Soldering, 10 sec.) 260 §C 260 §C Soldering Information Dual-In-Line Package Soldering (10 sec.) 260 §C 260 §C Small Outline Package Vapor Phase (60 sec.) 215 §C 215 §C Infrared (15 sec.) 220 §C 220 §C See AN-450 ‘‘Surface Mounting Methods and Their Effect on Product Reliability’’ for other methods of soldering surface mount devices. ESD tolerance (Note 7) 2000V 2000V Electrical Characteristics TA e 25§C, V a e 15 V DC, unless otherwise stated Parameter Conditions LM2900 LM3900 LM3301 Units Min Typ Max Min Typ Max Min Typ Max Open Voltage Gain Over Temp. Input Resistance Inverting Input

111 M X

Output Resistance 8 8 9 k X Unity Gain Bandwidth Inverting Input 2.5 2.5 2.5 MHz Input Bias Current Inverting Input, V a e 5V DC 30 200 30 200 30 300 nAInverting Input Slew Rate Positive Output Swing 0.5 0.5 0.5 V/msNegative Output Swing 20 20 20 Supply Current R L e % On All Amplifiers 6.2 10 6.2 10 6.2 10 mA DC Output V OUT High R L e 2k, I IN b e 0, 13.5 13.5 13.5Voltage V a e 15.0 V DC IINa e 0 Swing VOUT Low I IN a e 0V DC VOUT High V a e Absolute I IN b e 0, Maximum Ratings I IN a e 0 29.5 29.5 26.0 RL e %, Output Source 6 18 6 10 5 18 ISINK VOL e 1V, I IN b e 5 mA5 5 5

Electrical Characteristics (Note 6), V a e 15 V DC, unless otherwise stated (Continued) Parameter Conditions LM2900 LM3900 LM3301 Units Min Typ Max Min Typ Max Min Typ Max Power Supply Rejection T A e 25§C, f e 100 Hz 70 70 70 dB DMirror Gain @ 20 mAt o2 0 0 mA (Note 3) 2 5 2 5 2 5 % Mirror Current (Note 4) 10 500 10 500 10 500 mADC Negative Input Current T A e 25§C (Note 5) 1.0 1.0 1.0 mA DC Input Bias Current Inverting Input 300 300 nA Note 1: For operating at high temperatures, the device must be derated based on a 125 §C maximum junction temperature and a thermal resistance of 92 §C/W which applies for the device soldered in a printed circuit board, operating in a still air ambient. Thermal resistance for the S.O. package is 131 §C/W. Note 2: The output current sink capability can be increased for large signal conditions by overdriving the inverting input. This is shown in the section on Typical Characteristics. Note 3: This spec indicates the current gain of the current mirror which is used as the non-inverting input. Note 4: Input V BE match between the non-inverting and the inverting inputs occurs for a mirror current (non-inverting input current) of approximately 10 mA. This is therefore a typical design center for many of the application circuits. Note 5: Clamp transistors are included on the IC to prevent the input voltages from swinging below ground more than approximately b0.3 V DC. The negative input currents which may result from large signal overdrive with capacitance input coupling need to be externally limited to values of approximately 1 mA. Negative input currents in excess of 4 mA will cause the output voltage to drop to a low voltage. This maximum current applies to any one of the input terminals. If more than one of the input terminals are simultaneously driven negative smaller maximum currents are allowed. Common-mode current biasing can be used to prevent negative input voltages; see for example, the ‘‘Differentiator Circuit’’ in the applications section. Note 6: These specs apply for b40§C s TA s a85§C, unless otherwise stated. Note 7: Human body model, 1.5 k X in series with 100 pF. Application Hints When driving either input from a low-impedance source, a limiting resistor should be placed in series with the input lead to limit the peak input current. Currents as large as 20 mA will not damage the device, but the current mirror on the non-inverting input will saturate and cause a loss of mir- ror gain at mA current levelsÐespecially at high operating temperatures. Precautions should be taken to insure that the power supply for the integrated circuit never becomes reversed in polarity or that the unit is not inadvertently installed backwards in a test socket as an unlimited current surge through the result- ing forward diode within the IC could cause fusing of the internal conductors and result in a destroyed unit. Output short circuits either to ground or to the positive pow- er supply should be of short time duration. Units can be destroyed, not as a result of the short circuit current causing metal fusing, but rather due to the large increase in IC chip dissipation which will cause eventual failure due to exces- sive junction temperatures. For example, when operating from a well-regulated a5V DC power supply at T A e 25§C with a 100 k X shunt-feedback resistor (from the output to the inverting input) a short directly to the power supply will not cause catastrophic failure but the current magnitude will be approximately 50 mA and the junction temperature will be above T J max. Larger feedback resistors will reduce the current, 11 M X provides approximately 30 mA, an open cir- cuit provides 1.3 mA, and a direct connection from the out- put to the non-inverting input will result in catastrophic fail- ure when the output is shorted to V a as this then places the base-emitter junction of the input transistor directly across the power supply. Short-circuits to ground will have magni- tudes of approximately 30 mA and will not cause cata- strophic failure at T A e 25§C. Unintentional signal coupling from the output to the non-in- verting input can cause oscillations. This is likely only in breadboard hook-ups with long component leads and can be prevented by a more careful lead dress or by locating the non-inverting input biasing resistor close to the IC. A quick check of this condition is to bypass the non-inverting input to ground with a capacitor. High impedance biasing resis- tors used in the non-inverting input circuit make this input lead highly susceptible to unintentional AC signal pickup. Operation of this amplifier can be best understood by notic- ing that input currents are differenced at the inverting-input terminal and this difference current then flows through the external feedback resistor to produce the output voltage. Common-mode current biasing is generally useful to allow operating with signal levels near ground or even negative as this maintains the inputs biased at aVBE. Internal clamp transistors (see note 5) catch-negative input voltages at ap- proximately b0.3 V DC but the magnitude of current flow has to be limited by the external input network. For operation at high temperature, this limit should be approximately 100 mA. This new ‘‘Norton’’ current-differencing amplifier can be used in most of the applications of a standard IC op amp. Performance as a DC amplifier using only a single supply is not as precise as a standard IC op amp operating with split supplies but is adequate in many less critical applications. New functions are made possible with this amplifier which are useful in single power supply systems. For example, biasing can be designed separately from the AC gain as was shown in the ‘‘inverting amplifier,’’ the ‘‘difference integra- tor’’ allows controlling the charging and the discharging of the integrating capacitor with positive voltages, and the ‘‘fre- quency doubling tachometer’’ provides a simple circuit which reduces the ripple voltage on a tachometer output DC voltage.

Typical Performance Characteristics Open Loop Gain Voltage Gain Voltage Gain Input Current Supply Current Response Large Signal Frequency Output Sink Current Output Class-A Bias Current Output Source Current Supply Rejection Mirror Gain Maximum Mirror Current TL/H/7936–9

Typical Applications (Va e 15 V DC) Inverting Amplifier VODC e Va AV j b R2 TL/H/7936–3 Triangle/Square Generator TL/H/7936–4 Frequency-Doubling Tachometer TL/H/7936–5 Low V IN b VOUT Voltage Regulator TL/H/7936–6 Non-Inverting Amplifier VODC e Va AV j R2 TL/H/7936–7 Negative Supply Biasing VODC e R2 R3 Vb TL/H/7936–8AV j R2

Typical Applications (Va e 15 V DC) (Continued) Low-Drift Ramp and Hold Circuit TL/H/7936–10 Bi-Quad Active Filter (2nd Degree State-Variable Network) TL/H/7936–11 Q e 50 fO e 1 kHz

Typical Applications (Va e 15 V DC) (Continued) Voltage-Controlled Current Source (Transconductance Amplifier) TL/H/7936–12 Hi V IN ,L o( V IN b VO) Self-Regulator Q1 & Q2 absorb Hi V IN TL/H/7936–13 Ground-Referencing a Differential Input Signal TL/H/7936–14

Typical Applications (Va e 15 V DC) (Continued) Voltage Regulator (VO e VZ a VBE) TL/H/7936–15 Fixed Current Sources I2 e R1 R2 I1 TL/H/7936–16 Voltage-Controlled Current Sink (Transconductance Amplifier) TL/H/7936–17 Buffer Amplifier VIN t VBE TL/H/7936–18 Tachometer TL/H/7936–19 VODC e Af IN *Allows V O to go to zero.

Typical Applications (Va e 15 V DC) (Continued) Low-Voltage Comparator No negative voltage limit if properly biased. TL/H/7936–20 Power Comparator TL/H/7936–21 Comparator TL/H/7936–22 Schmitt-Trigger TL/H/7936–23 Square-Wave Oscillator TL/H/7936–24 Pulse Generator TL/H/7936–25 Frequency Differencing Tachometer VODC e A( f 1 b f2) TL/H/7936–26

Typical Applications (Va e 15 V DC) (Continued) Frequency Averaging Tachometer VODC e A( f 1 a f2) TL/H/7936–27 Squaring Amplifier (W/Hysteresis) TL/H/7936–28 Bi-Stable Multivibrator TL/H/7936–29 Differentiator (Common-Mode Biasing Keeps Input at aVBE) AV e 1 TL/H/7936–30 ‘‘OR’’ Gate f e A a B a C TL/H/7936–31 ‘‘AND’’ Gate f e A # B # C TL/H/7936–32 Difference Integrator TL/H/7936–33

Typical Applications (Va e 15 V DC) (Continued) Low Pass Active Filter fO e 1 kHz TL/H/7936–34 Staircase Generator TL/H/7936–35 VBE Biasing AV j b R2 TL/H/7936–36 Bandpass Active Filter TL/H/7936–37 fo e 1 kHz Q e 25

Typical Applications (Va e 15 V DC) (Continued) Low-Frequency Mixer TL/H/7936–38 Free-Running Staircase Generator/Pulse Counter TL/H/7936–39

Typical Applications (Va e 15 V DC) (Continued) Supplying I IN with Aux. Amp (to Allow Hi-Z Feedback Networks) TL/H/7936–40 One-Shot Multivibrator PW j 2 c 106C *Speeds recovery. TL/H/7936–41 Non-Inverting DC Gain to (0,0) TL/H/7936–42

Typical Applications (Va e 15 V DC) (Continued) Channel Selection by DC Control (or Audio Mixer) TL/H/7936–43

Typical Applications (Va e 15 V DC) (Continued) Power Amplifier TL/H/7936–44 One-Shot with DC Input Comparator TL/H/7936–45 Trips at V IN j 0.8 V a VIN must fall 0.8 V a prior to t 2 High Pass Active Filter TL/H/7936–46

Typical Applications (Va e 15 V DC) (Continued) Sample-Hold and Compare with New aVIN TL/H/7936–47 Sawtooth Generator TL/H/7936–48

Typical Applications (Va e 15 V DC) (Continued) Phase-Locked Loop TL/H/7936–49 Boosting to 300 mA Loads TL/H/7936–50

Split-Supply Applications (Va ea 15 V DC &V b eb 15 V DC) Non-Inverting DC Gain TL/H/7936–51 AC Amplifier TL/H/7936–52

Physical Dimensions inches (millimeters) Small Outline Package (M) Order Number LM3900M

LM2900/LM3900/LM3301 Quad Amplifiers Physical Dimensions inches (millimeters) (Continued) Molded Dual-In-Line Package (N) Order Number LM2900N, LM3900N or LM3301N LIFE SUPPORT POLICY NATIONAL’S PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT DEVICES OR SYSTEMS WITHOUT THE EXPRESS WRITTEN APPROVAL OF THE PRESIDENT OF NATIONAL SEMICONDUCTOR CORPORATION. As used herein: 1. Life support devices or systems are devices or 2. A critical component is any component of a life systems which, (a) are intended for surgical implant support device or system whose failure to perform can into the body, or (b) support or sustain life, and whose be reasonably expected to cause the failure of the life failure to perform, when properly used in accordance support device or system, or to affect its safety or with instructions for use provided in the labeling, can effectiveness. be reasonably expected to result in a significant injury to the user. National Semiconductor National Semiconductor National Semiconductor National Semiconductor Corporation Europe Hong Kong Ltd. Japan Ltd.

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