LH0101

LH0101 MAXIM | Alldatasheet

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Power Operational Amplifier General Description = CSCS Fetus The Maxim LHO101 Power Operational Amplifier de- @ Pin for Pin 2nd Source! = livers up to 5 Amp peak output current. Packaged in a 3° rugged TO-3 case, the LH0101 combines the ease of + @ +5 Amp Peak, 2 Amp Continuous Output Current ~ use and performance of a FET input op amp with the ro} power handling capabilities of a5 Amp output stage. @ Virtually No Crossover Distortion a? The output short circuit protection makes this device ideal for driving AC and DC motors, large capacitive @ 300 kHz Power Bandwidth loads, and electromagnetic actuators. The output stage virtually eliminates crossover distortion while 300 pA Input Bias Current using little quiescent power. The LH0101 is a wideband amplifier, with a full power 10 W/us Slew Rate bandwidth of 300kHz and a gain bandwidth of 5MHz To simplify connection to the LHO101, the output of @ 5 MHz Gain Bandwidth Maxim's LHO101 is connected to both the case and to pin 4, # 2s Settling Time to 0.01% Adjustable Current Limit Applications _ SS sCOrderring Information The LHO101 is well suited for applications requiring PART Team RANGE PACKAGE both standard op amp performance and high current THOOIGK 35°C to 185°C B Lead TOS | DC Motor LHOIOIK 55°C to +125°C_ BleadTO-3 | AC Motors LHOIO1ACK -25°C to +85°C 8 Lead TO-3 ‘Actuators LHOIOTAK 55°C to +125°C 8 Lead TO-3 Coaxial Cable Drivers Programmable Power Supplies Typical Operating Circuit Pin Configuration Top View auruns ASEAN 3 pe b eur ww wut oO) ecooacx ® ® ms wi) @ ® ve (a) ha } TT to scr 9 4 1 seavo wore omen MAXIM a a Maxim integrated Products 1 For free samples & the latest literature: http:/www.maxim-ic.com, or phone 1-800-998-8800

Power Operational Amplifier ‘w= ABSOLUTE MAXIMUM RATINGS © _ Supply Voltage. Vs... eeeeeeeeeseeesseeesseeessee #22V Output Short Circuit Duration (within rated power

6 Derate linearly at 25°C /W to zero at 150°C Operating Temperature Range

Powor Dissipation at Te = 25°C v.cseecseceeeeseessees 62W LHOIOIAG, LHOWIG es eee cc cveceseeese 25°C to +85°C =z Derate linearly at 2°C/W to zero at 150°C LHOIOIA. LHOIOT 2.20222 LLL LLL LILI 88°C to +128°C we _Dillerentit input Voltage. Vig vs s-esssecvess MOV But =Vy Storage Temperature 100000000201 65°C to 160°C Stresses above those listed under “Absolute Maximum Ratings” may cause permanent damage to the device These are stress ratings only ane functional Operation a the device a these or any other conditions above those indicated nthe operahional sectors ofthe spactications fe not imphed. Exposure 10 absolute maximum rating conditions for extonced periods may affect Govice relay DC ELECTRICAL CHARACTERISTICS (Vg = £18V. T, = 25°C unless otherwise noted. see Note 1) A - a ee a ) PARAMETER SYMBOL CONDITIONS LHOIOIAC, LHOWIA | _LHOWIC. LHOW | nuts, MIN. TYR MAX. | MIN. TYR MAX. | saput oteet Ta= 25°C 1 3 510 | mv input Ottset Voltage Vos Fy 21,2 Tua iNote a) 7 15 = ‘Change in Input Offset Voltage | SYS | (Note 2) 150 300 | www | with dissipated power | __4P2 _ ‘Change in i fart Soot vorane | 4% | vey=o ‘0 ‘0 |nwe] with temperature ar : ee a Ta= 25°C ee ee 7000 | pa | snp iascurert | te apc tyyg 7 TERDIOIGE eo oT na | (Note 4) LHOIOVA 300 1000 | nA | | Ta= 25°C _ _ 75 280 | pa | Input Otser Curent | tos [T= Ty YEHOTOIGIAG 5 5 [ma] | (Note 4) GHo10V/A 5s | 250. | rA_| Large Signal - . , Voltage Gain | Avo. Vo = ~10V. Ri = 100 aa 200 - 50 200 | wmv | T Asc=0n | Ai 1000 a7 sf? es Ty j ‘Output Voltage Swing | Vo | Av=41— | Au = 100 mone ne v | wore) R=5e sos 21 +05 =1 v ‘Common Mode . Sone mete cman | avi tov & 100 85 100 36 Power Supply | psAR | avs- ssvto~18v 8 100 85 100 8 Rejection Ratio - Quiescent Supply

2 MAKI

Power Operational Amplifier AC ELECTRICAL CHARACTERISTICS r (Vg = +15V, T, = 25°C, See Note 1) z LHO1O1AC, LHO101A LHO101C, LHO101 38 . PARAMETER SYMBOL CONDITIONS ———— UNITS MIN. TYR MAX. | MIN. TYR MAX. 3 Equivalent input 1 | = Noise Voltage en t wee 25 25 ; nw Jaz = Input Capacitance Cw [t= MHz Z 30 30 pF Power Bandwidth, -348 300 300 kHz Slew Rate (Note 4) sR Aye 100 78 10 wo Was ‘Small Signal Rise or ua | 200 200 ns Fall Time ile Agel | . | Small Signa! Overshoot ‘ | 10 __ 10 % Gain-Bandwidth Product GBw 40 50 5.0 MHZ (Note 4) aw : Large Signal Settling : Time to 0.01% ts 20 20 ss Total Harmonic Distortion | THO ek aaa 0.008 0.008 % | Note 1: Specification is at T, ~ 25°C. When supply voltages are - 15V, quiescent operating junction temperature will rise approximately 20°C without heat sinking Accordingly, Vos may change 0 SmV and Is and Ios will change significantly during warmup. Refer tothe le vs. temperature and power dissipation graphs for expected values, Temperature tests are made only at extremes. Note 2: Change in offset voltage with dissipated power is due entirely to average device temperature rise and not to differentia! thermal foeaback effects Test is performed without any heat sink Note 3; At light loads, the output swing may be limited by the second stage rather than the output stage. See the application section under “Output swing enhancement” for hints on how to obtain extended operation Note 4: These parameters are sample tested to 10% LTPO SAFE OPERATING AREA MAXIMUM POWER DISSIPATION, QUIESCENT POWER SUPPLY CURRENT s —— r) 0 ‘= = Te=25 E> ee wear sme % iy 3 = a > 3 fq a = Ad Zz? a) s : NoweaTsmK SS A 3 an) Eo 2” Bo pat 2 ae Eo ent Sk g° = "se E —_ i: i ~ £0 S]anrnre wear one 2 i bd 0 e oj bee is ——— 0 rr . s © % wo 1 se uTPUT OLE 1 TePERATURE |) FOWER SUPPY WEUAGE 1H) MAXIM

Power Operational Amplifier by INPUT COMMON-MODE VOLTAGE RANGE INPUT BIAS CURRENT INPUT BIAS CURRENT AFTER WARM-UP 2 «” roam A ™ 7° bed z z= wl og ax i Fs 5 ze go 2 2 Ss = 0 2 = = 3 5 1 z? 0 1 e INPUT BIAS CURRENT TOTAL HARMONIC VS. COMMON-MODE VOLTAGE EQUIVALENT INPUT NOISE VOLTAGE DISTORTION VS. GAIN P = Fa cd Th=2C Fs = aC 71 unpencance.teojy=-+1604 © Vow =0 2@ = Wo= #15 Po= Som = 80] PERFECTLY CANCELLED lp=0 2 Vow =0, 2 zg ar) :” ry Laid Ex 1 Fa Zw zw ry = z an) 5° Fd nome -0 3 Fi = a0 2 COMMON-MODE REJECTION POWER SUPPLY REJECTION TOTAL HARMONIC RATIO VS. FREQUENCY RATIO VS. FREQUENCY DISTORTION VS. FREQUENCY a z mrer : : ° z |e" Po=SmW iw Zw A 2 2 i” so Ba = ZB 4 a a a oe _. AAAXIAA

Power Operational Amplifier SMALL SIGNAL PULSE RESPONSE LARGE SIGNAL PULSE RESPONSE SMALL SIGNAL FREQUENCY r (NO LOAD) (RL = 102) RESPONSE (OPEN LOOP) » 8 eu = ~~ = = 0 +30 fe) Ej @ a 2 ma Zo ge = FA 2 : z0 13 3-02 3-10 =) 8 a ~0 WN rr ee OPEN-LOOP OUTPUT OUTPUT VOLTAGE SWING RESISTANCE VS. FREQUENCY WITH SWING ENHANCEMENT SETTING TIME Zi aa = 3 = 3 1m NO LORD

2 Zs Z| ow 107 1040

2 06 Jour = 1504 3 @ 2 5 E a OUTPUT VOLTAGE SWING VS. OUTPUT VOLTAGE SWING OPEN-LOOP OUTPUT RESISTANCE LOAD RESISTANCE VS. FREQUENCY za = ENHANCEMENT ——- an 3 2 A e ge 2 wirwour 2, 2 ao s SWING z 3 sa 5 haemo = Pay Vs= 215V THE IC 4 MAXIM a __ 5

Power Operational Amplifier ~ __________. Detailed Description socket or printed circuit board, without having to make hi tsink ti © _ The LH0101 consists of three stages: an operational re quurhut Connection through heatsink mounting . amplifier, a buffer, and a power output stage, (see ° Figure 1). The operational amplifier is similar to the Transistors Q6 and Q9 provide current limit protection. T1568. This operational amplifier was chosen foritsiow The current limit threshold is programmed by sense SZ Dias current, high slew rate, and fast setting time resistors connected between the supplies andthe short circuit protection pins, SC* and SC~.A voltage of about The butfer stage, made up of transistors 08, 5,Q10. G'6V “across the sense resistors turns onveiter O6 and Q11. is a unity gain current amplifier. The buffer (source current limit) or Q9 (sink current limit). These stage bandwidth is greater than 50MHz, and is current transistors then turn on Q12 or Q4, which divert excess limited to 50mA output by the JFETs Q8 and Q7. If the ‘is base current drive away from the darlington output Feedback pin is connected to the Output, the buffer transistors, preventing the output current from rising stage provides all output current up to 25mA. The —_eyond the preset limit buffer stage current flows through the 5012 resistors, R3 and R4, The voltage across these resistors turns on the high power output stage when the buffer stage output Application Hints current is approximately 25mA. The buffer stage contin- Output Swing Enhancement ues to supply current up to its 50mA current limit during te turn-on delay of the output stage, Only in The utput te butfr stage cips an limits te output Griving low resistance or high capacitance loads at Voltage swing before the output stage saturates. The high frequencies will there be any noticeable distortion tbat swings 11V to 12.5V with the Feedback terminal during the period when the output stage istumning on, Sorimeoted #0 the Output The output swing can be The high power output stage consists of the power _ increased by using the circuit of Figure 2. In this circuit darlingtons, Q1 and Q2, andthe currentlimit protection _the output stage operates with a gain of 1.5 and the circuit. The power darlington transistors are die output stage saturation voltage of approximately 1V attached directly to the case, minimizing thermal __limits the output voltage swing. The 0.01uF com- resistance, This electrically connects the collectors of pensation capacitor is required for loop stability in Q1 and Q2 tothe case, therefore the case isthe LHO101_ —_unity gain non-inverting buffer applications using Output connection. The output of the Maxim LHO101 is output swing enhancement, but is not needed in also connected to pin 4. This additional output connec- _circuits with a closed loop gain greater than 1.5 tion enables users to make all connections directly viaa Capacitive Loads Capacitive loads create an additional pole with the associated phase shift, which may cause oscillations 2S ye The LHO101 typically has 60° of phase margin asa unity ; gain buffer with no capacitive load. A 1000pF load will o s+ reduce this phase margin to 40° and 0.01yF will reduce it to only 22°. A phase margin of only 22° is generally kK considered unacceptably low and the LHO101 should rh® KO an 0s ‘OUTPUT. mis ° ; g ov “is = Figure. 1. Maxim LHO101 Schematic: Figure 2. High Power Voltage Follower with Swing Enhancement. 6 a - MAXIM

Power Operational Amplifier the bias compensation resistor also protects this input. _as 0.1202, these extra resistances can be a significant wm Direct connection of the inputs to ground should be —_ fraction of the total Rsc. The power dissipation of the avoided since excessive fault currents might flowifone _current limit resistor is =z of the power supplies were to be interrupted. A 1k{} or van? aR 38 greater resistor in series with the inputs will avoid this Poiss = _(0.6V)?__ 0.36 Watts = potential problem Rsc (in) Asc r) ____. Heatsinks and Power Dissipation Limits when the LH0101 is used without a heatsink, set the “= The maximum junction temperature of the LHO101 is Current limit to 250mA with 2.7{1 resistors for Rsc. 150°C. This is the basic limitation that, in conjunction Sate 0; ‘Area with the thermal resistance, sets the maximum allow- perating able power dissipation for the LHO101. Specifically, The Safe Operating Area curve shown in the typical characteristics section must not be exceeded. This Ppissimax) = __ 12 (MAX) "TA curve is for a case temperature of 25°C, and must be Oyo + O05 + OSA further derated for operation at elevated case temperatures. rere is the maximum allowable junction There are two basic limits that must be observed: the temperature of the LHO101, 150°C. maximum current limit and the maximum power dis- sipation limit. The SOA curve does not have any limits Ta is the ambient temperature. ‘set by secondary breakdown in the output transistors, _ the power dissipation limit is reached before the fc is the 9101 junction to case thermal resis- transistors approach their secondary breakdown limits, ics is the thermal resistance between the LHO101 case and the heatsink in °C/W. Table 1. HEATSINKS FOR LHO101 sa is the thermal resistance from the heatsink to [Manufacturer] Part# | ambient, | ‘Thermalioy t 6002-19 H The jc of the LH0101 is typically 2° C/W; a conservative eRe | tacseace design should use a value of 2.5°C/W to allow for | HPI-TO3-33CB _| device-to-device variations in yc. The actual power a a dissipation in a given application is the sum of the quiescent power dissipation (850mW typical with ~15V power supplies) and the power dissipation in the out-. Table 2. SOCKETS FOR LHO101 put transistors. The dissipation in the output transis« | = tors is the time average of the instantaneous product of ___Manutacturer [Part ‘Comments a the output current times the voltage difference between _| Robinson Nugent Inc. ‘002011 Chassis or heat | the output and the supply voltage. | | sink mounted socke Short Circuit Current Limiting | | Low cost socket The source and sink current limits are individually set Midland-Ross | 450-3716-01-03-00 | mounting. & by the current sense resistors connected between the —_| . socket pins are | power supplies and the short circuit current limit pins, Hypertronies | ¥skot02-00¢ | requiredto | SC* and SC°. Calculate the resistor values from the | mountone | formula: a | suonremour = 2%. sypentonie pobinson Nugent Ine Rsc 16 Bront Or 800 € 8th St Hudson, MA 01749 New Albany, IN 47150 This equation is only an approximation, and it is not (617) 568-0451 {812} 945-0211 unusual for the actual current limit to vary as much as 25% from the expected value. The 0.6V in the above —IERC , nat A formula is the Vee of Q6 and Q9, which may vary as 185 W. Magnolia By. PO Box 34820 much as 10% from device to device. This Vgealsohasa —Iei8) 736-1182 (214) 243-8327 temperature coefficient of about -2mV/°C. A second error source is the exact value of Rgc. Remember that grigiang-Ross Rsc includes all resistance between the power supply Gammon and the SC terminal, including printed circuit board 45 Concord Ave trace resistance, solder joints, and if a socket is used, Cambridge. MA 02238 the socket contact resistance. SinceRscmay beaslow (617) 491-5400 MAXIM al

Power Operational Amplifier positive feedback is such that the motor speed in- = __— r creases with increased torque load. =z These circuits will either source or sink current, depend- ° ing on the polarity of the input voltage, and can drive [s) DC motors in both directions. J Low Distortion Audio Amplifier ” ° The hermetically packaged LHO101 is well suited for L use as an audio amplifier for severe environments. = Figure 13 shows two LHO101s used in a bridge audio A | power amplifier. The bridge configuration doubles the 1m voltage that can be delivered to the load, in this case C7 delivering 50V peak-peak to an 8{2 speaker. This means nm that a 40 Watts RMS can be delivered to the 81) speaker + while using only +18V power supplies. The harmonic eur o-18 rite L_] distortion is a respectable 0.1%, which should suffice a for all but the most demanding applications. oT CRT Yoke Driver Circuit on, The 300kHz power bandwidth and 5 Amp peak output A Sno current capability of the LHO101 make it well suited for ine CRT yoke driver circuits such as Figure 14. This circuit is basically a constant current source/sink with a transconductance of 435 mA/V (reciprocal of the 2.31 current sense resistor). The resistor Roamp lowers the Q of the inductive yoke; the value of Roamp is chosen empirically for the least distortion at the operating frequency. At low frequencies RoamP is not required. ° DC Servomotor Phase Locked Loop maxion In the circuit of Figure 15, the shaft encoder produces fret 600 pulses per revolution. These pulses are compared Ane cuneNT UT RESTOR 1510 2W toa reference frequency by the digital phase compar- i Fimex msstor a ator of the CD4046. The output of the phase compar- Paro (weut persons im ator passes through a low pass filter and drives the C64 GYMS CARNCITORS, Th U0 ELECTROUITIC input of the LHO101. The LHO101 amplifies this signal Sect BYMSS CAMETORS trav coum and drives the DC servomotor. The phase-frequency comparator of the CD4046 increases or decreases the Figure 13. LHO101 Bridge Audio Power Amplifier. input voltage to the LHO101 until the shaft encoder output is the same frequency as the reference input TO Motor Speed _ Fin x 60 “ (in RPM) N ? ‘Where Fin is the frequency of the reference input and N | . L | is the number of shaft encoder pulses per revolution. aur wn sae A single-pulse-per-revoiution speed pickup can be ise used in place of the shaft encoder, but the PLL low pass 8 tb | filter time constant must be greatly increased a Note that this circuit is similar to a standard phase locked loop except that the LH0101, the motor, and the b shaft encoder replace the internal VCO of the CD4046. Unlike the VCO of the CD4046, the motor adds another pole to the system response and loop stability must be carefully analyzed, particularly if the motor and its load 230) has significant inertia. As with most feedback systems, Re the loop will be stable when there is only one dominant = pole. The loop filter time constant should preferably be | at least 1 decade higher or lower than the constant of Gi least | decade nigh Figure 14. CAT Yoke Driver Circuit MAXIM ees

Figure 15. Servomotor Phase Locked Loop © 1996 Maxim Integrated Products Printed USA MAXIM | registered trademark of Maxim Integrated Products.