EUP3010 EUTECH | Alldatasheet
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DS3010/A Ver1.4 Feb. 2009 1.5MHz,1A Synchronous S t e p - D o w n C o n v e r t e r w i t h S o f t S t a r t
DESCRIPTION
The EUP3010/A is a constant frequency, current mode, PWM step-down converter. The device integrates a main switch and a synchronous rectifier for high efficiency. The 2.5V to 5.5V input voltage range makes the EUP3010/A ideal for powering portable equipment that runs from a single cell Lithium-Ion (Li+) battery or 3-cell NiMH/ NiCd batteries. The output voltage can be regulated as low as 0.6V. The EUP3010/A supports up to 1A load current and can also run at 100% duty cycle for low dropout applications, extending battery life in portable systems. Switching frequency is internally set at 1.5MHz, allowing the use of small surface mount inductors and capacitors. The internal synchronous switch increases efficiency while eliminates the need for an external Schottky diode. The EUP3010/A is available in an adjustable output or fixed output 1.2V ,1.8V and 3.3V. Typical Application Circuit
FEATURES
z High Efficiency up to 96% z 1.5MHz Constant Switching Frequency z 1A Available Load Current z 270µA Typical Quiescent Current z 2.5V to 5.5V Input V oltage Range z Adjustable Output V oltage as Low as 0.6V z 100% Duty Cycle Low Dropout Operation z No Schottky Diode Required z Short Circuit and Thermal Protection z Excellent Line and Load Transient Response z ＜1µA Shutdown Current z Soft Start Function z Over Voltage Protection z Available in 1.2V ,1.8V ,3.3V Fixed Output or Adjustable Output Versions z Available in 2mm ×2mm TDFN-6 and 3mm × 3mm TQFN-16L Package z RoHS Compliant and 100% Lead(Pb)-Free
APPLICATIONS
z Cellular and Smart Phones z Portable Media Players/ MP3 Players z Digital Still and Video Cameras z Portable Instruments z WLAN PC Cards Figure 1. Adjustable Output Regulators
Figure 2. Fixed Output Regulators
DS3010/A Ver1.4 Feb. 2009 EUP3010/A Pin Description PIN EUP3010 TDFN-6 EUP3010A TQFN-16 DESCRIPTION NC 1 6, 8, 16 No Internal Connect( Floating or Connecting to GND). EN 2 7 Chip Enable Pin. Forcing this pin above 1.5V enables the part. Forcing this pin below 0.3V shuts down the device. Do not leave EN floating. VIN 3 9, 10, 11, 12 Supply V oltage Pin. SW 4 13, 14, 15 Switch Node Connection to Inductor. This pin connects to the drains of the internal main and synchronous power MOSFET switches. GND 5 1, 2, 3, 5 Common Ground. FB/VOUT 6 4 Feedback / Output V oltage Pin . EUP3010/A Functional Block Diagram
DS3010/A Ver1.4 Feb. 2009
Ordering Information
Order Number Package Type Markin g Operating Temperature Range EUP3010-12JIR1 TDFN-6 xxx g T -40 °C to +85°C EUP3010-18JIR1 TDFN-6 xxx g D -40 °C to +85°C EUP3010-33JIR1 TDFN-6 xxx g H -40 °C to +85°C EUP3010JIR1 TDFN-6 xxx g A -40 °C to +85°C EUP3010A-12JIR1 TQFN-16 xxxxx 3010A 1 T -40 °C to +85°C EUP3010A-18JIR1 TQFN-16 xxxxx 3010A 1 D -40 °C to +85°C EUP3010A-33JIR1 TQFN-16 xxxxx 3010A 1 H -40 °C to +85°C EUP3010AJIR1 TQFN-16 xxxxx 3010A 1 A -40 °C to +85°C Lead Free Code 1 : L e a d F r e e 0 : L e a d P a c k i n g R : T a p e & R e e l Operating temperature range I: Industry Standard Package Type J: TDFN J: TQFN Output Voltage Option 12: 1.2V 18: 1.8V 33: 3.3V Blank: Adjustable
DS3010/A Ver1.4 Feb. 2009 Absolute Maximum Ratings (1) Recommend Operating Conditions (2) Note (1): Stress beyond those listed under “Absolute Maximum Ratings” may damage the device. Note (2): The device is not guaranteed to function outside the recommended operating conditions.
Electrical Characteristics
Unless otherwise specified, TA=+25°C, VIN=3.6V . EUP3010/A Symbol Parameter Conditions Min Typ Max. Unit VIN Input V oltage Range 2.5 5.5 V IFB Feedback Current ±30 nA IQ Quiescent Current V FB=0.5V or VOUT=90%, SW Open 270 370 µA ISHDN Shutdown Current V EN=0V , VIN= 4.2V 1 µA IPK Peak Inductor Current V IN=3V , VFB=0.5V or VOUT=90% 1.2 1.5 A VFB Regulated Feedback V oltage (Note 3) ADJ Version 0.588 0.6 0.612 V VOUT Regulated Output V oltage IOUT=200mA Fix Version VOUT=1.2V , 1.8V , 3.3V -3 3 % ∆VOUT Output V oltage Line Regulation VIN=2.5V to 5.5V , ILOAD=0 0.25 0.4 %/V ∆VFB Reference V oltage Line Regulation VIN=2.5V to 5.5V 0.25 0.4 %/V VLOADREG Output V oltage Load Regulation ILOAD= 0mA to 1A 0.5 % VFB=0.6V or VOUT=100% 1.2 1.5 1.8 MHzfOSC Oscillator Frequency VFB=0V or VOUT=0V 700 kHz RPFET R DS(ON) of P-Channel FET I SW=200mA 0.28 0.4 Ω RNFET R DS(ON) of N-Channel FET I SW=-200mA 0.30 0.4 Ω ILSW SW Leakage Current V EN=0V , VSW=0V or 5V , VIN=5V ±1 µA VEN EN Threshold 0.3 1.0 1.5 V IEN EN Leakage Current 1 µA Note (3): The EUP3010/A is tested in a proprietary test mode that connects FB to the output of the error amplifier.
DS3010/A Ver1.4 Feb. 2009 Typical Operating Characteristics
DS3010/A Ver1.4 Feb. 2009
DS3010/A Ver1.4 Feb. 2009
DS3010/A Ver1.4 Feb. 2009
Application Information
The EUP3010/A uses a slope-compensated constant frequency, current mode architecture. Both the main (P-Channel MOSFET) and synchronous (N-channel MOSFET) switches are internal. During normal operation, the EUP3010/A regulates output voltage by switching at a constant frequency and then modulating the power transferred to the load each cycle using PWM comparator. The duty cycl e is controlled by three weighted differential sign als: the output of error amplifier, the main switch sense voltage and the slope-compensation ramp. It modulates output power by adjusting the inductor-peak current during the first half of each cycle. An N-channel, synchronous switch turns on during the second half of each cycle (off time). When the inductor current starts to reverse or when the PWM reaches the end of the oscill ator period, the synchronous switch turns off. This keep s excess current from flowing backward through the inductor, from the output capacitor to GND, or through the main and synchronous switch to GND. Inductor Selection The output inductor is selected to limit the ripple current to some predetermined value, typically 20%~40% of the full load current at the maximum input voltage. Large value inductors lower ri pple currents. Higher V IN or VOUT also increases the ripp le current as shown in equation. A reasonable starting point for setting ripple current is ∆I L=400mA (40% of 1A). −××= INV OUTV 1OUTV (f)(L) L∆I The DC current rating of the inductor should be at least equal to the maximum load current plus half the ripple current to prevent core saturation. Thus, a 1.2A rated inductor should be enough for most applications (1A+200mA). For better efficiency, choose a low DC-resistance inductor. C IN and COUT Selection In continuous mode, the source current of the top MOSFET is a square wave of duty cycle V OUT/VIN. The primary function of the input capacitor is to provide a low impedance loop for the edges of pulsed current drawn by the EUP3010/A. A low ESR input capacitor sized for the maximum RMS current must be used. The size required will vary depending on the load, output voltage and input voltage source impedance characteristics. A typical value is around 4.7µF. The input capacitor RMS current varies with the input voltage and the output voltage. The equation for the maximum RMS current in the input capacitor is: The output capacitor C OUT has a strong effect on loop stability. The selection of C OUT is driven by the required effective series resistance (ESR). ESR is a direct function of the volume of the capacitor, that is, physically larger capacitors have lower ESR. Once the ESR requirement for C OUT has been met, the RMS current rating genera lly far exceeds the I RIPPLE(P-P) requirement. The output ripple ∆VOUT is determined by: +×≅ OUT8fC 1ESRL∆IOUT∆V When choosing the input and output ceramic capacitors, choose the X5R or X7R dielectric formulations. These dielectrics have the best temperature and voltage characteristics of all the ceramics for a given value and size. Output Voltage Programming The output voltage is set by a resistive divider according to the following formula: +×= R110.6VOUTV For adjustable voltage packag e, the external resistive divider is connected to the output, allowing remote voltage sensing as shown in below figure. C1 is a feedforward cap which can speed loop response and reduce output ripple during load transient. Choose C1 value between 220pF and 680pF for most applications. −××= INV OV INV OV OIRMSI
DS3010/A Ver1.4 Feb. 2009 Thermal Considerations To avoid the EUP3010/A from exceeding the maximum junction temperature, the user will need to do a thermal analysis. The goal of the thermal analysis is to determine whether the operating conditions exceed the maximum junction temperature of the pa rt. The temperature rise is given by: T R=(PD)(θJA) Where P D=ILOAD 2 × R DS(ON) is the power dissipated by the regulator ; θJA is the thermal resistance from the junction of the die to the ambient temperature. The junction temperature, TJ, is given by: TJ=TA+TR Where TA is the ambient temperature. TJ should be below the maximum junction temperature of 125°C. PC Board Layout Checklist When laying out the printed circuit board, the following guidelines should be used to ensure proper operation of the EUP3010/A. 1. The input capacitor C IN should connect to V IN as closely as possible. This capacitor provides the AC current to the internal power MOSFETs. 2. The power traces, consisting of the GND trace, the SW trace and the V IN trace should be kept short, direct and wide. 3. The FB pin should connect directly to the feedback resistors. The resistive divider R1/R2 must be connected between the COUT and ground. 4. Keep the switching node, SW, away from the sensitive FB node.
DS3010/A Ver1.4 Feb. 2009 Packaging Information TDFN-6 MILLIMETERS INCHES SYMBOLS MIN. MAX. MIN. MAX. A 0.70 0.80 0.028 0.031 A1 0.00 0.05 0.000 0.002 b 0.20 0.40 0.008 0.016 D 1.90 2.10 0.075 0.083 D1 1.40 0.055 E 1.90 2.10 0.075 0.083 E1 0.80 0.031 e 0.65 0.026 L 0.25 0.45 0.010 0.018 DETAIL A
DS3010/A Ver1.4 Feb. 2009 TQFN-16 MILLIMETERS INCHES SYMBOLS MIN. MAX. MIN. MAX. A 0.70 0.80 0.028 0.031 A1 0.00 0.05 0.000 0.002 b 0.18 0.30 0.007 0.012 E 2.90 3.10 0.114 0.122 D 2.90 3.10 0.114 0.122 D1 1.70 0.067 E1 1.70 0.067 e 0.50 0.020 L 0.30 0.50 0.012 0.020