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Technical content

Features

V IN Range: 2.7V to 5.5V
V OUT Fixed or Adjustable from 0.6V to VIN
27µA No Load Quiescent Current
Up to 98% Efficiency
600mA Max Output Current
1.4MHz Switching Frequency
120µs Soft Start
Fast Load Transient
Over-Temperature Protection
Current Limit Protection
100% Duty Cycle Low-Dropout Operation
<1µA Shutdown Current
SOT23-5 Package
Temperature Range: -40°C to +85°C

Applications

Cellular Phones
Digital Cameras
Handheld Instruments
Microprocessor / DSP Core / IO Power
PDAs and Handheld Computers
USB Devices Typical Application (Fixed Output Voltage) 4.7µH 4.7µF 4.7µF C2 EN OUT VIN LX GND APS1056 VIN VO

(Top View) GND LX OUTEN VIN 1 3 4 Pin # Symbol Function 1 VIN Input supply voltage for the converter. 2 GND Ground pin. Connect to the output and input capacitor return. 3 EN Enable pin. 4 OUT Feedback input pin. This pin is connected either directly to the converter output or to an external resistive divider for an adjustable output. 5 LX Switching node. Connect the inductor to this pin. It is internally connected to the drain of both high- and low-side MOSFETs. APS1056 Fast Transient 600mA Step-Down Converter 2 (PRELIMINARY INFORMATION) APS1056.2007.04.0.9

Symbol Description Value Units PD Maximum Power Dissipation2, 3 667 mW θJA Thermal Resistance2 150 °C/W Symbol Description Value Units VIN Input Voltage GND 6.0 V VLX LX to GND -0.3 to V IN + 0.3 V VOUT OUT to GND -0.3 to V IN + 0.3 V VEN EN to GND -0.3 to 6.0 V TJ Operating Junction Temperature Range -40 to 150 °C TLEAD Maximum Soldering Temperature (at leads, 10 sec) 300 °C APS1056 Fast Transient 600mA Step-Down Converter APS1056.2007.04.0.9 (PRELIMINARY INFORMATION) 3 1. Stresses above those listed in Absolute Maximum Ratings may cause permanent damage to the device. Functional operation at condi- tions other than the operating conditions specified is not implied. Only one Absolute Maximum Rating should be applied at any one time. 2. Mounted on an FR4 board. 3. Derate 6.67mW/°C above 25°C.

Fast Transient 600mA Step-Down Converter 4 (PRELIMINARY INFORMATION) APS1056.2007.04.0.9 Electrical Characteristics1 TA = -40°C to +85°C, unless otherwise noted. Typical values are T A = 25°C, VIN = 3.6V. Symbol Description Conditions Min Typ Max Units Step-Down Converter VIN Input Voltage 2.7 5.5 V VIN Rising 2.7 V VUVLO UVLO Threshold Hysteresis 100 mV VIN Falling 1.8 V VOUT Output Voltage Tolerance IOUT = 0 to 600mA, -3.5 +3.5 %VIN = 2.7V to 5.5V VOUT Output Voltage Range 0.6 V IN V IQ Quiescent Current No Load, 0.6V Adjustable 27 70 µAVersion ISHDN Shutdown Current EN = AGND = PGND 1.0 µA ILIM P-Channel Current Limit 600 mA RDS(ON)H High Side Switch On Resistance 0.45 Ω RDS(ON)L Low Side Switch On Resistance 0.40 Ω ILXLEAK LX Leakage Current VIN = 5.5V, VLX = 0 to VIN, 1µ AEN = GND ∆VLinereg Line Regulation V IN = 2.7V to 5.5V 0.1 %/V VOUT Out Threshold Voltage Accuracy 0.6V Output, No Load 591 600 609 mVTA = 25°C IOUT Out Leakage Current 0.6V Output 0.2 µA ROUT Out Impedance >0.6V Output 250 k Ω TS Start-Up Time From Enable to Output 150 µsRegulation FOSC Oscillator Frequency T A = 25°C 1.0 1.4 2.0 MHz TSD Over-Temperature Shutdown Threshold 140 °C THYS Over-Temperature Shutdown Hysteresis 15 °C EN VEN(L) Enable Threshold Low 0.6 V VEN(H) Enable Threshold High 1.4 V IEN Input Low Current V IN = VOUT = 5.5V -1.0 1.0 µA 1. The APS1056 is guaranteed to meet performance specifications over the -40°C to +85°C operating temperature range and is assured by design, characterization, and correlation with statistical process controls.

Efficiency vs. Load (VOUT = 3.3V; L = 6.8µµH) Output Current (mA) Efficiency (%) 100 0.1 1 10 100 1000 VIN = 3.6V VIN = 4.2V VIN = 5.0V DC Regulation (VOUT = 3.3V; L = 6.8µH) Output Current (mA) Output Error (%) -1.0 -0.5 0.0 0.5 1.0 0.1 1 10 100 100 VIN = 5.0V VIN = 4.2V VIN = 3.6V Efficiency vs. Load (VOUT = 2.5V; L = 6.8µµH) Output Current (mA) Efficiency (%) 100 0.1 1 10 100 1000 VIN = 5.0V VIN = 3.6V VIN = 4.2V VIN = 2.7V DC Regulation (VOUT = 2.5V) Output Current (mA) Output Error (%) -1.0 -0.5 0.0 0.5 1.0 0.1 1 10 100 1000 VIN = 5.0V VIN = 3.6V VIN = 3.0V VIN = 4.2V Efficiency vs. Load (VOUT = 1.8V; L = 4.7µµH) Output Current (mA) Efficiency (%) 100 0.1 1 10 100 100 0 VIN = 2.7V VIN = 3.6V VIN = 4.2V DC Regulation (VOUT = 1.8V) Output Current (mA) Output Error (%) -1.0 -0.5 0.0 0.5 1.0 0.1 1 10 100 100 0 VIN = 4.2V VIN = 3.6V VIN = 2.7V APS1056 Fast Transient 600mA Step-Down Converter APS1056.2007.04.0.9 (PRELIMINARY INFORMATION) 5

Fast Transient 600mA Step-Down Converter 6 (PRELIMINARY INFORMATION) APS1056.2007.04.0.9 Typical Characteristics Frequency vs. Input Voltage Input Voltage (V) Frequency Variation (%) -4.0 -3.0 -2.0 -1.0 0.0 1.0 2.0 VOUT = 1.8V VOUT = 2.5V VOUT = 3.3V No Load Quiescent Current vs. Input Voltage Input Voltage (V) Supply Current (µµA) 85°C 25°C -40°C Output Voltage Error vs. Temperature (VIN = 3.6V; VO = 1.8V; IOUT = 400mA) Temperature (°°C) Output Error (%) -2.0 -1.0 0.0 1.0 2.0 -40 -20 0 20 40 60 80 100 Switching Frequency vs. Temperature (VIN = 3.6V; VOUT = 1.8V) Temperature (°°C) Variation (%) -15.0 -12.0 -9.0 -6.0 -3.0 0.0 3.0 6.0 9.0 12.0 15.0 -40 -20 0 20 40 60 80 100 Soft Start (VIN = 3.6V; VOUT = 1.8V; IOUT = 400mA) Time (100µµs/div) Enable and Output Voltage (top) (V) Inductor Current (bottom) (A) -5.0 -4.0 -3.0 -2.0 -1.0 0.0 1.0 2.0 3.0 4.0 5.0 -0.4 -0.2 0.0 0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.6 VEN IL VO Line Regulation (VOUT = 1.8V) Input Voltage (V) Accuracy (%) -0.40 -0.30 -0.20 -0.10 0.00 0.10 0.20 0.30 0.40 IOUT = 10mA IOUT = 400mA IOUT = 1mA

(300mA to 400mA; VIN = 3.6V; VOUT = 1.8V; C1 = 10µµF) Output Voltage (top) (V) Load and Inductor Current (200mA/div) (bottom) Time (50µs/div) 1.75 1.80 1.85 1.90 0.1 0.2 0.3 0.4 VO IO IL 400mA 300mA Load Transient Response (300mA to 400mA; VIN = 3.6V; VOUT = 1.8V; C1 = 10µµF; C4 = 100pF) Output Voltage (top) (V) Load and Inductor Current (200mA/div) (bottom) Time (50µs/div) 1.775 1.800 1.825 1.850 0.1 0.2 0.3 0.4 VO IO IL 400mA 300mA Load Transient Response (1mA to 300mA; VIN = 3.6V; VOUT = 1.8V; C1 = 10µµF; CFF = 100pF) Output Voltage (top) (V) Load and Inductor Current (200mA/div) (bottom) Time (50µs/div) 1.7 1.8 1.9 2.0 VO 300mA 1mA IO IL Load Transient Response (300mA to 400mA; VIN = 3.6V; VOUT = 1.8V; C1 = 4.7µµF) Output Voltage (top) (V) Load and Inductor Current (200mA/div) (bottom) Time (50µs/div) 1.75 1.80 1.85 1.90 0.1 0.2 0.3 0.4 VO IO IL 400mA 300mA P-Channel RDS(ON) vs. Input Voltage Input Voltage (V) RDS(ON) (mΩΩ) 300 350 400 450 500 550 600 650 700 750 25°C 120°C 100°C 85°C N-Channel RDS(ON) vs. Input Voltage Input Voltage (V) RDS(ON) (mΩΩ) 300 350 400 450 500 550 600 650 700 750 25°C 120°C 100°C 85°C APS1056 Fast Transient 600mA Step-Down Converter APS1056.2007.04.0.9 (PRELIMINARY INFORMATION) 7

(VIN = 3.6V; VOUT = 1.8V; IOUT = 400mA) Time (500ns/div) Output Voltage (AC coupled) (top) (mV) Inductor Current (bottom) (A) -120 -100 -80 -60 -40 -20 0.1 0.2 0.3 0.4 0.5 0.6 0.7 0.8 0.9 VO IL Line Response (VOUT = 1.8V @ 400mA) Output Voltage (top) (V) Input Voltage (bottom) (V) Time (25µµs/div) 1.76 1.77 1.78 1.79 1.80 1.81 1.82 3.0 3.5 4.0 4.5 5.0 5.5 6.0 Output Ripple (VIN = 3.6V; VOUT = 1.8V; IOUT = 1mA) Time (10µs/div) Output Voltage (AC coupled) (top) (mV) Inductor Current (bottom) (A) -120 -100 -80 -60 -40 -20 -0.10 -0.05 0.00 0.05 0.10 0.15 0.20 0.25 0.30 VO IL APS1056 Fast Transient 600mA Step-Down Converter 8 (PRELIMINARY INFORMATION) APS1056.2007.04.0.9

Fast Transient 600mA Step-Down Converter APS1056.2007.04.0.9 (PRELIMINARY INFORMATION) 9 Functional Block Diagram EN LX Err .Amp Logic DH DL GND VINOUT Voltage Reference INPUT See note Note: For adjustable version, the internal feedback divider is omitted and the OUT pin is tied directly to the internal error amplifier. Functional Description The APS1056 is a high performance 600mA 1.4MHz monolithic step-down converter. It has been designed with the goal of minimizing external component size and optimizing efficiency over the complete load range. Apart from the small bypass input capacitor, only a small L-C filter is required at the output. Typically, a 4.7µH inductor and a 4.7µF ceramic capacitor are recommended (see table of values). The fixed output version requires only three external power components (C IN, C OUT, and L). The adjustable version can be programmed with external feedback to any voltage, ranging from 0.6V to the input voltage. An additional feed-forward capacitor can also be added to the external feedback to pro- vide improved transient response (see Figure 1). At dropout, the converter duty cycle increases to 100% and the output voltage tracks the input volt- age minus the R DSON drop of the P-channel high- side MOSFET. The input voltage range is 2.7V to 5.5V. The con- verter efficiency has been optimized for all load conditions, ranging from no load to 600mA. The internal error amplifier and compensation pro- vides excellent transient response, load, and line regulation. Soft start eliminates any output voltage overshoot when the enable or the input voltage is applied.

Fast Transient 600mA Step-Down Converter 10 (PRELIMINARY INFORMATION) APS1056.2007.04.0.9 Control Loop The APS1056 is a peak current mode step-down converter. The current through the P-channel MOSFET (high side) is sensed for current loop control, as well as short circuit and overload pro- tection. A fixed slope compensation signal is added to the sensed current to maintain stability for duty cycles greater than 50%. The peak current mode loop appears as a voltage-programmed current source in parallel with the output capacitor. The output of the voltage error amplifier programs the current mode loop for the necessary peak switch current to force a constant output voltage for all load and line conditions. Internal loop compen- sation terminates the transconductance voltage error amplifier output. For fixed voltage versions, the error amplifier reference voltage is internally set to program the converter output voltage. For the adjustable output, the error amplifier reference is fixed at 0.6V. Soft Start / Enable Soft start limits the current surge seen at the input and eliminates output voltage overshoot. When pulled low, the enable input forces the APS1056 into a low-power, non-switching state. The total input current during shutdown is less than 1µA. Current Limit and Over-Temperature Protection For overload conditions, the peak input current is limited. To minimize power dissipation and stresses under current limit and short-circuit conditions, switching is terminated after entering current limit for a series of pulses. Switching is terminated for seven consecutive clock cycles after a current limit has been sensed for a series of four consecutive clock cycles. Thermal protection completely disables switching when internal dissipation becomes excessive. The junction over-temperature threshold is 140°C with 15°C of hysteresis. Once an over-temperature or over-current fault conditions is removed, the output voltage automatically recovers. Under-Voltage Lockout Internal bias of all circuits is controlled via the V IN input. Under-voltage lockout (UVLO) guarantees sufficient V IN bias and proper operation of all inter- nal circuitry prior to activation. Figure 1: Enhanced Transient Response Schematic. L1 CDRH3D16-4R7 4.7µH 10µF 4.7µF U1 APS1056 SOT23-5 C2 4.7µF 10V 0805 X5R VOUT =1.8V GND VIN Enable LX EN OUT VIN LX GND APS1056 GND2 118k 59k C1 10µF 6.3V 0805 X5R 100pF n/a

Fast Transient 600mA Step-Down Converter APS1056.2007.04.0.9 (PRELIMINARY INFORMATION) 11 Applications Information Inductor Selection The step-down converter uses peak current mode control with slope compensation to maintain stability for duty cycles greater than 50%. The output induc- tor value must be selected so the inductor current down slope meets the internal slope compensation requirements. The internal slope compensation for the adjustable and low-voltage fixed versions of the APS1056 is 0.24A/µsec. This equates to a slope compensation that is 75% of the inductor current down slope for a 1.5V output and 4.7µH inductor. This is the internal slope compensation for the adjustable (0.6V) version or low-voltage fixed ver- sions. When externally programming the 0.6V ver- sion to 2.5V, the calculated inductance is 7.5µH. In this case, a standard 6.8µH value is selected. For high-voltage fixed versions ( ≥2.5V), m = 0.48A/ µsec. Table 1 displays inductor values for the APS1056 fixed and adjustable options. Manufacturer's specifications list both the inductor DC current rating, which is a thermal limitation, and the peak current rating, which is determined by the saturation characteristics. The inductor should not show any appreciable saturation under normal load conditions. Some inductors may meet the peak and average current ratings yet result in excessive loss- es due to a high DCR. Always consider the losses associated with the DCR and its effect on the total converter efficiency when selecting an inductor. The 4.7µH CDRH3D16 series inductor selected from Sumida has a 105mΩ DCR and a 900mA DC current rating. At full load, the inductor DC loss is 17mW which gives a 2.8% loss in efficiency for a 600mA, 1.5V output. Input Capacitor Select a 4.7µF to 10µF X7R or X5R ceramic capac- itor for the input. To estimate the required input capacitor size, determine the acceptable input rip- ple level (V PP) and solve for C. The calculated value varies with input voltage and is a maximum when V IN is double the output voltage. Always examine the ceramic capacitor DC voltage coefficient characteristics when selecting the prop- er value. For example, the capacitance of a 10µF, 6.3V, X5R ceramic capacitor with 5.0V DC applied is actually about 6µF. CIN(MIN) = 1 VPP IO VO VIN VO VIN VO VIN CIN = VO VIN VPP IO 0.75 ⋅ VO L = = ≈ 3 ⋅ VO = 3 ⋅ 2.5V = 7.5µH m 0.75 ⋅ VO 0.24A µsec A µsec A A µsec 0.75 ⋅ VO m = = = 0.24 L 0.75 ⋅ 1.5V 4.7µH A µsec Table 1: Inductor Values. Configuration Output Voltage Inductor 0.6V Adjustable With 1V, 1.2V 2.2µH External Feedback 1.5V, 1.8V 4.7µH 2.5V, 3.3V 6.8µH Fixed Output 0.6V to 3.3V 4.7µH

Fast Transient 600mA Step-Down Converter 12 (PRELIMINARY INFORMATION) APS1056.2007.04.0.9 The maximum input capacitor RMS current is: The input capacitor RMS ripple current varies with the input and output voltage and will always be less than or equal to half of the total DC load current. for V IN = 2 · VO The term appears in both the input voltage ripple and input capacitor RMS current equations and is a maximum when V O is twice VIN. This is why the input voltage ripple and the input capacitor RMS current ripple are a maximum at 50% duty cycle. The input capacitor provides a low impedance loop for the edges of pulsed current drawn by the APS1056. Low ESR/ESL X7R and X5R ceramic capacitors are ideal for this function. To minimize stray inductance, the capacitor should be placed as closely as possible to the IC. This keeps the high frequency content of the input current localized, minimizing EMI and input voltage ripple. The proper placement of the input capacitor (C2) can be seen in the evaluation board layout in Figure 2. A laboratory test set-up typically consists of two long wires running from the bench power supply to the evaluation board input voltage pins. The induc- tance of these wires, along with the low-ESR ceramic input capacitor, can create a high Q net- work that may affect converter performance. This problem often becomes apparent in the form of excessive ringing in the output voltage during load transients. Errors in the loop phase and gain meas- urements can also result. Since the inductance of a short PCB trace feeding the input voltage is significantly lower than the power leads from the bench power supply, most applications do not exhibit this problem. In applications where the input power source lead inductance cannot be reduced to a level that does not affect the converter performance, a high ESR tantalum or aluminum electrolytic should be placed in parallel with the low ESR, ESL bypass ceramic. This dampens the high Q network and stabilizes the system. Output Capacitor The output capacitor limits the output ripple and provides holdup during large load transitions. A 4.7µF to 10µF X5R or X7R ceramic capacitor typi- cally provides sufficient bulk capacitance to stabi- lize the output during large load transitions and has the ESR and ESL characteristics necessary for low output ripple. The output voltage droop due to a load transient is dominated by the capacitance of the ceramic out- put capacitor. During a step increase in load cur- rent, the ceramic output capacitor alone supplies the load current until the loop responds. Within two or three switching cycles, the loop responds and the inductor current increases to match the load current demand. The relationship of the output volt- age droop during the three switching cycles to the output capacitance can be estimated by: Once the average inductor current increases to the DC load level, the output voltage recovers. The above equation establishes a limit on the minimum value for the output capacitor with respect to load transients. The internal voltage loop compensation also limits the minimum output capacitor value to 4.7µF. This is due to its effect on the loop crossover frequency (bandwidth), phase margin, and gain margin. Increased output capacitance will reduce the crossover frequency with greater phase margin. COUT = 3 · ∆ILOAD VDROOP · FS VO VIN VO VIN IO RMS(MAX)I 2= VO VIN VO VIN VO VIN VO VIN

Fast Transient 600mA Step-Down Converter APS1056.2007.04.0.9 (PRELIMINARY INFORMATION) 15 For the condition where the step-down converter is in dropout at 100% duty cycle, the total device dis- sipation reduces to: Since R DS(ON), quiescent current, and switching losses all vary with input voltage, the total losses should be investigated over the complete input voltage range. Given the total losses, the maximum junction tem- perature can be derived from the θ JA for the SOT23-5 package which is 160°C/W. Layout The suggested PCB layout for the APS1056 is shown in Figures 2, 3, and 4. The following guide- lines should be used to help ensure a proper layout. 1. The input capacitor (C2) should connect as closely as possible to V IN (Pin 3) and PGND (Pins 6-8). 2. C1 and L1 should be connected as closely as possible. The connection of L1 to the LX pin should be as short as possible. 3. The feedback trace or OUT pin (Pin 2) should be separate from any power trace and connect as closely as possible to the load point. Sensing along a high-current load trace will degrade DC load regulation. If external feed- back resistors are used, they should be placed as closely as possible to the OUT pin (Pin 2) to minimize the length of the high impedance feedback trace. 4. The resistance of the trace from the load return to the PGND (Pins 6-8) should be kept to a minimum. This will help to minimize any error in DC regulation due to differences in the poten- tial of the internal signal ground and the power ground. A high density, small footprint layout can be achieved using an inexpensive, miniature, non- shielded, high DCR inductor. TJ(MAX) = PTOTAL · ΘJA + TAMB PTOTAL = IO 2 · RDSON(HS) + IQ · VIN

Fast Transient 600mA Step-Down Converter 16 (PRELIMINARY INFORMATION) APS1056.2007.04.0.9 Step-Down Converter Design Example Specifications VO = 1.8V @ 600mA (adjustable using 0.6V version), Pulsed Load ∆ILOAD = 300mA VIN = 2.7V to 4.2V (3.6V nominal) FS = 1.4MHz TAMB = 85°C 1.8V Output Inductor (use 4.7µH; see Table 1) For Sumida inductor CDRH3D16, 4.7µH, DCR = 105m Ω. 1.8V Output Capacitor VDROOP = 0.1V 4.7µH · 1.4MHz · 4.2V 23 RMSI L1 · F · VIN(MAX) = · 3 · ∆ILOAD VDROOP · FS 3 · 0.3A 0.1V · 1.4MHz COUT = = = 6.4 µF; use 10µF

= 45mArms (VO) · (VIN(MAX) - VO) = Pesr = esr · IRMS 2 = 5mΩ · (45mA)2 = 10µW IPKL1 = IO + ∆IL1 = 0.6A + 0.068A = 0.668A2 PL1 = IO 2 ⋅ DCR = 0.6A2 ⋅ 105mΩ = 38mW L1 = 3 ⋅ VO2 = 3 ⋅ 1.8V = 5.4µHµsec A µsec A

Fast Transient 600mA Step-Down Converter APS1056.2007.04.0.9 (PRELIMINARY INFORMATION) 17 Input Capacitor Input Ripple VPP = 25mV APS1056 Losses TJ(MAX) = TAMB + ΘJA · PLOSS = 85°C + (160°C/W) · 118mW = 103.9°C PTOTAL + (tsw · F · IO + IQ) · VIN IO 2 · (RDSON(HS) · VO + RDSON(LS) · [VIN -VO]) VIN + (5ns · 1.4MHz · 0.6A + 70µA) · 4.2V = 118mW 4.2V IO RMSI P = esr · IRMS 2= = 0.3Arms CIN = = = 4.87µF; use 4.7µF1 VPP IO 25mV 0.6A

Table 3: Evaluation Board Component Values. Table 4: Typical Surface Mount Inductors. Inductance Max DC DCR Size (mm) Manufacturer Part Number (µH) Current (A) ( Ω) LxWxH Type Adjustable Version R2 = 59kΩ R2 = 221kΩ1 (0.6V device) VOUT (V) R1 (k Ω) R1 (k Ω) L1 (µH) 0.8 19.6 75.0 2.2 0.9 29.4 113 2.2 1.0 39.2 150 2.2 1.1 49.9 187 2.2 1.2 59.0 221 2.2 1.3 68.1 261 2.2 1.4 78.7 301 4.7 1.5 88.7 332 4.7 1.8 118 442 4.7 1.85 124 464 4.7 2.0 137 523 6.8 2.5 187 715 6.8 3.3 267 1000 6.8 Fixed Version R2, R4 Not Used VOUT (V) R1 (k Ω) L1 (µH) 0.6-3.3V 0 4.7 APS1056 Fast Transient 600mA Step-Down Converter 18 (PRELIMINARY INFORMATION) APS1056.2007.04.0.9 1. For reduced quiescent current, R2 and R4 = 221k Ω.

Table 5: Surface Mount Capacitors. Manufacturer Part Number Value Voltage Temp. Co. Case MuRata GRM219R61A475KE19 4.7µF 10V X5R 0805 MuRata GRM21BR60J106KE19 10µF 6.3V X5R 0805 MuRata GRM21BR60J226ME39 22µF 6.3V X5R 0805 APS1056 Fast Transient 600mA Step-Down Converter APS1056.2007.04.0.9 (PRELIMINARY INFORMATION) 19

Fast Transient 600mA Step-Down Converter 20 (PRELIMINARY INFORMATION) APS1056.2007.04.0.9 Advanced Analogic Technologies, Inc. 830 E. Arques Avenue, Sunnyvale, CA 94085 Phone (408) 737-4600 Fax (408) 737-4611 © Advanced Analogic Technologies, Inc. AnalogicTech cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in an AnalogicTech pr oduct. No circuit patent licenses, copyrights, mask work rights, or other intellectual property rights are implied. AnalogicTech reserves the right to make changes to their products or specifications or to discontinue any product or service with- out notice. Except as provided in AnalogicTech’s terms and conditions of sale, AnalogicTech assumes no liability whatsoever, an d AnalogicTech disclaims any express or implied war- ranty relating to the sale and/or use of AnalogicTech products including liability or warranties relating to fitness for a part icular purpose, merchantability, or infringement of any patent, copyright or other intellectual property right. In order to minimize risks associated with the customer’s applications, adequate design and operating safeguards must be provided by the customer to minimize inherent or procedural hazards. Testing and other quality control techniques are utilized to the extent An alogicTech deems necessary to support this warranty. Specific testing of all parameters of each device is not necessarily performed. AnalogicTech and the AnalogicTech logo are trademarks of Advanced Analogic Technologies Incorporated. All other brand and product names appearing in this document are registered trademarks or trademarks of their respective holder s. 1. Contact Sales for other voltage options. 2. XYY = assembly and date code. 3. Sample stock is generally held on part numbers listed in BOLD.

Ordering Information

Package Information

All dimensions in millimeters. 4° ± 4° 0.15 ± 0.07 0.45 ± 0.15 0.10 BSC 1.20 ± 0.25 1.575 ± 0.125 2.80 ± 0.20 0.40 ± 0.10 0.60 REF 2.85 ± 0.15

1.90 BSC

0.95 BSC 1.10 ± 0.20 10° ± 5° GAUGE PLANE 0.075 ± 0.075

0.60 REF

All AnalogicTech products are offered in Pb-free packaging. The term “Pb-free” means semiconductor products that are in compliance with current RoHS standards, including the requirement that lead not exceed 0.1% by weight in homogeneous materials. For more information, please visit our website at http://www.analogictech.com/pbfree. Output Voltage1 Package Marking 2 Part Number (Tape and Reel)3 1.8 SOT23-5 APS1056IGV-1.8-T1 Adj ≥ 0.6 SOT23-5 APS1056IGV-0.6-T1

Product Information

APS1056 specifications and overview.

Summary

Fast Transient 600mA Step-Down Converter

Description

Fast Transient 600mA Step-Down Converter

Source title APS1056 Datasheet(PDF) - Advanced Analogic Technologies

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