AD810AR-REEL

AD810ARZ AD | Alldatasheet

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8-Pin Plastic Mini-DIP (N), SOIC (R) and Cerdip (Q) Packages OFFSET NULL TOP VIEW AD810 DISABLE +VS OUTPUT OFFSET NULL –IN +IN –VS REV. A Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. a Low Power Video Op Amp with Disable AD810 Tel: 617/329-4700 Fax: 617/326-8703

FEATURES

80 MHz Bandwidth (3 dB, G = +1)

75 MHz Bandwidth (3 dB, G = +2)

1000 V/ ms Slew Rate

50 ns Settling Time to 0.1% (V O = 10 V Step) Ideal for Video Applications 30 MHz Bandwidth (0.1 dB, G = +2) 0.02% Differential Gain

0.048 Differential Phase

2.9 nV/ √ Hz Input Voltage Noise 13 pA/ √Hz Inverting Input Current Noise Low Power 8.0 mA Supply Current max 2.1 mA Supply Current (Power-Down Mode) High Performance Disable Function Turn-Off Time 100 ns Break Before Make Guaranteed Input to Output Isolation of 64 dB (OFF State) Flexible Operation Specified for 65 V and 615 V Operation

62.9 V Output Swing Into a 150 V Load (V S = 65 V)

APPLICATIONS

Professional Video Cameras Multimedia Systems NTSC, PAL & SECAM Compatible Systems Video Line Driver ADC/DAC Buffer DC Restoration Circuits PRODUCT DESCRIPTION The AD810 is a composite and HDTV compatible, current feedback, video operational amplifier, ideal for use in systems such as multimedia, digital tape recorders and video cameras. The 0.1 dB flatness specification at bandwidth of 30 MHz (G = +2) and the differential gain and phase of 0.02% and 0.04° (NTSC) make the AD810 ideal for any broadcast quality video system. All these specifications are under load conditions of 150 Ω (one 75 Ω back terminated cable). The AD810 is ideal for power sensitive applications such as video cameras, offering a low power supply current of 8.0 mA max. The disable feature reduces the power supply current to only 2.1 mA, while the amplifier is not in use, to conserve power. Furthermore the AD810 is specified over a power supply range of ± 5 V to ± 15 V. The AD810 works well as an ADC or DAC buffer in video systems due to its unity gain bandwidth of 80 MHz. Because the AD810 is a transimpedance amplifier, this bandwidth can be maintained over a wide range of gains while featuring a low noise of 2.9 nV/√ Hz for wide dynamic range applications. 0.10 0.03 0.01 0.02 0.06 0.04 0.05 0.07 0.08 0.09 1413121110987 0.20 0.18 0.16 0.14 0.12 0.10 0.08 0.06 0.04 0.02 GAIN PHASE GAIN = +2 R F = 715Ω R L = 150Ω fC = 3.58MHz

100 IRE

SUPPLY VOLTAGE – ± Volts DIFFERENTIAL GAIN – % DIFFERENTIAL PHASE – Degrees Differential Gain and Phase vs. Supply Voltage GAIN = +2 R L = 150Ω ±2.5V ±5V ±2.5V PHASE GAIN 10 100 1 1000 –45 –90 –135 –180 –225 –270 CLOSED-LOOP GAIN – dB PHASE SHIFT – Degrees FREQUENCY – MHz ±5V VS = ±15V VS = ±15V Closed-Loop Gain and Phase vs. Frequency, G = +2, RL = 150, RF = 715 Ω

REV. A–2– AD810–SPECIFICATIONS(@ TA = +258C and VS = 615 V dc, RL = 150 V unless otherwise noted) AD810A AD810S 1 Parameter Conditions V S Min Typ Max Min Typ Max Units DYNAMIC PERFORMANCE 3 dB Bandwidth (G = +2) R FB = 715 ± 5 V 4 05 0 4 05 0 M H z (G = +2) RFB = 715 ± 1 5 V 5 57 5 5 57 5 M H z (G = +1) RFB = 1000 ± 1 5 V 4 08 0 4 08 0 M H z (G = +10) RFB = 270 ± 1 5 V 5 06 5 5 06 5 M H z 0.1 dB Bandwidth (G = +2) R FB = 715 ± 5 V 1 32 2 1 32 2 M H z (G = +2) RFB = 715 ± 1 5 V 1 53 0 1 53 0 M H z Full Power Bandwidth V O = 20 V p-p, RL = 400 Ω± 15 V 16 16 MHz Slew Rate2 RL = 150 Ω± 5 V 350 350 V/ µs RL = 400 Ω± 15 V 1000 1000 V/ µs Settling Time to 0.1% 10 V Step, G = –1 ± 15 V 50 50 ns Settling Time to 0.01% 10 V Step, G = –1 ± 15 V 125 125 ns Total Harmonic Distortion f = 10 MHz, V O = 2 V p-p RL = 400 Ω , G = +2 ± 15 V –61 –61 dBc INPUT OFFSET VOLTAGE ± 5 V, ± 15 V 1.5 6 1.5 6 mV TMIN–TMAX ± 5 V, ± 15 V 2 7.5 4 15 mV Offset Voltage Drift 71 5 µV/°C INPUT BIAS CURRENT –Input T MIN–TMAX ± 5 V, ± 15 V 0.7 5 0.8 5 µA +Input T MIN–TMAX ± 5 V, ± 15 V 2 7.5 2 10 µA OPEN-LOOP T MIN–TMAX TRANSRESISTANCE V O = ± 10 V, RL = 400 Ω± 15 V 1.0 3.5 1.0 3.5 M Ω OPEN-LOOP T MIN–TMAX DC VOLTAGE GAIN V O = ± 10 V, RL = 400 Ω± 15 V 86 100 80 100 dB VO = ± 2.5 V, RL = 100 Ω± 5 V 7 68 8 7 28 8 d B COMMON-MODE REJECTION T MIN–TMAX VOS VCM = ± 12 V ± 1 5 V 5 66 4 5 66 4 d B VCM = ± 2.5 V ± 5 V 5 26 0 5 06 0 d B ± Input Current T MIN–TMAX ± 5 V, ± 15 V 0.1 0.4 0.1 0.4 µA/V POWER SUPPLY REJECTION ± 4.5 V to ± 18 V VOS TMIN–TMAX 65 72 60 72 dB ± Input Current T MIN–TMAX 0.05 0.3 0.05 0.3 µA/V INPUT VOLTAGE NOISE f = 1 kHz ± 5 V, ± 15 V 2.9 2.9 nV/ √Hz INPUT CURRENT NOISE –I IN, f = 1 kHz ± 5 V, ± 15 V 13 13 pA/ √Hz +IIN, f = 1 kHz ± 5 V, ± 15 V 1.5 1.5 pA/ √Hz INPUT COMMON-MODE ± 5 V ± 2.5 ± 3.0 ± 2.5 ± 3V VOLTAGE RANGE ± 15 V ± 12 ± 13 ± 12 ± 13 V OUTPUT CHARACTERISTICS Output Voltage Swing 3 RL = 150 Ω , TMIN–TMAX ± 5 V ± 2.5 ± 2.9 ± 2.5 ± 2.9 V RL = 400 Ω± 15 V ± 12.5 ± 12.9 ± 12.5 ± 12.9 V RL = 400 Ω , TMIN–TMAX ± 15 V ± 12 ± 12 V Short-Circuit Current ± 15 V 150 150 mA Output Current T MIN–TMAX ± 5 V, ± 1 5 V 4 06 0 3 06 0 m A OUTPUT RESISTANCE Open Loop (5 MHz) 15 15 Ω INPUT CHARACTERISTICS Input Resistance +Input ± 15 V 2.5 10 2.5 10 M Ω –Input ± 15 V 40 40 Ω Input Capacitance +Input ± 15 V 2 2 pF DISABLE CHARACTERISTICS 4 OFF Isolation f = 5 MHz, See Figure 43 64 64 dB OFF Output Impedance See Figure 43 (R F + RG)i13 pF (R F+ RG)i13 pF

ABSOLUTE MAXIMUM RATINGS 1 Output Short Circuit Duration . . . . Observe Derating Curves Storage Temperature Range Operating Temperature Range NOTES 1Stresses above those listed under “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress rating only and functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied. Exposure to absolute maximum raring conditions for extended periods may affect device reliability. 28-Pin Plastic Package: θJA = 90°C/Watt; 8-Pin Cerdip Package: θJA = 110°C/Watt; 8-Pin SOIC Package: θJA = 150°C/Watt. ESD SUSCEPTIBILITY ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 volts, which readily accumulate on the human body and on test equipment, can discharge without detection. Although the AD810 features ESD protection circuitry, permanent damage may still occur on these devices if they are subjected to high energy electrostatic discharges. Therefore, proper ESD precautions are recommended to avoid any performance degradation or loss of functionality. ORDERING GUIDE Temperature Package Package Model Range Description Option AD810AN –40 °C to +85°C 8-Pin Plastic DIP N-8 AD810AR –40 °C to +85°C 8-Pin Plastic SOIC R-8 AD810AR-REEL –40 °C to +85°C 8-Pin Plastic SOIC R-8 5962-9313201MPA –55 °C to +125°C 8-Pin Cerdip Q-8 AD810A AD810S 1 Parameter Conditions V S Min Typ Max Min Typ Max Units Turn On Time5 ZOUT = Low, See Figure 54 170 170 ns Turn Off Time Z OUT = High 100 100 ns Disable Pin Current Disable Pin = 0 V ± 5 V 5 07 5 5 07 5 µA ± 15 V 290 400 290 400 µA Min Disable Pin Current to Disable T MIN–TMAX ± 5 V, ± 15 V 30 30 µA POWER SUPPLY Operating Range +25 °C to TMAX ± 2.5 ± 18 ± 2.5 ± 18 V TMIN ± 3.0 ± 18 ± 3.5 ± 18 V Quiescent Current ± 5 V 6.7 7.5 6.7 7.5 mA ± 15 V 6.8 8.0 6.8 8.0 mA TMIN–TMAX ± 5 V, ± 15 V 8.3 10.0 9 11.0 mA Power-Down Current ± 5 V 1.8 2.3 1.8 2.3 mA ± 15 V 2.1 2.8 2.1 2.8 mA NOTES 1See Analog Devices Military Data Sheet for 883B Specifications. 2Slew rate measurement is based on 10% to 90% rise time with the amplifier configured for a gain of –10. 3Voltage Swing is defined as useful operating range, not the saturation range. 4Disable guaranteed break before make. 5Turn On Time is defined with ± 5 V supplies using complementary output CMOS to drive the disable pin. Specifications subject to change without notice. MAXIMUM POWER DISSIPATION The maximum power that can be safely dissipated by the AD810 is limited by the associated rise in junction temperature. For the plastic packages, the maximum safe junction tempera- ture is 145°C. For the cerdip package, the maximum junction temperature is 175°C. If these maximums are exceeded momen- tarily, proper circuit operation will be restored as soon as the die temperature is reduced. Leaving the device in the “overheated” condition for an extended period can result in device burnout. To ensure proper operation, it is important to observe the derating curves. 2.4 0.4 140 1.0 0.6 –40 0.8 –60 1.6 1.2 1.4 1.8 2.0 2.2 120100806040200–20 TOTAL POWER DISSIPATION – Watts 8-PIN MINI-DIP AMBIENT TEMPERATURE – 8-PIN SOIC 8-PIN CERDIP 8-PIN MINI-DIP Maximum Power Dissipation vs. Temperature While the AD810 is internally short circuit protected, this may not be sufficient to guarantee that the maximum junction temperature is not exceeded under all conditions. 0.1µF +V S 6AD810 0.1µF –VS 10kΩ SEE TEXT Offset Null Configuration AD810 REV. A –3–

REV. A –11– GENERAL DESIGN CONSIDERATIONS The AD810 is a current feedback amplifier optimized for use in high performance video and data acquisition systems. Since it uses a current feedback architecture, its closed-loop bandwidth depends on the value of the feedback resistor. Table I below contains recommended resistor values for some useful closed- loop gains and supply voltages. As you can see in the table, the closed-loop bandwidth is not a strong function of gain, as it would be for a voltage feedback amp. The recommended resistor values will result in maximum bandwidths with less than 0.1 dB of peaking in the gain vs. frequency response. The –3 dB bandwidth is also somewhat dependent on the power supply voltage. Lowering the supplies increases the values of internal capacitances, reducing the bandwidth. To compensate for this, smaller values of feedback resistor are sometimes used at lower supply voltages. The characteristic curves illustrate that bandwidths of over 100 MHz on 30 V total and over 50 MHz on 5 V total supplies can be achieved. Table I. –3 dB Bandwidth vs. Closed-Loop Gain and Resistance Values (RL = 150 V) VS = 615 V Closed-Loop –3 dB BW Gain R FB RG (MHz) +1 1 k Ω 80 +2 715 Ω 715 Ω 75 +10 270 Ω 30 Ω 65 –1 681 Ω 681 Ω 70 –10 249 Ω 24.9 Ω 65 VS = 65 V Closed-Loop –3 dB BW Gain R FB RG (MHz) +1 910 Ω 50 +2 715 Ω 715 Ω 50 +10 270 Ω 30 Ω 50 –1 620 Ω 620 Ω 55 –10 249 Ω 24.9 Ω 50 ACHIEVING VERY FLAT GAIN RESPONSE AT HIGH FREQUENCY Achieving and maintaining gain flatness of better than 0.1 dB above 10 MHz is not difficult if the recommended resistor values are used. The following issues should be considered to ensure consistently excellent results. CHOICE OF FEEDBACK AND GAIN RESISTOR Because the 3 dB bandwidth depends on the feedback resistor, the fine scale flatness will, to some extent, vary with feedback resistor tolerance. It is recommended that resistors with a 1% tolerance be used if it is desired to maintain exceptional flatness over a wide range of production lots. PRINTED CIRCUIT BOARD LAYOUT As with all wideband amplifiers, PC board parasitics can affect the overall closed-loop performance. Most important are stray capacitances at the output and inverting input nodes. (An added capacitance of 2 pF between the inverting input and ground will add about 0.2 dB of peaking in the gain of 2 response, and increase the bandwidth to 105 MHz.) A space (3/16" is plenty) should be left around the signal lines to minimize coupling. Also, signal lines connecting the feedback and gain resistors should be short enough so that their associated inductance does not cause high frequency gain errors. Line lengths less than 1/4" are recommended. QUALITY OF COAX CABLE Optimum flatness when driving a coax cable is possible only when the driven cable is terminated at each end with a resistor matching its characteristic impedance. If coax were ideal, then the resulting flatness would not be affected by the length of the cable. While outstanding results can be achieved using inexpensive cables, some variation in flatness due to varying cable lengths is to be expected. POWER SUPPLY BYPASSING Adequate power supply bypassing can be critical when optimizing the performance of a high frequency circuit. Inductance in the power supply leads can contribute to resonant circuits that produce peaking in the amplifier's response. In addition, if large current transients must be delivered to the load, then bypass capacitors (typically greater than 1 µF) will be required to provide the best settling time and lowest distortion. Although the recommended 0.1 µF power supply bypass capacitors will be sufficient in most applications, more elaborate bypassing (such as using two paralleled capacitors) may be required in some cases. POWER SUPPLY OPERATING RANGE The AD810 will operate with supplies from ± 18 V down to about ± 2.5 V. On ± 2.5 V the low distortion output voltage swing will be better than 1 V peak to peak. Single supply operation can be realized with excellent results by arranging for the input common-mode voltage to be biased at the supply midpoint. OFFSET NULLING A 10 kΩ pot connected between Pins 1 and 5, with its wiper connected to V+, can be used to trim out the inverting input current (with about ± 20 µA of range). For closed-loop gains above about 5, this may not be sufficient to trim the output offset voltage to zero. Tie the pot's wiper to ground through a large value resistor (50 k Ω for ± 5 V supplies, 150 kΩ for ± 15 V supplies) to trim the output to zero at high closed-loop gains. Applications–

about 750 ns by using open drain logic such as the 74HC05. and is somewhat dependent on the load impedance. Figure 47. A Video Line Driver Operating at a Gain of +2 Figure 48. Closed-Loop Gain and Phase vs. Frequency, Figure 49. Differential Gain and Phase vs. Supply Voltage Figure 50. Fine-Scale Gain (Normalized) vs. Frequency Figure 51. –3 dB Bandwidth vs. Supply Voltage,

REV. A–16– OUTLINE DIMENSIONS Dimensions shown in inches and (mm). Plastic Mini-DIP (N) Package 0.011 ±0.003 (0.28 ±0.08) 0.30 (7.62) REF 15° PIN 1 0.25 (6.35) 0.31 (7.87) 0.10 (2.54) BSC SEATING PLANE 0.035 ±0.01 (0.89 ±0.25) 0.18 ±0.03 (4.57 ±0.76) 0.033 (0.84) NOM 0.018 ±0.003 (0.46 ±0.08) 0.125 (3.18) MIN 0.165 ±0.01 (4.19 ±0.25) 0.39 (9.91) MAX Cerdip (Q) Package 0.320 (8.13) 0.290 (7.37) 0.015 (0.38) 0.008 (0.20) 15° 0.005 (0.13) MIN 0.055 (1.40) MAX PIN 1 0.310 (7.87) 0.220 (5.59) 0.405 (10.29) MAX 0.200 (5.08) MAX SEATING PLANE 0.023 (0.58) 0.014 (0.36) 0.070 (1.78) 0.030 (0.76) 0.060 (1.52) 0.015 (0.38) 0.150 (3.81) MIN 0.200 (5.08) 0.125 (3.18) 0.100 (2.54) BSC 8-Pin SOIC (R) Package 0.019 (0.48) 0.014 (0.36) 0.050 (1.27) BSC 0.102 (2.59) 0.094 (2.39) 0.197 (5.01) 0.189 (4.80) 0.010 (0.25) 0.004 (0.10) 0.098 (0.2482) 0.075 (0.1905) 0.190 (4.82) 0.170 (4.32) 0.030 (0.76) 0.018 (0.46) 10° 0.090 (2.29) CHAMF 8 5 4PIN 1 0.157 (3.99) 0.150 (3.81) 0.244 (6.20) 0.228 (5.79) 0.150 (3.81) All brand or product names mentioned are trademarks or registered trademarks of their respective holders. C1737–24–10/92PRINTED IN U.S.A.