AAT2503 ANALOGICTECH | Alldatasheet

Document overview

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Technical content

Features

  • 800mA Step-Down Converter —V IN Range: 2.7V to 5.5V —V OUT Range: 0.9V to VIN — High Efficiency — 2MHz Switching Frequency
  • Two 150mA Low Dropout Regulators OUT Range: 0.6V to VIN — High Output Accuracy: ±1.5%
  • 85µA of Total I Q
  • Independent Enable Pins
  • Integrated Power MOSFETs
  • Over-Temperature and Current Limit Protection
  • QFN34-20 Package
  • -40°C to +85°C Temperature Range

Applications

  • Cellular Phones
  • Digital Cameras
  • Handheld Instruments
  • Microprocessor/DSP Core/IO Power
  • PDAs and Handheld Computers Typical Application AAT2503 R5 R7 2.2μF OUTA OUTB POKPOK OUTA OUTB AGND VLDOA VLDOB LX FB VOUT (Buck) PGND VIN VP FBB FBA 2.2μF 10μF ENB EN ENA VIN 100kΩ MODE/SYNC

Pin # Symbol Function 1 FBB Feedback input pin for LDOB. This pin is connected to OUTB via an external resistor. It is used to see the output of LDOB to regulate to the desired value via an external resistor divider. For fixed versions, short FBB to OUTB. 2 ENA Enable pin for LDOA. When connected low, LDOA is disabled and consumes less than 1µA of current. When connected high, normal operation. 3 ENB Enable pin for LDOB. When connected low, LDOB is disabled and consumes less than 1µA of current. When connected high, normal operation. 4 MODE/SYNC Connect to ground for PWM/PFM mode and optimized efficiency throughout the load range. Connect high for low noise PWM operation under all operating conditions. Connect to an external clock for synchronization (PWM only). 5 FB Feedback input pin for the step-down converter. This pin is connected to the converter out- put via an external resistor. It is used to see the output of the converter to regulate to the desired value via an external resistor divider. 6 AGND Ground connection pin. 7 PGND Main power ground return pin for the step-down converter. Connect to the output and input capacitor return. 8, 9 LX Connect inductor to this pin. Switching node internally connected to the drain of both high- and low-side MOSFETs. 10 VP Input supply voltage for the converter. Must be closely decoupled. 11, 12 N/C Not connected. 13 VIN Bias supply. Supply power for the internal circuitry. Connect to input power via low pass filter with decoupling to AGND. 14 EN Enable for the step-down converter. A logic low disables the converter and it consumes less than 1µA of current. A logic high enables normal operation. 15 POK Power-OK pin with open drain output. It is pulled low when the OUTA pin is outside the regu- lation window of ±10%. Place a pull-up resistor between POK and OUTA. 16 FBA Feedback input pin for LDOA. This pin is connected to OUTA via an external resistor. It is used to see the output of LDOA to regulate to the desired value via an external resistor divider. For fixed versions, short FBA to OUTA. 17 OUTA LDOA output pin; should be closely decoupled with a low-ESR ceramic capacitor. 18 VLDOA Input voltage pin for linear regulator A; should be closely decoupled. 19 VLDOB Input voltage pin for linear regulator B; should be closely decoupled. 20 OUTB LDOB output pin; should be closely decoupled with a low-ESR ceramic capacitor. EP Exposed paddle; connect to ground directly beneath the package. AAT2503 Adjustable 3-Channel Regulator 2 2503.2007.04.1.1

(Top View) Absolute Maximum Ratings1 Thermal Information FBB ENA ENB MODE/SYNC FB AGND PGND LX LX VP VIN EN N/C N/C POK FBA OUTA VLDOA VLDOB OUTB Symbol Description Value Units VP, VIN, VLDO Input Voltage and Bias Power to GND 6.0 V VLX LX to GND -0.3 to VP + 0.3 V VFB FB to GND -0.3 to VP + 0.3 V VN EN, MODE/SYNC to GND -0.3 to 6.0 V TJ Operating Junction Temperature Range -40 to 150 °C TLEAD Maximum Soldering Temperature (at leads, 10 sec) 300 °C Symbol Description Value Units PD Maximum Power Dissipation (TA = 25°C) 2.0 W θJA Thermal Resistance2 50 °C/W AAT2503 Adjustable 3-Channel Regulator 2503.2007.04.1.1 3 1. Stresses above those listed in Absolute Maximum Ratings may cause permanent damage to the device. Functional operation at condi- tions other than the operating conditions specified is not implied. Only one Absolute Maximum Rating should be applied at any one time. 2. Mounted on an FR4 board.

Electrical Characteristics1 VIN = 3.6V; TA = -40°C to +85°C, unless otherwise noted. Typical values are T A = 25°C. Symbol Description Conditions Min Typ Max Units Bias Power Supply IQ Quiescent Current ENA = ENB = EN = VIN; ILOAD = 0 85 145 µA ISHDN Shutdown Current ENA = ENB = EN = GND 1.0 µA LDOA, LDOB; IOUT = 150mA VLDO Input Voltage 2.8 5.5 V VOUT Output Voltage Tolerance IOUT = 1mA T A = 25°C -1.5 1.5 %to 150mA T A = -40°C to +85°C -2.5 2.5 VFB Feedback Voltage 0.593 0.6 0.607 V VDO Dropout Voltage2 IOUT = 150mA 150 mV ΔVOUT/ VOUT*ΔVIN Line Regulation3 VIN = VOUT + 1 to 5.0V 0.09 %/V VEN(L) Enable Threshold Low 0.6 V VEN(H) Enable Threshold High 1.4 V IOUT Output Current 150 mA ISC Short-Circuit Current VOUT < 0.4V 300 mA ISHT Shutdown Current VIN = 5V 1.0 µA TSD Over-Temperature Shutdown 140 °CThreshold THYS Over-Temperature Shutdown 15 °CHysteresis LDOA; IOUT = 150mA VPOK Power-OK Trip Threshold VOUT Rising, TA = 25°C 90 94 98 % of V OUT VPOKHYS Power-OK Hysteresis 1.0 % of V OUT VPOK(LO) Power-OK Output Voltage Low I SINK = 1mA 0.4 V IPOK Power-OK Output Leakage Current V POK <5.5V, VOUT in Regulation 1.0 µA AAT2503 Adjustable 3-Channel Regulator 4 2503.2007.04.1.1 1. The AAT2503 is guaranteed to meet performance specifications over the -40°C to +85°C operating temperature range and is assu red by design, characterization, and correlation with statistical process controls. 2. VDO is defined as VIN - VOUT when VOUT is 98% of nominal. 3. CIN = 10µF.

Electrical Characteristics (continued)1 VIN = 3.6V; TA = -40°C to +85°C, unless otherwise noted. Typical values are T A = 25°C. Symbol Description Conditions Min Typ Max Units Step-Down Converter; IOUT = 800mA VIN Input Voltage 2.7 5.5 V VIN Rising 1.8 V UVLO Under-Voltage Lockout Voltage Hysteresis 250 mV VIN Falling 1.5 V VOUT Output Voltage Tolerance IOUT = 0 to 800mA; -3.0 3.0 %VIN = 2.7V to 5.5V VOUT VOUT Programmable Range 0.9 VIN V VFB Feedback Threshold Voltage 0.891 0.9 0.909 V ISHDN Shutdown Current EN = GND 1.0 µA ILX_LEAK LX Leakage Current VIN = 5.5, VLX = 0 to VIN 1.0 µA IFB Feedback Leakage VFB = 1.0V 0.2 µA ILIM Current Limit 1.2 A RDS(ON)H High Side Switch On Resistance 400 mΩ RDS(ON)L Low Side Switch On Resistance 300 mΩ ΔVOUT/VOUT Load Regulation ILOAD = 0 to 800mA 0.5 % ΔVOUT/ VOUT*ΔVIN Line Regulation 0.2 %/V FOSC Oscillator Frequency 1.6 2.0 2.4 MHz TSD Over-Temperature Shutdown 140 °CThreshold THYS Over-Temperature Shutdown 15 °CHysteresis VEN(L) Enable Threshold Low 0.6 V VEN(H) Enable Threshold High 1.4 V IEN EN Input Leakage VEN = 5V, VIN = 5V -1.0 1.0 µA VMODE/SYNC(L) Enable Threshold Low VIN × V0.4 VMODE/SYNC(H) Enable Threshold High VIN × V0.7 IMODE/SYNC Input Low Current -1.0 1.0 µA AAT2503 Adjustable 3-Channel Regulator 2503.2007.04.1.1 5 1. The AAT2503 is guaranteed to meet performance specifications over the -40°C to +85°C operating temperature range and is assu red by design, characterization, and correlation with statistical process controls.

Typical Characteristics—Step-Down Converter Efficiency vs. Output Current (VOUT = 2.5V; L = 3.3µH) Output Current (mA) Efficiency (%) 607080 100 0 1 10 100 1000 VIN = 4.2V VIN = 3.6V VIN = 3.3V PWM Only Mode Efficiency vs. Output Current (VOUT = 1.8V; L = 2.2µH) Output Current (mA) Efficiency (%) 607080 100 0 1 10 100 100 VIN = 4.2V VIN = 3.6V VIN = 2.7V PWM Only Mode Efficiency vs. Output Current (VOUT = 0.9V; L = 1µH) Output Current (mA) Efficiency (%) 2030 8090 0 1 10 100 1000 VIN = 3.6V VIN = 2.7V VIN = 4.2V PWM Only Mode Switching Frequency vs. Temperature (VIN = 3.6V; IOUT = 800mA) Temperature (°°C) Frequency (MHz) 1.5 1.6 1.7 1.8 1.9 2.0 2.1 2.2 2.3 2.4 -40 -20 0 20 40 60 80 100 VOUT = 0.9V VOUT = 1.8V VOUT = 2.5V Load Regulation (VOUT = 1.8V; VMODE/SYNC = VIN; L = 2.2µH) Output Current (mA) Accuracy (%) -1.2 -0.9-0.6 -0.3 0 1 10 100 100 VIN = 4.2V VIN = 3.3V VIN = 3.6V Soft Start (VIN = 3.6V; VOUT = 1.8V; IOUT = 800mA) ENABLE and VOUT (Top and Middle) (V) Inductor Current (Bottom) (A) Time (100µs/div) 0.0 2.0 4.0 6.0 -0.5 0.0 0.5 1.0 ENABLE VOUT IINDUCTOR 1.8V AAT2503 Adjustable 3-Channel Regulator 6 2503.2007.04.1.1

Typical Characteristics—Step-Down Converter No Load Quiescent Current vs. VIN (VOUT = 0.9V; L = 1µH) Input Voltage (V) Quiescent Current (µA) 3540 TA = 25°C TA = 85°C TA = -40°C Output Voltage Error vs. Temperature (VIN = 3.6V; VOUT = 0.9V; IOUT = 800mA) Temperature (°°C) Output Voltage Error (%)-2.0 -1.5 -1.0 -0.5 0.0 0.5 1.0 1.5 2.0 -40 -20 0 20 40 60 80 100 VOUT = 0.9V VIN = 1.8V VIN = 2.5V Turn Off (VIN = 3.6V; VOUT = 1.8V; IOUT = 800mA) ENABLE and VOUT (Top and Middle) (V) Inductor Current (Bottom) (A) Time (100µs/div) 0.0 2.0 4.06.0 -0.5 0.0 0.5 1.00V 1.8V ENABLE VOUT (1V/div) IINDUCTOR Line Regulation (VOUT = 1.8V; VMODE/SYNC = VIN) Accuracy (%) Input Voltage (V) -1.2 -0.9 -0.6 -0.3 0.00.30.6 0.9 1.2 IL = 800mA IL = 100mA IL = 10mA Line Regulation (VOUT = 0.9V; VMODE/SYNC = VIN) Accuracy (%) Input Voltage (V) -1.2 -0.9 -0.6 -0.3 0.0 0.30.6 0.9 1.2 IL = 800mA IL = 650mA No Load Quiescent Current vs. VIN (VOUT = 1.8V; L = 2.2µH) Input Voltage (V) Quiescent Current (µA) 4045 TA = 85°C TA = -40°C TA = 25°C AAT2503 Adjustable 3-Channel Regulator 2503.2007.04.1.1 7

Typical Characteristics—Step-Down Converter Light Load Output Ripple (VIN = 2.7V; VOUT = 1.8V; IOUT = 1mA) Inductor Current (Bottom) (A) Output Voltage (AC coupled) (Top) (mV) Time (10µs/div) -0.2 0.0 0.2 0.4 0.60.81.0 1.2 1.4 -60 -50 -40 -30-20-10 1020 VOUT IINDUCTOR Heavy Load Output Ripple (VIN = 3.6V; VOUT = 1.8V; IOUT = 800mA) Inductor Current (Bottom) (A) Output Voltage (AC coupled) (Top) (mV) Time (200ms/div) 0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 -60 -50 -40 -30 -20 -10 VOUT IINDUCTOR Line Transient (VOUT = 1.8V; IOUT = 800mA; VIN = 3.6V to 4.2V) Input Voltage (top) (V) Output Voltage (bottom) (V) Time (20µs/div) 0.0 0.5 1.0 1.52.0 2.5 3.0 3.54.0 4.5 5.0 1.5 1.6 1.7 1.81.9 2.0 2.1 2.22.3 2.4 2.5 Load Transient (VIN = 3.6V; VOUT = 1.8V; IOUT = 300mA to 650mA) Output Voltage (top) (V) Load and Inductor Current (Bottom) (A) Time (20µs/div) 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.02.2 0.0 0.3 0.6 VOUT IOUT IINDUCTOR 650mA 300mA AAT2503 Adjustable 3-Channel Regulator 8 2503.2007.04.1.1

Adjustable 3-Channel Regulator 2503.2007.04.1.1 9 Typical Characteristics—LDO Regulator DC Regulation (VIN = 3.6V; VOUT = 1.8V) DC Regulation (%) Temperature (°°C) -2.5 -2.0 -1.5 -1.0 -0.5 0.0 0.5 1.0 1.52.02.5 -40 -20 0 20 40 60 80 10 IOUT = 1mA IOUT = 150mA IOUT = 100mA IOUT = 50mA DC Regulation (VIN = 3.6V; VOUT = 2.8V) DC Regulation (%) Temperature (°°C) -2.5 -2.0 -1.5-1.0 -0.5 0.0 0.5 1.01.52.02.5 -40 -20 0 20 40 60 80 100 IOUT = 1mA IOUT = 150mAIOUT = 100mA IOUT = 50mA Dropout Characteristics Input Voltage (V) Output Voltage (V) 2.4 2.5 2.6 2.7 2.8 2.9 3.0 150mA 100mA 50mA 10mA 1mA DC Regulation (VIN = 3.6V; VOUT = 1.2V) DC Regulation (%) Temperature (°°C) -2.5 -2.0-1.5 -1.0 -0.5 0.0 0.51.0 1.5 2.02.5 -40 -20 0 20 40 60 80 10 IOUT = 1mA IOUT = 150mA IOUT = 100mA IOUT = 50mA Dropout Voltage vs. Temperature (VOUT = 2.8V) Temperature (°°C) Dropout Voltage (mV) 2040 100 120 -40 -20 0 20 40 60 80 100 12 150mA 100mA 50mA Dropout Voltage vs. Output Current (VOUT = 2.8V) Output Current (mA) Dropout Voltage (mV) 4050 6070 100 0 20 40 60 80 100 120 140 160 85°C 25°C -40°C

Typical Characteristics—LDO Regulator Load Transient (VIN = 3.6V; VOUT = 1.8V; IOUT = 50mA to 100mA) Output Current (Bottom) (A) Output Voltage (Top) (V) Time (50µs/div) 0.6 0.8 1.01.2 1.4 1.6 1.8 2.02.2 -0.1 0.0 0.10.2 0.3 0.4 0.5 0.60.7 Turn-Off Response Time (VIN = 3.6V; VOUT = 1.8V; IOUT = 150mA) ENABLE (Top ) (V) Output Voltage (Bottom) (V) Time (50µs/div) -10 Load Transient (VIN = 3.6V; VOUT = 1.8V; IOUT = 1mA to 100mA) Output Voltage (top) (V) Output Current (Bottom) (A) Time (200µs/div) 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.0 2.2 -0.1 0.0 0.1 0.2 0.3 0.4 0.5 0.6 0.7 Quiescent Current vs. Input Voltage (VOUT = 2.8V) Input Voltage (V) Quiescent Current (µA) 1923 2731 IOUT = 0mA IOUT = 10mA IOUT = 50mA IOUT = 100mAIOUT = 150mA Turn-On Response Time (VIN = 3.6V; VOUT = 1.8V; IOUT = 150mA) ENABLE (Top ) (V) Output Voltage (Bottom) (V) Time (10µs/div) -10 AAT2503 Adjustable 3-Channel Regulator 10 2503.2007.04.1.1

Typical Characteristics—LDO Regulator Load Regulation (VOUT = 2.8V) Output Current (mA) Output Error (%) -2.0 -1.5 -1.0 -0.5 0.0 0.5 1.0 1.52.0 0 1 10 100 100 VIN = 3.3V VIN = 3.6V VIN = 5.5V VIN = 4.2V Line Regulation (VOUT = 1.2V) Output Error (%) Input Voltage (V) -2.0 -1.5 -1.0 -0.5 0.0 0.5 1.0 1.5 2.0 150mA 100mA 50mA 10mA1mA Load Regulation (VOUT = 1.2V) Output Current (mA) Output Error (%) -2.0 -1.5 -1.0 -0.5 0.0 0.5 1.0 1.52.0 0 1 10 100 100 VIN = 2.7V VIN = 3.6V VIN = 5.5V VIN = 4.2V Line Transient (VOUT = 1.8V; IOUT = 100mA; VIN = 3.6V to 4.2V) Input Voltage (top) (V) Output Voltage (bottom) (V) Time (100µs/div) 0.0 0.51.01.5 2.0 2.5 3.0 3.5 4.0 4.55.0 1.6 1.71.81.9 2.0 2.1 2.2 2.3 2.4 2.52.6 VOUT VIN Line Transient (VOUT = 1.8V; IOUT = 150mA; VIN = 3.6V to 4.2V) Input Voltage (top) (V) Output Voltage (bottom) (V) Time (100µs/div) 0.0 0.5 1.01.52.0 2.5 3.0 3.54.04.55.0 1.5 1.6 1.71.81.9 2.0 2.1 2.22.32.42.5 VOUT VIN AAT2503 Adjustable 3-Channel Regulator 2503.2007.04.1.1 11

Adjustable 3-Channel Regulator 12 2503.2007.04.1.1 Functional Block Diagram EN VLDOA OUTB MODE/SYNC POK LXLogic DH DL PGND VINFB AGND OUTA VLDOB FBB FBA ENA ENB VP Control Logic Voltage Reference Voltage Reference 94% VREF Err. Amp. Err. Amp. Err. Amp. Over-Current Protection Over-Current Protection Functional Description The AAT2503 is a high performance power man- agement IC comprised of a step-down converter and two linear regulators. The step-down convert- er operates in both fixed and variable frequency modes for high efficiency performance. The switch- ing frequency is 2MHz, minimizing the size of the inductor. The converter requires only three external components (C IN, C OUT, and L). The LDOs can deliver up to 150mA each. Each regulator has independent input voltage and enable pins and operates with ceramic capacitors. Switch-Mode Step-Down Converter The switching regulator is a monolithic step-down converter operating with input voltage range of 2.7V to 5.5V. Power devices are sized for 800mA current capability and achieve over 95% efficiency. PFM operation maintains high efficiency under light load conditions (typically <50mA). The MODE/SYNC pin allows an optional "PWM Only" mode. This main- tains constant frequency and low output ripple across all load conditions. Alternatively, the IC can be synchronized to an external clock via the MODE/SYNC input. External synchronization is maintained between 1MHz and 3MHz. It consumes 30µA of typical no load quiescent current, making it also ideal for light load applications. The oscillator operates at 2MHz, minimizing the cost and size of external components. A logic low on the EN pin shuts the converter down and makes it consume less than 1µA of current. Soft start increases the inductor current limit point in discrete steps when the input voltage or enable input is applied. It limits the current surge seen at the input and eliminates output voltage overshoot.

Adjustable 3-Channel Regulator 2503.2007.04.1.1 13 For overload conditions, the peak input current is limited. As load impedance decreases and the out- put voltage falls closer to zero, more power gets internally dissipated, raising the device tempera- ture. Thermal protection completely disables switching when internal dissipation becomes excessive, protecting the device from damage. The junction over-temperature threshold is 140°C with 15°C of hysteresis. Control Loop The AAT2503 includes a peak current mode step- down converter. The current through the P-channel MOSFET (high side) is sensed for current loop control, as well as short-circuit and overload pro- tection. A fixed slope compensation signal is added to the sensed current to maintain stability for duty cycles greater than 50%. The peak current mode loop appears as a voltage-programmed current source in parallel with the output capacitor. The output of the voltage error amplifier programs the current mode loop for the necessary peak switch current to force a constant output voltage for all load and line conditions. Internal loop compen- sation terminates the transconductance voltage error amplifier output. For fixed voltage versions, the error amplifier reference voltage is internally set to program the converter output voltage. For the adjustable output, the error amplifier reference is fixed at 0.9V. Soft Start / Enable Soft start limits the current surge seen at the input and eliminates output voltage overshoot in the step-down converter. The step-down converter and the two LDOs have independent enable pins. When pulled low, the enable input forces the LDO into shutdown mode and forces the step-down converter into a low- power, non-switching state. The input current dur- ing shutdown is less than 1µA. Linear Regulators The two linear regulators are high performance LDOs where each LDO can source up to 150mA of current. For added flexibility, both regulators have independent input voltages operating from 2.8V to 5.5V. An external feedback pin for each LDO allows programming the output voltage from V IN to 0.6V. The regulators have short-circuit and thermal pro- tection in case of adverse operating conditions. LDOA features an integrated Power-OK compara- tor which indicates when the output is out of regu- lation. The POK is an open drain output and it is held low when the AAT2503 is in shutdown mode. Under-Voltage Lockout Internal bias of all circuits is controlled via the VIN pin. Under-voltage lockout guarantees sufficient V IN bias and proper operation of all internal circuits prior to activation. Over-Temperature Protection Thermal protection completely disables switching when internal dissipation becomes excessive. The junction over-temperature threshold is 140°C with 15°C of hysteresis. Once an over-temperature or over-current fault conditions is removed, the output voltage automatically recovers.

Adjustable 3-Channel Regulator 14 2503.2007.04.1.1 Applications Information Step-Down Converter Inductor Selection The step-down converter uses peak current mode control with slope compensation to maintain stability for duty cycles greater than 50%. The output induc- tor value must be selected so the inductor current down slope meets the internal slope compensation requirements. The internal slope compensation for the AAT2503 step-down converter is 0.51A/µsec. This equates to a slope compensation that is 75% of the inductor current down slope for a 1.5V output and 2.2µH inductor. Manufacturer's specifications list both the inductor DC current rating, which is a thermal limitation, and the peak current rating, which is determined by the saturation characteristics. The inductor should not show any appreciable saturation under normal load conditions. Some inductors may meet the peak and average current ratings yet result in excessive loss- es due to a high DCR. Always consider the losses associated with the DCR and its effect on the total converter efficiency when selecting an inductor. The 2.2µH CDRH2D14 series Sumida inductor has a 94mΩ DCR and a 1.5A DC current rating. At full 800mA load, the inductor DC loss is 17mW which gives a 2.8% loss in efficiency for a 800mA, 1.8V output. Input Capacitor Select a 4.7µF to 10µF X7R or X5R ceramic capac- itor for the input of the step-down converter. To esti- mate the required input capacitor size, determine the acceptable input ripple level (V PP) and solve for CIN. The calculated value varies with input voltage and is a maximum when V IN is double the output voltage. Always examine the ceramic capacitor DC voltage coefficient characteristics when selecting the prop- er value. For example, the capacitance of a 10µF, 6.3V, X5R ceramic capacitor with 5.0V DC applied is actually about 6µF. The maximum input capacitor RMS current is: The input capacitor RMS ripple current varies with the input and output voltage and will always be less than or equal to half of the total DC load current. 0.75 ⋅ VO m = = = 0.51 L 0.75 ⋅ 1.5V 2.2μH A μsec VO VIN VO VIN CIN(MIN) = 1 VPP IO VO VIN VO VIN VO VIN CIN = VO VIN VPP IO VO VIN VO VIN Table 1: Inductor Values. Configuration Output Voltage Inductor 0.9V Adjustable With 1V, 1.2V 1.5µH External Feedback 1.5V, 1.8V 2.2µH 2.5V, 3.3V 3.3µH

Adjustable 3-Channel Regulator 2503.2007.04.1.1 15 for VIN = 2 x VO: The term appears in both the input voltage ripple and input capacitor RMS current equations and is a maximum when V O is twice VIN. This is why the input voltage ripple and the input capacitor RMS current ripple are a maximum at 50% duty cycle. The input capacitor provides a low impedance loop for the edges of pulsed current drawn by the AAT2503. Low ESR/ESL X7R and X5R ceramic capacitors are ideal for this function. To minimize stray inductance, the capacitor should be placed as closely as possible to the IC. This keeps the high frequency content of the input current localized, minimizing EMI and input voltage ripple. A laboratory test set-up typically consists of two long wires running from the bench power supply to the evaluation board input voltage pins. The induc- tance of these wires, along with the low-ESR ceramic input capacitor, can create a high Q net- work that may affect converter performance. This problem often becomes apparent in the form of excessive ringing in the output voltage during load transients. Errors in the loop phase and gain meas- urements can also result. Since the inductance of a short PCB trace feeding the input voltage is significantly lower than the power leads from the bench power supply, most applications do not exhibit this problem. In applications where the input power source lead inductance cannot be reduced to a level that does not affect the converter performance, a high ESR tantalum or aluminum electrolytic should be placed in parallel with the low ESR, ESL bypass ceramic. This dampens the high Q network and stabilizes the system. Output Capacitor The output capacitor limits the output ripple and provides holdup during large load transitions. A 4.7µF to 10µF X5R or X7R ceramic capacitor typi- cally provides sufficient bulk capacitance to stabi- lize the output during large load transitions and has the ESR and ESL characteristics necessary for low output ripple. The output voltage droop due to a load transient is dominated by the capacitance of the ceramic out- put capacitor. During a step increase in load cur- rent, the ceramic output capacitor alone supplies the load current until the loop responds. Within two or three switching cycles, the loop responds and the inductor current increases to match the load current demand. The relationship of the output volt- age droop during the three switching cycles to the output capacitance can be estimated by: Once the average inductor current increases to the DC load level, the output voltage recovers. The above equation establishes a limit on the minimum value for the output capacitor with respect to load transients. The internal voltage loop compensation also limits the minimum output capacitor value to 4.7µF. This is due to its effect on the loop crossover frequency (bandwidth), phase margin, and gain margin. Increased output capacitance will reduce the crossover frequency with greater phase margin. Adjustable Output Resistor Selection The output voltage on the step-down converter is programmed with external resistors R2 and R6. To limit the bias current required for the external feed- back resistor string while maintaining good noise immunity, the minimum suggested value for R6 is 59kΩ. Although a larger value will further reduce quiescent current, it will also increase the imped- ance of the feedback node, making it more sensitive to external noise and interference. Table 2 summa- rizes the resistor values for various output voltages with R6 set to either 59kΩ for good noise immunity or 221kΩfor reduced no load input current. With enhanced transient response for extreme pulsed load application, an external feed-forward capacitor (C1 in Fig.3) can be added. COUT = 3 · ΔILOAD VDROOP · FS VO VIN VO VIN IO RMS(MAX)I 2=

Adjustable 3-Channel Regulator 16 2503.2007.04.1.1 Table 2: Step-Down Converter Resistor Values for Various Output Voltages. Thermal Calculations There are three types of losses associated with the AAT2503 step-down converter: switching losses, conduction losses, and quiescent current losses. Conduction losses are associated with the R DS(ON) characteristics of the power output switching devices. Switching losses are dominated by the gate charge of the power output switching devices. At full load, assuming continuous conduction mode (CCM), a simplified form of the LDO losses is given by: I Q is the step-down converter quiescent current. The term tsw is used to estimate the full load step- down converter switching losses. For the condition where the step-down converter is in dropout at 100% duty cycle, the total device dis- sipation reduces to: Since R DS(ON), quiescent current, and switching losses all vary with input voltage, the total losses should be investigated over the complete input voltage range. Given the total losses, the maximum junction tem- perature can be derived from the θ JA for the QFN34-20 package which is 50°C/W. LDO Linear Regulator Input Capacitor A 1µF or larger capacitor is typically recommended for C IN in most applications. A C IN capacitor is not required for basic LDO regulator operation; howev- er, if the AAT2503 is physically located more than three centimeters from an input power source, a C IN capacitor will be needed for stable operation. CIN should be located as closely to the device VIN pin as practically possible. C IN values greater than 1µF will offer superior input line transient response and will assist in maximizing the highest possible power supply ripple rejection. Ceramic, tantalum, or aluminum electrolytic capac- itors may be selected for C IN. There is no specific capacitor ESR requirement for C IN; however, for 150mA LDO regulator output operation, ceramic capacitors are recommended for C IN due to their inherent capability over tantalum capacitors to with- stand input current surges from low impedance sources such as batteries in portable devices. Output Capacitor For proper load voltage regulation and operational stability, a capacitor is required between pins OUTA, OUTB, and GND. The C OUT capacitor connection to the LDO regulator ground pin should be made as direct as practically possible for maximum device performance. The AAT2503 has been specifically designed to function with very low ESR ceramic capacitors. For best performance, ceramic capaci- tors are recommended. Typical output capacitor values for maximum out- put current conditions range from 1µF to 10µF. TJ(MAX) = PTOTAL · ΘJA + TAMB PTOTAL = IO 2 · RDSON(HS) + IQ · VIN PTOTAL IO 2 · (RDSON(HS) · VO + RDSON(LS) · [VIN - VO]) VIN + (tsw · F · IO + IQ) · VIN R6 = 59kΩ R6 = 221kΩ VOUT (V) R2 (kΩ) R2 (kΩ) 0.9* 0 0 1.0 6.65 24.3 1.1 13.3 48.7 1.2 19.6 73.2 1.3 26.1 97.6 1.4 32.4 124 1.5 39.2 147 1.8 59.0 221 1.85 61.9 232 2.0 71.5 274 2.5 105 392 2.8 124 464 3.0 137 511 3.3 158 590 * For the 0.9V output, R6 is open.

Adjustable 3-Channel Regulator 2503.2007.04.1.1 17 Applications utilizing the exceptionally low output noise and optimum power supply ripple rejection characteristics of the AAT2503 should use 2.2µF or greater for C OUT. If desired, COUT may be increased without limit. In low output current applications where output load is less than 10mA, the minimum value for C OUT can be as low as 0.47µF. Capacitor Characteristics Ceramic composition capacitors are highly recom- mended over all other types of capacitors for use with the AAT2503. Ceramic capacitors offer many advantages over their tantalum and aluminum elec- trolytic counterparts. A ceramic capacitor typically has very low ESR, is lower cost, has a smaller PCB footprint, and is non-polarized. Line and load tran- sient response of the LDO regulator is improved by using low ESR ceramic capacitors. Since ceramic capacitors are non-polarized, they are not prone to incorrect connection damage. Equivalent Series Resistance ESR is a very important characteristic to consider when selecting a capacitor. ESR is the internal series resistance associated with a capacitor that includes lead resistance, internal connections, size and area, material composition, and ambient tem- perature. Typically, capacitor ESR is measured in milliohms for ceramic capacitors and can range to more than several ohms for tantalum or aluminum electrolytic capacitors. Ceramic Capacitor Materials Ceramic capacitors less than 0.1µF are typically made from NPO or C0G materials. NPO and C0G materials generally have tight tolerance and are very stable over temperature. Larger capacitor values are usually composed of X7R, X5R, Z5U, or Y5V dielectric materials. These two material types are not recommended for use with LDO regulators since the capacitor tolerance can vary more than ±50% over the operating temperature range of the device. A 2.2µF Y5V capacitor could be reduced to 1µF over temperature; this could cause problems for circuit operation. X7R and X5R dielectrics are much more desirable. The temperature tolerance of X7R dielec- tric is better than ±15%. Capacitor area is another contributor to ESR. Capacitors which are physically large in size will have a lower ESR when compared to a smaller sized capacitor of an equivalent materi- al and capacitance value. These larger devices can improve circuit transient response when compared to an equal value capacitor in a smaller package size. Consult capacitor vendor datasheets carefully when selecting capacitors for LDO regulators. Adjustable Output Resistor Selection The output voltage on the linear regulator is pro- grammed with external resistors: R4 and R7 for LDOA and R5 and R8 for LDOB. Table 3 summa- rizes the resistor values for various output volt- ages with R4 and R5 set to either 59k Ω for good noise immunity or 221kΩfor reduced no load input current. Table 3: LDO Linear Regulators Resistor Values for Various Output Voltages. LDO R7, R8 = 59kΩ R7, R8 = 221kΩ VOUT (V) R4, R5 (kΩ) R4, R5 (kΩ) 0.6* 0 0 0.8 19.6 75 0.9 29.4 113 1.0 39.2 150 1.1 49.9 187 1.2 59.0 221 1.3 68.1 261 1.4 78.7 301 1.5 88.7 332 1.8 118 442 1.85 124 464 2.0 137 523 2.5 187 715 3.3 267 1000 * For the 0.6V output, R7 and R8 are open.

Adjustable 3-Channel Regulator 18 2503.2007.04.1.1 POK Output LDOA of the AAT2503 features an integrated Power OK comparator which can be used as an error flag. The POK open drain output goes low when output voltage is 6% (typ) below its nominal regulation voltage. Additionally, any time LDOA is in shutdown, the POK output is pulled low. Connect a pull-up resistor from POK to OUTA. Enable Function The AAT2503 features an LDO regulator enable/dis- able function. Each LDO has its own dedicated enable pin. These pins (ENA, ENB) are active high and are compatible with CMOS logic. To assure the LDO regulators will switch on, ENA/B must be greater than 1.4V. The LDO regulators will shut down when the voltage on the ENA/B pins falls below 0.6V. In shutdown, the LDO regulators will consume less than 1.0µA of current. If the enable function is not needed in a specific application, it may be tied to V IN to keep the LDO regulator in a continuously on state. Short-Circuit Protection The AAT2503 contains internal short-circuit protec- tion that will trigger when the output load current exceeds the internal threshold limit. Under short- circuit conditions, the output of the LDO regulator will be current limited until the short-circuit condi- tion is removed from the output or LDO regulator package power dissipation exceeds the device thermal limit. Thermal Protection Each of the two LDOs of the AAT2503 has an inter- nal thermal protection circuit which will turn on when the device die temperature exceeds 140°C. The LDO regulator outputs will remain in a shutdown state until the internal die temperature falls back below the ~125°C trip point. The combination and interaction between the short-circuit and thermal protection systems allows the LDO regulators to withstand indefinite short-circuit conditions without sustaining permanent damage. No-Load Stability The LDOs in the AAT2503 are designed to main- tain output voltage regulation and stability under operational no-load conditions. This is an important characteristic for applications where the output cur- rent may drop to zero. Reverse Output-to-Input Voltage Conditions and Protection Under normal operating conditions, a parasitic diode exists between the output and input of the LDO reg- ulator. The input voltage should always remain greater than the output load voltage maintaining a reverse bias on the internal parasitic diode. Conditions where V OUT might exceed VIN should be avoided since this would forward bias the internal parasitic diode and allow excessive current flow into the V OUT pin, possibly damaging the LDO regulator. In applications where there is a possibility of V OUT exceeding VIN for brief amounts of time during nor- mal operation, the use of a larger value CIN capaci- tor is highly recommended. A larger value of CIN with respect to COUT will effect a slower C IN decay rate during shutdown, thus preventing V OUT from exceeding V IN. In applications where there is a greater danger of VOUT exceeding VIN for extended periods of time, it is recommended to place a Schottky diode across V IN to VOUT (connecting the cathode to V IN and anode to V OUT). The Schottky diode forward voltage should be less than 0.45V. Thermal Considerations and High Output Current Applications The LDOs of the AAT2503 are designed to deliver continuous output load currents of 150mA each under normal operation. This is desirable for circuit applications where there might be a brief high in- rush current during a power-on event. The limiting characteristic for the maximum output load current safe operating area is essentially package power dissipation and the internal preset thermal limit of the device. In order to obtain high operating currents, careful device layout and circuit operating conditions need to be taken into account.

Adjustable 3-Channel Regulator 2503.2007.04.1.1 19 The following discussions will assume the LDO regulator is mounted on a printed circuit board uti- lizing the minimum recommended footprint as stat- ed in the layout considerations section of this doc- ument. At any given ambient temperature (T A), the maximum package power dissipation can be deter- mined by the following equation: Constants for the AAT2503 are T J(MAX) (the maxi- mum junction temperature for the device, which is 125°C) and θ JA = 50°C/W (the package thermal resistance). Typically, maximum conditions are cal- culated at the maximum operating temperature of T A = 85°C and under normal ambient conditions where T A = 25°C. Given TA = 85°C, the maximum package power dissipation is 800mW. At TA = 25°C, the max- imum package power dissipation is 2W. The maximum continuous output current for the AAT2503 is a function of the package power dissi- pation and the input-to-output voltage drop across the LDO regulator. To determine the maximum output current for a given output voltage, refer to the following equation. This calculation accounts for the total power dissipation of the LDO regulator, including that caused by ground current. PD(MAX) = TJ(MAX) - TA θJA PD(MAX) = [(VIN - VOUTA)IOUTA + (VIN · IGND)] + [(VIN - VOUTB)IOUTB + (VIN · IGND)] Layout The suggested PCB layout for the AAT2503 is shown in Figures 2 and 3. The following guidelines should be used to help ensure a proper layout. 1. The input capacitors (C4, C7, C8, and C9) should connect as closely as possible to VIN and PGND. 2. The output capacitor (C5, and C6) of the LDOs connect as closely as possible to OUT. C2 and L1 should be connected as closely as possible. The connection of L1 to the LX pin should be as short as possible. Do not make the node small by using a narrow trace. The trace should be kept wide, direct, and short. 3. The feedback trace should be separate from any power trace and connect as closely as pos- sible to the load point. Sensing along a high- current load trace will degrade DC load regula- tion. Feedback resistors should be placed as closely as possible to VOUT to minimize the length of the high impedance feedback trace. If possible, they should also be placed away from the LX (switching node) and inductor to improve noise immunity. 4. The resistance of the trace from the load return to the PGND should be kept to a minimum. This will help to minimize any error in DC regu- lation due to differences in the potential of the internal signal ground and the power ground. 5. Ensure all ground pins are tied to the ground plane. No pins should be left floating. For max- imum power dissipation, it is recommended that the exposed Pad must be soldered to a good conductive PCB ground plane layer to further increase local heat dissipation.

Adjustable 3-Channel Regulator 2503.2007.04.1.1 21 Table 4: Surface Mount Capacitors. Table 5: Suggested Inductors and Suppliers. Manufacturer Part Number Value (µF) Voltage Rating Temp. Co. Case Size Murata GRM219R60J106KE19 10 6.3 X5R 0805 Murata GRM188R60J475KE19 4.7 6.3 X5R 0603 Murata GRM188R61A225KE34 2.2 10 X5R 0603 Murata GRM188R61A105KA61 1.0 10 X5R 0603 Murata GRM185R60J105KE26 1.0 6.3 X5R 0603 Inductance Saturated Rated DCR Size (mm) Manufacturer Part Number (µH) Current (mA) (m Ω) LxWxH Type Sumida CDRH2D14-1R5 1.5 1800 63 3.2x3.2x1.55 Shielded Sumida CDRH2D14-2R2 2.2 1500 94 3.2x3.2x1.55 Shielded Sumida CDRH2D14-3R3 3.3 1200 125 3.2x3.2x1.55 Shielded Coiltronics SD3812-1R5 1.5 1580 78 4.0x4.0x1.2 Shielded Coiltronics SD3812-2R2 2.2 1320 111 4.0x4.0x1.2 Shielded Coiltronics SD3812-3R3 3.3 1100 159 4.0x4.0x1.2 Shielded Taiyo Yuden NR3010-1R5 1.5 1200 80 3.0x3.0x1.0 Shielded Taiyo Yuden NR3010-2R2 2.2 1100 95 3.0x3.0x1.0 Shielded Taiyo Yuden NR3010-3R3 3.3 870 140 3.0x3.0x1.0 Shielded

Adjustable 3-Channel Regulator 22 2503.2007.04.1.1

Ordering Information

Package Channel 1 Channel 2 Channel 3 Marking1 Part Number (Tape and Reel)2 QFN34-20 0.9V 0.6V 0.6V TPXYY AAT2503IZL-BAA-T1 All AnalogicTech products are offered in Pb-free packaging. The term “Pb-free” means 1. XYY = assembly and date code. 2. Sample stock is generally held on part numbers listed in BOLD. Legend Voltage Code Adjustable A(0.6V) 0.9 B 1.2 E 1.5 G 1.8 I 1.9 Y 2.5 N 2.6 O 2.7 P 2.8 Q 2.85 R 2.9 S 3.0 T 3.3 W 4.2 C

All dimensions in millimeters. 4.00 ± 0.05 3.00 ± 0.05 0.075 ± 0.075 0.40 ± 0.10 0.24 ± 0.06 0.50 ± 0.05 0.214 ± 0.0360.025 ± 0.025 0.925 ± 0.125 7.5° ± 7.5° Top View Bottom View Side View Detail "B" Detail "A" Option A: C0.30 (4x) max Chamfered corner Option B: R0.30 (4x) max Round corner Pin 1 indicator (optional) Detail "A" Index Area (D/2 x E/2) Detail "B" AAT2503 Adjustable 3-Channel Regulator 2503.2007.04.1.1 23 Advanced Analogic Technologies, Inc. 830 E. Arques Avenue, Sunnyvale, CA 94085 Phone (408) 737-4600 Fax (408) 737-4611 1. The leadless package family, which includes QFN, TQFN, DFN, TDFN and STDFN, has exposed copper (unplated) at the end of the lead terminals due to the manufacturing process. A solder fillet at the exposed copper edge cannot be guaranteed and is not re quired to ensure a proper bottom solder connection. © Advanced Analogic Technologies, Inc. AnalogicTech cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in an AnalogicTech product. No circuit patent licenses, copyrights, mask work rights, or other intellectual property rights are implied. AnalogicTech reserves the right to make changes to their products or specifications or to discontinue any product or service with- out notice. Except as provided in AnalogicTech’s terms and conditions of sale, AnalogicTech assumes no liability whatsoever, and AnalogicTech disclaims any express or implied war- ranty relating to the sale and/or use of AnalogicTech products including liability or warranties relating to fitness for a particular purpose, merchantability, or infringement of any patent, copyright or other intellectual property right. In order to minimize risks associated with the customer’s applications, adequate design and operating safeguards must be provided by the customer to minimize inherent or procedural hazards. Testing and other quality control techniques are utilized to the extent AnalogicTech deems necessary to support this warranty. Specific testing of all parameters of each device is not necessarily performed. AnalogicTech and the AnalogicTech logo are trademarks of Advanced Analogic Technologies Incorporated. All other brand and product names appearing in this document are registered trademarks or trademarks of their respective holder s.