AAT1106ICB-0.6-T1

DATASHEET SEARCH SITE | WWW.ALLDATASHEET.COM

Document overview

• Manufacturer or author: Provided By ALLDATASHEET.COM(FREE DATASHEET DOWNLOAD SITE)
• PDF pages: 19

Technical content

Features

• V IN Range: 2.5V to 5.5V
• V OUT: Adjustable 0.6V to VIN
• Up to 600mA Output Current
• Up to 96% Efficiency
• 1.5MHz Switching Frequency
• 100% Duty Cycle Dropout Operation
• Adaptive Slope Compensated Current Mode Control for Excellent Line and Load Transient Response
• <1 μA Shutdown Current
• Short-Circuit and Thermal Fault Protection
• TSOT23-5 Package
• -40°C to +85°C Temperature Range

Applications

• Cellular Phones, Smartphones
• Digital Still Cameras
• Digital Video Cameras
• Microprocessor and DSP Core Supplies
• MP3 and Portable Media Players
• PDAs
• Wireless and DSL Modems Typical Application IN EN LX FB GND VIN 2.5V to 5.5V 4.7μF 10μF 316K 634K 22pF 2.2μH VOUT 1.8V AAT1106

Skyworks Solutions, Inc. • Phone [781] 376-3000 • Fax [781] 376-3100 • sales@skyworksinc.com • www.skyworksinc.com 201970B • Skyworks Proprietary Information • Products and Product Information are Subject to Change Without Notice. • March 15, 2013 Pin Descriptions Pin # Symbol Function 1E N Enable pin. Active high. In shutdown, all functions are disabled drawing <1μA supply current. Do not leave EN fl oating. 2 GND Ground pin. 3L X Switching node. Connect the output inductor to this pin. Connects to the drains of the internal P- and N-chan- nel MOSFET switches. 4 IN Supply input pin. Must be closely decoupled to GND with a 2.2 μF or larger ceramic capacitor. 5F B Feedback input pin. Connect FB to the center point of the external resistor divider. The feedback threshold voltage is 0.6V. Pin Configuration TSOT23-5 (Top View) GND FB INLX EN 1 3 4

Skyworks Solutions, Inc. • Phone [781] 376-3000 • Fax [781] 376-3100 • sales@skyworksinc.com • www.skyworksinc.com 201970B • Skyworks Proprietary Information • Products and Product Information are Subject to Change Without Notice. • March 15, 2013 Absolute Maximum Ratings Symbol Description Value Units VIN Input Supply Voltage -0.3 to 6.0 VVEN, VFB EN, FB Voltages -0.3 to VIN + 0.3VLX LX Voltages TJ Operating Temperature Range -40 to +85 °CTS Storage Temperature Range -65 to +150 TLEAD Lead Temperature (soldering, 10s) 300 Recommended Operating Conditions Symbol Description Value Units JA Thermal Resistance (TSOT23-5) 150 °C/W PD Maximum Power Dissipation at TA = 25°C 667 mW 1. Absolute Maximum Ratings are those values beyond which the life of a device may be impaired. 2. TJ is calculated from the ambient temperature TA and power dissipation PD according to the following formula: T J = TA + PD · JA. 3. Thermal resistance is specified with approximately 1 square inch of 1 oz copper.

Skyworks Solutions, Inc. • Phone [781] 376-3000 • Fax [781] 376-3100 • sales@skyworksinc.com • www.skyworksinc.com 201970B • Skyworks Proprietary Information • Products and Product Information are Subject to Change Without Notice. • March 15, 2013

Electrical Characteristics

VIN = VEN = 3.6V, TA = 25°C, unless otherwise noted. Symbol Description Conditions Min Typ Max Units Step-Down Converter VIN Input Voltage Range 2.5 5.5 V IQ Input DC Supply Current Active Mode, VFB = 0.5V 270 400 μAShutdown Mode, VFB = 0V, VIN = 4.2V 0.08 1.0 VFB Regulated Feedback Voltage TA = 25°C 0.5880 0.6000 0.6120 VTA = 0°C  TA  +85°C 0.5865 0.6135 TA = -40°C  TA  +85°C 0.5850 0.6150 IFB FB Input Bias Current V FB = 0.65V -30 30 nA VOUT/ VOUT/VIN Output Voltage Line Regulation V IN = 2.5V to 5.5V, IOUT = 10mA 0.11 0.40 %/V VOUT/ VOUT/IOUT Output Voltage Load Regulation I OUT = 10mA to 600mA 0.0015 %/mA ILIM Maximum Output Current V IN = 3.0V 600 mA FOSC Oscillator Frequency V FB = 0.6V 1.2 1.5 1.8 MHz TS Startup Time From Enable to Output Regulation 100 μs RDS(ON) P-Channel MOSFET I LX = 300mA 0.30 0.50 N-Channel MOSFET I LX = 300mA 0.20 0.45 Peak Inductor Current VIN = 3V, VFB = 0.5V, Duty Cycle <35% 1.20 A Output Over-Voltage Lockout VOVL = VOVL - VFB 60 mV VEN(L) Enable Threshold Low 0.4 VVEN(H) Enable Threshold High 1.4 IEN Input Low Current -1.0 1.0 μA TSD Over-Temperature Shutdown Threshold 150 °CTHYS Over-Temperature Shutdown Hysteresis 15 1. 100% production test at +25°C. Specifications over the temperature range are guaranteed by design and characterization.

Skyworks Solutions, Inc. • Phone [781] 376-3000 • Fax [781] 376-3100 • sales@skyworksinc.com • www.skyworksinc.com 201970B • Skyworks Proprietary Information • Products and Product Information are Subject to Change Without Notice. • March 15, 2013 Typical Characteristics Efficiency vs. Output Current (VOUT = 2.5V; L = 2.2µH; TA = 25°°C) Output Current (mA) Efficiency (%) 0.1 1 10 100 1000 100 VIN = 3.6V VIN = 4.2V VIN = 2.7V Efficiency vs. Output Current (VIN = 3.6V; VOUT = 2.5V; TA = 25°°C) Output Current (mA) Efficiency (%) 0.1 1 10 100 1000 100 L = 10µH L = 4.7µH L = 2.2µH L = 1.4µH Efficiency vs. Output Current (VOUT = 1.8V; L = 2.2µH; TA = 25°°C) Output Current (mA) Efficiency (%) 0.1 1 10 100 1000 100 VIN = 3.6V VIN = 4.2V VIN = 2.7V Efficiency vs. Output Current (VIN = 3.6V; VOUT = 1.8V; TA = 25°°C) Output Current (mA) Efficiency (%) 0.1 1 10 100 1000 100 L = 10µH L = 4.7µH L = 2.2µH L = 1.4µH Efficiency vs. Output Current (VOUT = 1.5V; L = 2.2µH; TA = 25°°C) Output Current (mA) Efficiency (%) 0.1 1 10 100 1000 100 VIN = 2.7V VIN = 3.6V VIN = 4.2V Efficiency vs. Output Current (VOUT = 1.2V; L = 2.2µH; TA = 25°°C) Output Current (mA) Efficiency (%) 0.1 1 10 100 1000 100 VIN = 2.7V VIN = 3.6V VIN = 4.2V

Skyworks Solutions, Inc. • Phone [781] 376-3000 • Fax [781] 376-3100 • sales@skyworksinc.com • www.skyworksinc.com 201970B • Skyworks Proprietary Information • Products and Product Information are Subject to Change Without Notice. • March 15, 2013 Typical Characteristics Efficiency vs. Input Voltage (VIN = 3.6V; L = 2.2µH; VOUT = 1.8V) Input Voltage (V) Efficiency (%) 2 3 4 56 100 ILOAD = 10mA ILOAD = 100mA ILOAD = 500mA Output Voltage vs. Output Current (VIN = 3.6V; VOUT = 1.8V; L = 2.2µH) Load Current (mA) Output Voltage (V) 0 200 400 600 800 1000 1200 1.64 1.66 1.68 1.7 1.72 1.74 1.76 1.78 1.8 1.82 1.84 Frequency vs. Input Voltage (VOUT = 1.8V; ILOAD = 150mA; L = 2.2µH) Input Voltage (V) Frequency (MHz) 1.470 1.480 1.490 1.500 1.510 1.520 1.530 1.540 1.550 1.560 RDS(ON) vs. Input Voltage Input Voltage (V) RDS(ON) (ΩΩ) 0.150 0.200 0.250 0.300 0.350 0.400 2 2.5 3 3.5 4 4.5 5 5.5 6 P-Channel MOSFET N-Channel MOSFET Feedback Voltage vs. Temperature (VIN = 3.6V) Temperature (°°C) Feedback Voltage (V) 0.597 0.598 0.599 0.600 0.601 0.602 0.603 0.604 -40 -20 0 20 40 60 80 100 RDS(ON) vs. Temperature (VIN = 3.6V) Temperature (°C) RDS(ON) (Ω) -45 -15 15 45 60 90 0.15 0.18 0.21 0.24 0.27 0.30 0.33 0.36 75-30 0 30 N-Channel P-Channel

Skyworks Solutions, Inc. • Phone [781] 376-3000 • Fax [781] 376-3100 • sales@skyworksinc.com • www.skyworksinc.com 201970B • Skyworks Proprietary Information • Products and Product Information are Subject to Change Without Notice. • March 15, 2013 Typical Characteristics Frequency vs. Temperature Temperature (°C) OSC Frequency (MHz) -50 -25 0 25 50 150 1.10 1.15 1.20 1.25 1.30 1.35 1.40 1.45 1.50 1.55 1.60 100 Input Supply Current vs. Temperature Temperature (°C) Input Supply Current (µA) -50 -30 -10 10 30 50 70 90 200 220 240 260 280 300 320 Load Transient Response (PWM Mode Only; ILOAD = 100mA to 400mA; L = 2.2µH; CIN = 10µF; COUT = 10µF; VIN = 3.6V; VOUT = 1.8V) VSW 2V/div VOUT 100mV/div ILOAD 500mA/div 40µs/div Load Transient Response (Light Load Mode to PWM Mode; ILOAD = 28mA to 400mA; L = 2.2µH; CIN = 10µF; COUT = 10µF; VIN = 3.6V; VOUT = 1.8V) VSW 2V/div VOUT 200mV/div ILOAD 500mA/div PWM Light Load 4µs/div

Skyworks Solutions, Inc. • Phone [781] 376-3000 • Fax [781] 376-3100 • sales@skyworksinc.com • www.skyworksinc.com 201970B • Skyworks Proprietary Information • Products and Product Information are Subject to Change Without Notice. • March 15, 2013 Typical Characteristics Startup Waveform (VOUT = 1.8V; CFF = 0pF; RLOAD = 3ΩΩ; CIN = 4.7µF; COUT = 10µF; L = 2.2µH) Time (20µs/div) Output Voltage (top) (V) Input Current (bottom) (A) -0.25 0.00 0.25 0.50 0.75 1.00 1.25 1.50 1.75 VOUT = 1.8V IIN VEN = 3.0V Startup Waveform (VOUT = 1.8V; CFF = 22pF; RLOAD =3 ΩΩ; CIN = 4.7µF; COUT = 10µF; L = 2.2µH) Time (20µs/div) Output Voltage (mid) (V) Input Current (bottom) (A) -0.25 0.00 0.25 0.50 0.75 1.00 1.25 1.50 1.75 VEN = 3.0V VOUT = 1.8V IIN Startup Waveform (VOUT = 1.8V; CFF = 100pF; RLOAD = 3ΩΩ; CIN = 4.7µF; COUT = 10µF; L = 2.2µH) Time (20µs/div) Output Voltage (top) (V) Input Current (bottom) (A) -0.25 0.00 0.25 0.50 0.75 1.00 1.25 1.50 1.75 VEN = 3.0V VOUT = 1.8V IIN

Skyworks Solutions, Inc. • Phone [781] 376-3000 • Fax [781] 376-3100 • sales@skyworksinc.com • www.skyworksinc.com 201970B • Skyworks Proprietary Information • Products and Product Information are Subject to Change Without Notice. • March 15, 2013 Functional Description The AAT1106 is a high performance 600mA, 1.5MHz fixed frequency monolithic switch-mode step-down converter which uses a current mode architecture with an adaptive slope compensation scheme. It minimizes external com- ponent size and optimizes efficiency over the complete load range. The adaptive slope compensation allows the device to remain stable over a wider range of inductor values so that smaller values (1μH to 4.7μH) with associ- ated lower DCR can be used to achieve higher efficiency. Apart from the small bypass input capacitor, only a small L-C filter is required at the output. The AAT1106 can be programmed with external feedback to any voltage, ranging from 0.6V to the input voltage. It uses internal MOSFETs to achieve high efficiency and can generate very low output voltage by using an internal reference of 0.6V. At dropout, the converter duty cycle increases to 100% and the output voltage tracks the input voltage minus the low R DS(ON) drop of the P-channel high-side MOSFET. The input voltage range is 2.5V to 5.5V. The converter efficiency has been optimized for all load condi- tions, ranging from no load to 600mA at V IN = 3V. The internal error amplifier and compensation provides excel- lent transient response, load, and line regulation. Current Mode PWM Control Slope compensated current mode PWM control provides stable switching and cycle-by-cycle current limit for excellent load and line response and protection of the internal main switch (P-channel MOSFET) and synchro- nous rectifier (N-channel MOSFET). During normal operation, the internal P-channel MOSFET is turned on for a specified time to ramp the inductor current at each rising edge of the internal oscillator, and is switched off when the feedback voltage is above the 0.6V reference voltage. The current comparator, I COMP, limits the peak inductor current. When the main switch is off, the syn- chronous rectifier turns on immediately and stays on until either the inductor current starts to reverse, as indicated by the current reversal comparator, I ZERO, or the beginning of the next clock cycle. Functional Block Diagram PWM LOGIC NON-OVE RLAP CONTROL DRV OSC SLOPE COMP BLANKING EA COMP0.6V LX COUT FB VOUT 0.6V VIN REFEN VIN VIN 2.7 - 5.5V IZERO COMP ISENSE COMP QS RQ R RS LATCH SHUTDOWN1 0.65V OVDET GND

Skyworks Solutions, Inc. • Phone [781] 376-3000 • Fax [781] 376-3100 • sales@skyworksinc.com • www.skyworksinc.com 201970B • Skyworks Proprietary Information • Products and Product Information are Subject to Change Without Notice. • March 15, 2013 Control Loop The AAT1106 is a peak current mode step-down con- verter. The current through the P-channel MOSFET (high side) is sensed for current loop control, as well as short circuit and overload protection. An adaptive slope com- pensation signal is added to the sensed current to main- tain stability for duty cycles greater than 50%. The peak current mode loop appears as a voltage-programmed current source in parallel with the output capacitor. The output of the voltage error amplifier programs the cur- rent mode loop for the necessary peak switch current to force a constant output voltage for all load and line con- ditions. Internal loop compensation terminates the transconductance voltage error amplifier output. For the adjustable output, the error amplifier reference is fixed at 0.6V. Enable The enable pin is active high. When pulled low, the enable input forces the AAT1106 into a low-power, non- switching state. The total input current during shutdown is less than 1μA. Current Limit and Over-Temperature Protection For overload conditions, the peak input current is limit- ed. To minimize power dissipation and stresses under current limit and short-circuit conditions, switching is terminated after entering current limit for a series of pulses. Switching is terminated for seven consecutive clock cycles after a current limit has been sensed for a series of four consecutive clock cycles. Thermal protec- tion completely disables switching when internal dissipa- tion becomes excessive. The junction over-temperature threshold is 150°C with 15°C of hysteresis. Once an over-temperature or over-current fault conditions is removed, the output voltage automatically recovers. Dropout Operation When the input voltage decreases toward the value of the output voltage, the AAT1106 allows the main switch to remain on for more than one switching cycle and increases the duty cycle until it reaches 100%. The duty cycle D of a step-down converter is defined as: D = TON · FOSC · 100% ≈ VOUT VIN

• 100% Where TON is the main switch on time and F OSC is the oscillator frequency (1.5MHz). The output voltage then is the input voltage minus the voltage drop across the main switch and the inductor. At low input supply voltage, the R DS(ON) of the P-channel MOSFET increases and the efficiency of the converter decreases. Caution must be exercised to ensure the heat dissipated does not exceed the maximum junction tem- perature of the IC. Maximum Load Current The AAT1106 will operate with an input supply voltage as low as 2.5V; however, the maximum load current decreases at lower input due to the large IR drop on the main switch and synchronous rectifier. The slope com- pensation signal reduces the peak inductor current as a function of the duty cycle to prevent sub-harmonic oscil- lations at duty cycles greater than 50%. Conversely, the current limit increases as the duty cycle decreases.

Skyworks Solutions, Inc. • Phone [781] 376-3000 • Fax [781] 376-3100 • sales@skyworksinc.com • www.skyworksinc.com 201970B • Skyworks Proprietary Information • Products and Product Information are Subject to Change Without Notice. • March 15, 2013 Part L ( μH) Max DCR (m) Rated DC Current (A) Size WxLxH (mm) Sumida CR43 1.4 56.2 2.52 3.3 86.2 1.44 4.7 108.7 1.15 Sumida CDRH4D18 1.0 4.5 1,72 3.3 110 1.04 4.7 162 0.84 Toko D312C 1.5 120 1.29 3.3 180 0.98 4.7 240 0.79 Table 2: Typical Surface Mount Inductors. For output voltages above 2.0V, when light-load effi- ciency is important, the minimum recommended induc- tor size is 2.2 μH. For optimum voltage-positioning load transients, choose an inductor with DC series resistance in the 50m  to 150m  range. For higher efficiency at heavy loads (above 200mA), or minimal load regulation (with some transient overshoot), the resistance should be kept below 100m . The DC current rating of the inductor should be at least equal to the maximum load current plus half the ripple current to prevent core satu- ration (600mA + 105mA). Table 2 lists some typical surface mount inductors that meet target applications for the AAT1106. Manufacturer's specifications list both the inductor DC current rating, which is a thermal limitation, and the peak current rating, which is determined by the satura- tion characteristics. The inductor should not show any appreciable saturation under normal load conditions. Some inductors may meet the peak and average current ratings yet result in excessive losses due to a high DCR. Always consider the losses associated with the DCR and its effect on the total converter efficiency when selecting an inductor. For example, the 2.2μH CR43 series induc- tor selected from Sumida has a 71.2m Ω DCR and a 1.75ADC current rating. At full load, the inductor DC loss is 25mW which gives a 2.8% loss in efficiency for a 600mA, 1.5V output. Slope Compensation The AAT1106 step-down converter uses peak current mode control with a unique adaptive slope compensation scheme to maintain stability with lower value inductors for duty cycles greater than 50%. Using lower value inductors provides better overall efficiency and also makes it easier to standardize on one inductor for differ- ent required output voltage levels. In order to do this and keep the step-down converter stable when the duty cycle is greater than 50%, the AAT1106 separates the slope compensation into 2 phases. The required slope compensation is automatically detected by an internal circuit using the feedback voltage V FB before the error amp comparison to VREF. Error AmpVREF VFB When below 50% duty cycle, the slope compensation is 0.284A/μs; but when above 50% duty cycle, the slope compensation is set to 1.136A/ μs. The output inductor value must be selected so the inductor current down slope meets the internal slope compensation requirements. Below 50% duty cycle, the slope compensation require- ment is: 1.25 2 · Lm = = 0.284A/µs Therefore: 0.625 mL = = 2.2µH Above 50% duty cycle, 2 · Lm = = 1.136A/µs Therefore: 2.5 mL = = 2.2µH With these adaptive settings, a 2.2 μH inductor can be used for all output voltages from 0.6V to 5V.

Skyworks Solutions, Inc. • Phone [781] 376-3000 • Fax [781] 376-3100 • sales@skyworksinc.com • www.skyworksinc.com 201970B • Skyworks Proprietary Information • Products and Product Information are Subject to Change Without Notice. • March 15, 2013 Input Capacitor Selection The input capacitor reduces the surge current drawn from the input and switching noise from the device. The input capacitor impedance at the switching frequency shall be less than the input source impedance to prevent high frequency switching current passing to the input. A low ESR input capacitor sized for maximum RMS current must be used. Ceramic capacitors with X5R or X7R dielectrics are highly recommended because of their low ESR and small temperature coefficients. A 4.7μF ceram- ic capacitor is sufficient for most applications. To estimate the required input capacitor size, determine the acceptable input ripple level (V PP) and solve for C. The calculated value varies with input voltage and is a maximum when V IN is double the output voltage. VO VIN CIN = VO VIN VPP IO VO VIN VO VIN CIN(MIN) = 1 VPP IO Always examine the ceramic capacitor DC voltage coeffi- cient characteristics when selecting the proper value. For example, the capacitance of a 10 μF, 6.3V, X5R ceramic capacitor with 5.0V DC applied is actually about 6 μF. The maximum input capacitor RMS current is: VO VIN VO VIN The input capacitor RMS ripple current varies with the input and output voltage and will always be less than or equal to half of the total DC load current: VO VIN VO VIN for VIN = 2 · VO. IO RMS(MAX)I 2= The term VO VIN VO VIN appears in both the input voltage ripple and input capacitor RMS current equations and is at maximum when V O is twice V IN. This is why the input voltage ripple and the input capacitor RMS current ripple are a maximum at 50% duty cycle. The input capacitor provides a low impedance loop for the edges of pulsed current drawn by the AAT1106. Low ESR/ESL X7R and X5R ceramic capacitors are ideal for this function. To minimize stray inductance, the capacitor should be placed as closely as possible to the IC. This keeps the high frequency content of the input current localized, minimizing EMI and input voltage ripple. The proper placement of the input capacitor (C1) can be seen in the evaluation board layout in Figure 2. A laboratory test set- up typically consists of two long wires running from the bench power supply to the evaluation board input voltage pins. The inductance of these wires, along with the low- ESR ceramic input capacitor, can create a high Q network that may affect converter performance. This problem often becomes apparent in the form of excessive ringing in the output voltage during load transients. Errors in the loop phase and gain measurements can also result. Since the inductance of a short PCB trace feeding the input voltage is significantly lower than the power leads from the bench power supply, most applications do not exhib- it this problem. In applications where the input power source lead inductance cannot be reduced to a level that does not affect the converter performance, a high ESR tantalum or aluminum electrolytic should be placed in parallel with the low ESR, ESL bypass ceramic. This dampens the high Q network and stabilizes the system. Output Capacitor Selection The output capacitor is required to keep the output volt- age ripple small and to ensure regulation loop stability. The output capacitor must have low impedance at the switching frequency. Ceramic capacitors with X5R or X7R dielectrics are recommended due to their low ESR and high ripple current. The output ripple V OUT is deter- mined by: VOUT · (VIN - VOUT) VIN · fOSC · L 8 · fOSC · C3 The output capacitor limits the output ripple and pro- vides holdup during large load transitions. A 4.7 μF to

Skyworks Solutions, Inc. • Phone [781] 376-3000 • Fax [781] 376-3100 • sales@skyworksinc.com • www.skyworksinc.com 201970B • Skyworks Proprietary Information • Products and Product Information are Subject to Change Without Notice. • March 15, 2013 10μF X5R or X7R ceramic capacitor typically provides sufficient bulk capacitance to stabilize the output during large load transitions and has the ESR and ESL charac- teristics necessary for low output ripple. The output volt- age droop due to a load transient is dominated by the capacitance of the ceramic output capacitor. During a step increase in load current, the ceramic output capac- itor alone supplies the load current until the loop responds. Within two or three switching cycles, the loop responds and the inductor current increases to match the load current demand. The relationship of the output voltage droop during the three switching cycles to the output capacitance can be estimated by: COUT = 3 · ΔILOAD VDROOP · FS Once the average inductor current increases to the DC load level, the output voltage recovers. The above equa- tion establishes a limit on the minimum value for the out- put capacitor with respect to load transients. The internal voltage loop compensation also limits the minimum output capacitor value to 4.7 μF. This is due to its effect on the loop crossover frequency (bandwidth), phase margin, and gain margin. Increased output capacitance will reduce the crossover frequency with greater phase margin. The maximum output capacitor RMS ripple current is given by: VOUT · (VIN(MAX) - VOUT) RMS(MAX)I L · F · VIN(MAX) Dissipation due to the RMS current in the ceramic output capacitor ESR is typically minimal, resulting in less than a few degrees rise in hot-spot temperature. Thermal Calculations There are three types of losses associated with the AAT1106 step-down converter: switching losses, conduc- tion losses, and quiescent current losses. Conduction losses are associated with the R DS(ON) characteristics of the power output switching devices. Switching losses are dominated by the gate charge of the power output switch- ing devices. At full load, assuming continuous conduction mode (CCM), a simplified form of the losses is given by: PTOTAL IO 2 · (RDSON(HS) · VO + RDSON(LS) · [VIN - VO]) VIN + (tsw · F · IO + IQ) · VIN IQ is the step-down converter quiescent current. The term tsw is used to estimate the full load step-down con- verter switching losses. For the condition where the step-down converter is in dropout at 100% duty cycle, the total device dissipation reduces to: PTOTAL = IO 2 · RDSON(HS) + IQ · VIN Since RDS(ON), quiescent current, and switching losses all vary with input voltage, the total losses should be inves- tigated over the complete input voltage range. Given the total losses, the maximum junction temperature can be derived from the  JA for the TSOT23-5 package which is 150°C/W. TJ(MAX) = PTOTAL · ΘJA + TA Layout Guidance When laying out the PC board, the following steps should be taken to ensure proper operation of the AAT1106. These items are also illustrated graphically in Figure 3. The power traces (GND, LX, IN) should be kept short, direct, and wide to allow large current flow. Place suf- ficient multiple-layer pads when needed to change the trace layer. 2. The input capacitor (C1) should connect as closely as possible to IN (Pin 4) and GND (Pin 2). 3. The output capacitor C3 and L1 should be connected as closely as possible. The connection of L1 to the LX pin should be as short as possible and there should not be any signal lines under the inductor. 4. The feedback FB trace (Pin 5) should be separate from any power trace and connect as closely as pos- sible to the load point. Sensing along a high-current load trace will degrade DC load regulation. The external feedback resistors should be placed as close as possible to the FB pin (Pin 5) to minimize the length of the high impedance feedback trace. 5. The resistance of the trace from the load return to the GND (Pin 2) should be kept to a minimum. This will help to minimize any error in DC regulation due to differences in the potential of the internal signal ground and the power ground.

Skyworks Solutions, Inc. • Phone [781] 376-3000 • Fax [781] 376-3100 • sales@skyworksinc.com • www.skyworksinc.com 201970B • Skyworks Proprietary Information • Products and Product Information are Subject to Change Without Notice. • March 15, 2013 a: Top Layer b: Internal GND Plane c: Bottom Layer d: Middle Layer Figure 2: AAT1106 Four-Layer Layout Example with Internal GND Plane. Evaluation Board Description The AAT1106 evaluation board contains a fully tested 600mA, 1.5MHz Step-Down DC/DC Regulator. The circuit has an input voltage range of 2.5V to 5.5V and four pre- The AAT1106 comes in a small 5-pin TSOT23 package and the board has been optimized to fit small form factor designs. An optional TVS (SM6T6V8A) is connected between VIN and GND so that the evaluation board can be used in a hot-plug application. These features, plus the nominal operating frequency of 1.5MHz allowing the use of low profile surface mount components, make the AAT1106 evaluation board an ideal circuit for use in battery-powered, hand-held applications. A schematic of the complete circuit is shown in Figure 3. The evaluation board layer details are provided in Figures 4, 5, 6 and 7. Table 3 provides the component list for the AAT1106 evaluation board.

Skyworks Solutions, Inc. • Phone [781] 376-3000 • Fax [781] 376-3100 • sales@skyworksinc.com • www.skyworksinc.com 201970B • Skyworks Proprietary Information • Products and Product Information are Subject to Change Without Notice. • March 15, 2013 EN1 GND 2 AAT1106 JP1 4.7µH 2.2µH R2A 316k 316k 10µH VIN VOUT LX IN4 FB/VOUT5 LX 3 C2 22pF 1 2 JP2 R2B 470k R2C 634k R2D 1M 2.5V ~ 5.5V Figure 3: AAT1106 Evaluation Board Schematic. Component Part# Description Manufacturer U1 AAT1106 1.5 MHz, 600mA Synchronous Step-Down Converter Skyworks L1 SF32-2R2M-R INDUCTOR 2.2 μH 1.8A SMD Fenfa C1 GRM42-6X7R475K16PT CAP CERAMIC 4.7 μF16V X7R 10% 1206 MURATA C2 C1005COG1H220JT000P CAP CERAMIC 22pF 50V C0G 5% 0402 TDK C3 GRM31BR71C106KA01L CAP CERAMIC 10 μF 16V X7R 10% 1206 MURATA R1, R2A Chip Resistor RES 316k Ω 1/16W 1% 0402 SMD R2B Chip Resistor (optional) RES 470k Ω 1/16W 1% 0402 SMD R2C Chip Resistor (optional) RES 634k Ω 1/16W 1% 0402 SMD R2D Chip Resistor (optional) RES 1M Ω 1/16W 1% 0402 SMD No Designator SM6T6V8A (optional) 6.8V TVS ST Table 3: AAT1106 Evaluation Board Component Listing.

Skyworks Solutions, Inc. • Phone [781] 376-3000 • Fax [781] 376-3100 • sales@skyworksinc.com • www.skyworksinc.com 201970B • Skyworks Proprietary Information • Products and Product Information are Subject to Change Without Notice. • March 15, 2013

Ordering Information

Output Voltage Package Marking 1 Part Number (Tape & Reel)2 Adj. 0.6 to VIN TSOT23-5 VVXYY AAT1106ICB-0.6-T1 Skyworks Green™ products are compliant with all applicable legislation and are halogen-free. For additional information, refer to Skyworks Definition of Green™ , document number SQ04-0074. Package Information3 TSOT23-5 0.450 ±± 0.150 0.950 BSC

1.600 BSC

0.450 ±± 0.150

0.127 BSC

Detail "A"

2.800 BSC

1.900 BSC

0° ++10° -0° Top View End View Detail "A"Side View 0.950 ±± 0.150 0.050 ±± 0.050

2.900 BSC

All dimensions in millimeters. 1. XYY = assembly and date code. 2. Sample stock is generally held on part numbers listed in BOLD. 3. Package outline exclusive of mold flash and metal burr.

Skyworks Solutions, Inc. • Phone [781] 376-3000 • Fax [781] 376-3100 • sales@skyworksinc.com • www.skyworksinc.com 201970B • Skyworks Proprietary Information • Products and Product Information are Subject to Change Without Notice. • March 15, 2013 Copyright © 2012, 2013 Skyworks Solutions, Inc. All Rights Reserved. Information in this document is provided in connection with Skyworks Solutions, Inc. (“Skyworks”) products or services. These materials, including the information contained herein, are provided by Skyworks as a service to its customers and may be used for informational purposes only by the customer. Skyworks assumes no responsibility fo r errors or omissions in these materials or the information contained herein. Sky- works may change its documentation, products, services, specifi cations or product descriptions at any time, without notice. Skyworks makes no commitment to update the materials or information and shall have no responsibility whatsoever for confl icts, incompatibilities, or other diffi culties arising from any future changes. No license, whether express, implied, by estoppel or otherwise, is granted to any intellectual property rights by this document. Skyworks assumes no liability for any materials, products or information provided here- under, including the sale, distribution, reproduction or use of Skyworks products, information or materials, except as may be provided in Skyworks Terms and Conditions of Sale. THE MATERIALS, PRODUCTS AND INFORMATION ARE PROVIDED “AS IS” WITHOUT WARRANTY OF ANY KIND, WHETHER EXPRESS, IMPLIED, STATUTORY, OR OTHERWISE, INCLUDING FITNESS FOR A PARTICULAR PURPOSE OR USE, MERCHANTABILITY, PERFORMANCE, QUALITY OR NON-INFRINGEMENT OF ANY INTELLECTUAL PROPERTY RIGHT; ALL SUCH WARRANTIES ARE HEREBY EXPRESSLY DISCLAIMED. SKYWORKS DOES NOT WARRANT THE ACCURACY OR COMPLETENESS OF THE INFORMATION, TEXT, GRAPHICS OR OTHER ITEMS CONTAINED WITHIN THESE MATERIALS. SKYWORKS SHALL NOT BE LIABLE FOR ANY DAMAGES, IN- CLUDING BUT NOT LIMITED TO ANY SPECIAL, INDIRECT, INCIDENTAL, STATUTORY, OR CONSEQUENTIAL DAMAGES, INCLUDING WITHOUT LIMITATION, LOST REVENUES OR LOST PROFITS THAT MAY RESULT FROM THE USE OF THE MATERIALS OR INFORMATION, WHETHER OR NOT THE RECIPIENT OF MATERIALS HAS BEEN ADVISED OF THE POSSIBILITY OF SUCH DAMAGE. Skyworks products are not intended for use in medical, lifesaving or life-sustaining applications, or other equipment in which the failure of the Skyworks products could lead to personal injury, death, physical or en- vironmental damage. Skyworks customers using or selling Skyworks products for use in such applications do so at their own risk and agree to fully indemnify Skyworks for any damages resulting from such improper use or sale. Customers are responsible for their products and applications using Skyworks products, which may deviate from published specifi cations as a result of design defects, errors, or operation of products outside of pub- lished parameters or design specifi cations. Customers should include design and operating safeguards to minimize these and other risks. Skyworks assumes no liability for applications assistance, customer product design, or damage to any equipment resulting from the use of Skyworks products outside of stated published specifi cations or parameters. Skyworks, the Skyworks symbol, and “Breakthrough Simplicity” are trademarks or registered trademarks of Skyworks Solutions, Inc., in the United States and other countries. Third-party brands and names are for identifi cation purposes only, and are the property of their respective owners. Additional information, including relevant terms and conditions, posted at www.skyworksinc.com, are incorporated by reference.