1054I

LT1054IS8PBF LINER | Alldatasheet

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Technical content

Switched-Capacitor Voltage Converter with Regulator The L T®1054 is a monolithic, bipolar , switched-capacitor voltage converter and regulator . The L T1054 provides higher output current than previously available converters with significantly lower voltage losses. An adaptive switch driver scheme optimizes efficiency over a wide range of output currents. Total voltage loss at 100mA output current is typically 1.1V . This holds true over the full supply voltage range of 3.5V to 15V . Quiescent current is typically 2.5mA. The L T1054 also provides regulation, a feature not previ- ously available in switched-capacitor voltage converters. By adding an external resistive divider a regulated output can be obtained. This output will be regulated against changes in both input voltage and output current. The L T1054 can also be shut down by grounding the feedback pin. Supply current in shutdown is less than 100µA. The internal oscillator of the L T1054 runs at a nominal frequency of 25kHz. The oscillator pin can be used to ad- just the switching frequency or to externally synchronize the L T1054. The L T1054 is pin compatible with previous converters such the L TC1044/ICL7660. L T1054/L T1054 Voltage Loss

APPLICATIONS

■ Output Current: 100mA (LT1054) 125mA (LT1054L) ■ Reference and Error Amplifier for Regulation ■ Low Loss: 1.1V at 100mA ■ Operating Range: 3.5V to 15V (LT1054) 3.5V to 7V (LT1054L) ■ External Shutdown ■ External Oscillator Synchronization ■ Can Be Paralleled ■ Pin Compatible with the LTC®1044/ICL7660 ■ Available in SW16 and SO-8 Packages ■ Voltage Inverter ■ Voltage Regulator ■ Negative Voltage Doubler ■ Positive Voltage Doubler L, L T , L TC, L TM, Burst Mode, Linear Technology and the Linear logo are registered trademarks and ThinSOT is a trademark of Linear Technology Corporation. All other trademarks are the property of their respective owners. REFERENCE OSC DRIVE DRIVE DRIVE DRIVE OSC CAP– GND CAP+ FEEDBACK/ SHUTDOWN R R *EXTERNAL CAPACITORS 2.5V –VOUT LT1054 • BD Q Q VREF CIN* VIN COUT* OUTPUT CURRENT (mA) VOLTAGE LOSS (V)

1054 TA01•

TJ = 125°C TJ = 25°C TJ = –55°C LT1054 LT1054L 3.5V ≤ VIN ≤ 15V (LT1054) 3.5V ≤ VIN ≤ 7V (LT1054L) CIN = COUT = 100µF INDICATES GUARANTEED TEST POINT

Supply Voltage (Note 2) Input Voltage Operating Junction Temperature Range (Note 1) TOP VIEW FB/SHDN CAP+ GND CAP– OSC V REF VOUT N8 PACKAGE 8-LEAD PLASTIC DIP J8 PACKAGE 8-LEAD CERAMIC DIP TJMAX = 125°C, θJA = 130°C/W TOP VIEW OSC VREF VOUT FB/SHDN CAP+ GND CAP– S8 PACKAGE 8-LEAD PLASTIC SO TJMAX = 125°C, θJA = 120°C/W SEE REGULATION AND CAPACITOR SELECTION SECTIONS IN THE APPLICATIONS INFORMATION FOR IMPORTANT INFORMATION ON THE S8 DEVICE TOP VIEW SW PACKAGE 16-LEAD PLASTIC SO NC NC FB/SHDN CAP GND CAP– NC NC NC NC V OSC V REF VOUT NC NC TJMAX = 125°C, θJA = 150°C/W PIN CONFIGURATION ORDER INFORMATION LEAD FREE FINISH TAPE AND REEL PART MARKING PACKAGE DESCRIPTION TEMPERATURE RANGE L T1054CN8#PBF L T1054CN8#TRPBF L T1054CN8 8-Lead Plastic DIP 0°C to 100°C L T1054IN8#PBF L T1054IN8#TRPBF L T1054IN8 8-Lead Plastic DIP –40°C to 100°C L T1054MJ8#PBF L T1054MJ8#TRPBF L T1054MJ8 8-Lead Ceramic DIP –55°C to 125°C L T1054CS8#PBF L T1054CS8#TRPBF 1054 8-Lead Plastic SO 0°C to 100°C L T1054LCS8#PBF L T1054LCS8#TRPBF 1054L 8-Lead Plastic SO 0°C to 100°C L T1054IS8#PBF L T1054IS8#TRPBF 1054I 8-Lead Plastic SO –40°C to 100°C L T1054CSW#PBF L T1054CSW#TRPBF L T1054CSW 16-Lead Plastic SO 0°C to 100°C L T1054ISW#PBF L T1054ISW#TRPBF L T1054ISW 16-Lead Plastic SO –40°C to 100°C L T1054CJ8#PBF OBSOLETE PART L T1054CJ8#TRPBF L T1054CJ8 8-Lead Ceramic DIP 0°C to 100°C Consult L TC Marketing for parts specified with wider operating temperature ranges. Consult L TC Marketing for information on non-standard lead based finish parts. For more information on lead free part marking, go to: http://www.linear .com/leadfree/ For more information on tape and reel specifications, go to: http://www.linear .com/tapeandreel/ Maximum Junction Temperature (Note 3) Storage Temperature Range

ELECTRICAL CHARACTERISTICS

Note 1: Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. Exposure to any Absolute Maximum Rating condition for extended periods may affect device reliability and lifetime. Note 2: The absolute maximum supply voltage rating of 16V is for unregulated circuits using L T1054. For regulation mode circuits using L T1054 with V OUT ≤ 15V at Pin 5 (Pin 11 on S package), this rating may be increased to 20V . The absolute maximum supply voltage for L T1054L is 7V . Note 3: The devices are guaranteed by design to be functional up to the absolute maximum junction temperature. Note 4: For voltage loss tests, the device is connected as a voltage inverter , with pins 1, 6, and 7 (3, 12, and 13 S package) unconnected. The voltage losses may be higher in other configurations. The l denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25°C. (Note 7) PARAMETER CONDITIONS MIN TYP MAX UNITS Supply Current ILOAD = 0mA L T1054: VIN = 3.5V VIN = 15V l l 2.5 3.0 4.0 5.0 mA mA L T1054L: V IN = 3.5V VIN = 7V l l 2.5 3.0 4.0 5.0 mA mA Supply Voltage Range L T1054 L T1054L l l 3.5 3.5 V V Voltage Loss (V IN – |VOUT|) CIN = COUT = 100µF Tantalum (Note 4) IOUT = 10mA IOUT = 100mA IOUT = 125mA (L T1054L) l l l 0.35 1.10 1.35 0.55 1.60 1.75 V V V Output Resistance ∆I OUT = 10mA to 100mA (Note 5) l 10 15 Ω Oscillator Frequency L T1054: 3.5V ≤ VIN ≤ 15V L T1054L: 3.5V ≤ VIN ≤ 7V l l kHz kHz Reference Voltage I REF = 60µA, TJ = 25°C l 2.35 2.25 2.50 2.65 2.75 V V Regulated Voltage V IN = 7V , TJ = 25°C, RL = 500Ω (Note 6) –4.70 –5.00 –5.20 V Line Regulation L T1054: 7V ≤ VIN ≤ 12V , RL = 500Ω (Note 6) l 5 25 mV Load Regulation VIN = 7V , 100Ω ≤ 500Ω (Note 6) l 10 50 mV Maximum Switch Current 300 mA Supply Current in Shutdown VPIN1 = 0V l 100 200 µA Note 5: Output resistance is defined as the slope of the curve, (∆VOUT vs ∆IOUT), for output currents of 10mA to 100mA. This represents the linear portion of the curve. The incremental slope of the curve will be higher at currents <10mA due to the characteristics of the switch transistors. Note 6: All regulation specifications are for a device connected as a positive-to-negative converter/regulator with R1 = 20k, R2 = 102.5k, C1 = 0.002µF , (C1 = 0.05µF S package) C IN = 10µF tantalum, COUT = 100µF tantalum. Note 7: The S8 package uses a different die than the H, J8, N8 and S packages. The S8 device will meet all the existing data sheet parameters. See Regulation and Capacitor Selection in the Applications Information section for differences in application requirements.

TYPICAL PERFORMANCE CHARACTERISTICS Supply Current in Shutdown Average Input Current Output Voltage Loss Output Voltage Loss Output Voltage Loss Shutdown Threshold Supply Current Oscillator Frequency TEMPERATURE (°C) – 50 SHUTDOWN THRESHOLD (V) 0.4 0.5 0.6 25 75 LT1054 • TPC01 0.3 0.2 – 25 0 50 100 125 0.1 VPIN1 INPUT VOLTAGE (V) SUPPLY CURRENT (mA) IL = 0 5 10 15 LT1054 • TPC02 TEMPERATURE (°C) –50 –70 FREQUENCY (kHz) 0 50 75 LT1054 • TPC03 –25 25 100 125 VIN = 15V VIN = 3.5V INPUT VOLTAGE (V) QUIESCENT CURRENT (µA) 120 5 10 15 LT1054 • TPC04 100 VPIN1 = 0V OUTPUT CURRENT (mA) AVERAGE INPUT CURRENT (mA)20 100 140 LT1050 • TPC05 120 40 10020 60 80 INPUT CAPACITANCE (µF) VOLTAGE LOSS (V) 0.2 0.6 0.8 1.0 1.4 10 50 70 LT1054 • TPC06 0.4 1.2 40 90 10020 30 60 80 INVERTER CONFIGURATION COUT = 100µF TANTALUM fOSC = 25kHz IOUT = 100mA IOUT = 50mA IOUT = 10mA OSCILLATOR FREQUENCY (kHz) VOLTAGE LOSS (V) 10 100 LT1054 • TPC07 INVERTER CONFIGURATION C IN = 10µF TANTALUM COUT = 100µF TANTALUM IOUT = 100mA IOUT = 50mA IOUT = 10mA OSCILLATOR FREQUENCY (kHz) VOLTAGE LOSS (V) 10 100 LT1054 • TPC08 INVERTER CONFIGURATION C IN = 100µF TANTALUM COUT = 100µF TANTALUM IOUT = 100mA IOUT = 50mA IOUT = 10mA

TYPICAL PERFORMANCE CHARACTERISTICS Regulated Output Voltage Reference Voltage Temperature Coefficient TEMPERATURE (°C) –50 –12.6 OUTPUT VOLTAGE (V) –12.4 –12.0 –11.8 –11.6 –4.7 –5.0 0 50 75 LT1054 • TPC09 –12.2 –4.9 –4.8 –5.1 –25 25 100 125 TEMPERATURE (°C) –50 –100 REFERENCE VOLTAGE CHANGE (mV)–80 –40 –20 100 0 50 75 LT1054 • TPC10 –60 –25 25 100 125 VREF AT 0 = 2.500V PIN FUNCTIONS FB/SHDN (Pin 1): Feedback/Shutdown Pin. This pin has two functions. Pulling Pin 1 below the shutdown threshold (≈ 0.45V) puts the device into shutdown. In shutdown the reference/regulator is turned off and switching stops. The switches are set such that both C IN and COUT are discharged through the output load. Quiescent current in shutdown drops to approximately 100µA (see Typical Performance Characteristics). Any open-collector gate can be used to put the L T1054 into shutdown. For normal (unregulated) operation the device will start back up when the external gate is shut off. In L T1054 circuits that use the regulation feature, the external resistor divider can provide enough pull-down to keep the device in shutdown until the output capacitor (C OUT) has fully discharged. For most applica- tions where the L T1054 would be run intermittently, this does not present a problem because the discharge time of the output capacitor will be short compared to the off- time of the device. In applications where the device has to start up before the output capacitor (C OUT) has fully discharged, a restart pulse must be applied to Pin 1 of the L T1054. Using the circuit of Figure 5, the restart signal can be either a pulse (t p > 100µs) or a logic high. Diode coupling the restart signal into Pin 1 will allow the output voltage to come up and regulate without overshoot. The resistor divider R3/R4 in Figure 5 should be chosen to provide a signal level at pin 1 of 0.7V to 1.1V . Pin 1 is also the inverting input of the L T1054’s error amplifier and as such can be used to obtain a regulated output voltage. CAP +/CAP – (Pin 2/Pin 4): Pin 2, the positive side of the input capacitor (C IN), is alternately driven between V + and ground. When driven to V +, Pin 2 sources current from V+. When driven to ground Pin 2 sinks current to ground. Pin 4, the negative side of the input capacitor , is driven alternately between ground and VOUT. When driven to ground, Pin 4 sinks current to ground. When driven to V OUT Pin 4 sources current from COUT. In all cases current flow in the switches is unidirectional as should be expected using bipolar switches. V OUT (Pin 5): In addition to being the output pin this pin is also tied to the substrate of the device. Special care must be taken in L T1054 circuits to avoid pulling this pin positive with respect to any of the other pins. Pulling Pin 5 positive with respect to Pin 3 (GND) will forward bias the substrate diode which will prevent the device from starting. This condition can occur when the output load driven by the L T1054 is referred to its positive supply (or to some other positive voltage). Note that most op amps present just such a load since their supply currents flow from their V + terminals to their V– terminals. To prevent start-up problems with this type of load an external

10µF TANTALUM COUT 100µF TANTALUM VOUT LT1054 • F05 VIN 2.2µFR3 R1 = ≈ + 1 WHERE VREF = 2.5V NOMINAL *CHOOSE THE CLOSEST 1% VALUE FOR EXAMPLE: TO GET VOUT = –5V REFERRED TO THE GROUND PIN OF THE LT1054, CHOOSE R1 = 20k, THEN |VOUT| ))VREF 2 – 40mV ))2.5V 2 – 40mV + 1|VOUT| 1.21V LT1054 FB/SHDN CAP+ GND CAP OSC VREF VOUT be 20k or greater because the reference output current is limited to ≈100µA. R2 should be chosen to be in the range of 100k to 300k. For optimum results the ratio of C IN/COUT is recommended to be 1/10. C1, required for good load regulation at light load currents, should be 0.002µF for all output voltages. A new die layout was required to fit into the physical dimensions of the S8 package. Although the new die of the L T1054CS8 will meet all the specifications of the existing L T1054 data sheet, subtle differences in the layout of the new die require consideration in some ap- plication circuits. In regulating mode circuits using the 1054CS8 the nominal values of the capacitors, C IN and COUT, must be approximately equal for proper operation at elevated junction temperatures. This is different from the earlier part. Mismatches within normal production tolerances for the capacitors are acceptable. Making the nominal capacitor values equal will ensure proper opera- tion at elevated junction temperatures at the cost of a small degradation in the transient response of regulator circuits. For unregulated circuits the values of C IN and COUT are normally equal for all packages. For S8 applica- tions assistance in unusual applications circuits, please consult the factory. It can be seen from the circuit block diagram that the maximum regulated output voltage is limited by the supply voltage. For the basic configuration, |VOUT| referred to the ground pin of the L T1054 must be less than the total of the supply voltage minus the voltage loss due to the switches. The voltage loss versus output current due to the switches can be found in Typical Performance Characteristics. Other configurations such as the negative doubler can provide higher output voltages at reduced output currents (see Typical Applications). Capacitor Selection For unregulated circuits the nominal values of C IN and COUT should be equal. For regulated circuits see the section on Regulation. While the exact values of C IN and COUT are noncritical, good quality, low ESR capacitors such as solid tantalum are necessary to minimize voltage losses at high currents. For C IN the effect of the ESR of the capacitor will be multiplied by four due to the fact that switch currents are approximately two times higher than output current and losses will occur on both the charge and discharge cycle. This means that using a capacitor with 1Ω of ESR for C IN will have the same effect as increasing the output imped- ance of the L T1054 by 4Ω. This represents a significant increase in the voltage losses. For C OUT the affect of ESR is less dramatic. COUT is alternately charged and discharged at a current approximately equal to the output current and the ESR of the capacitor will cause a step function to oc- cur in the output ripple at the switch transitions. This step function will degrade the output regulation for changes in output load current and should be avoided. Realizing that large value tantalum capacitors can be expensive, a technique that can be used is to parallel a smaller tantalum capacitor with a large aluminum electrolytic capacitor to gain both low ESR and reasonable cost. Where physical size is a concern some of the newer chip type surface mount tantalum capacitors can be used. These capacitors are normally rated at working voltages in the 10V to 20V range and exhibit very low ESR (in the range of 0.1Ω). Output Ripple The peak-to-peak output ripple is determined by the value of the output capacitor and the output current. Peak-to- peak output ripple may be approximated by the formula: dV = IOUT 2fCOUT Figure 5

where dV = peak-to-peak ripple and f = oscillator frequency. For output capacitors with significant ESR a second term must be added to account for the voltage step at the switch transitions. This step is approximately equal to: (2IOUT)(ESR of COUT) Power Dissipation The power dissipation of any L T1054 circuit must be limited such that the junction temperature of the device does not exceed the maximum junction temperature rat- ings. The total power dissipation must be calculated from two components, the power loss due to voltage drops in the switches and the power loss due to drive current losses. The total power dissipated by the L T1054 can be calculated from: P ≈ (VIN – |VOUT|)(IOUT) + (VIN)(IOUT)(0.2) where both VIN and VOUT are referred to the ground pin (Pin 3) of the L T1054. For L T1054 regulator circuits, the power dissipation will be equivalent to that of a linear regulator . Due to the limited power handling capability of the L T1054 packages, the user will have to limit output current requirements or take steps to dissipate some power external to the L T1054 for large input/output differentials. This can be accomplished by placing a resistor in series with C IN as shown in Figure 6. A portion of the input voltage will then be dropped across this resistor without affecting the output regulation. Because switch current is approximately 2.2 times the output current and the resistor will cause a voltage drop when C IN is both charging and discharging, the resistor should be chosen as: RX = VX/(4.4 IOUT) where: VX ≈ VIN – [(L T1054 Voltage Loss)(1.3) + |VOUT|] and IOUT = maximum required output current. The factor of 1.3 will allow some operating margin for the L T1054. For example: assume a 12V to – 5V converter at 100mA output current. First calculate the power dissipation without an external resistor: P = 700mW + 240mW = 940mW At θJA of 130°C/W for a commercial plastic device this would cause a junction temperature rise of 122°C so that the device would exceed the maximum junction tempera- ture at an ambient temperature of 25°C. Now calculate the power dissipation with an external resistor (R X). First find how much voltage can be dropped across RX. The maxi- mum voltage loss of the L T1054 in the standard regulator configuration at 100mA output current is 1.6V , so: This resistor will reduce the power dissipated by the L T1054 by (4.9V)(100mA) = 490mW . The total power dis- sipated by the L T1054 would then be (940mW – 490mW) = 450mW . The junction temperature rise would now be only 58°C. Although commercial devices are guaranteed to be functional up to a junction temperature of 125°C, the specifications are only guaranteed up to a junction tem- perature of 100°C, so ideally you should limit the junction temperature to 100°C. For the above example this would mean limiting the ambient temperature to 42°C. Other steps can be taken to allow higher ambient temperatures. The thermal resistance numbers for the L T1054 packages represent worst-case numbers with no heat sinking and still air . Small clip-on type heat sinks can be used to lower the thermal resistance of the L T1054 package. In some systems there may be some available airflow which will help to lower the thermal resistance. Wide PC board traces from the L T1054 leads can also help to remove heat from the device. This is especially true for plastic packages. CIN COUT VOUT LT1054 • F06 VIN RX LT1054 FB/SHDN CAP+ GND CAP OSC VREF VOUT Figure 6

Basic Voltage Inverter/Regulator Positive Doubler 100µF VIN –VOUT LT1054 • TAO2 LT1054 FB/SHDN CAP+ GND CAP OSC VREF VOUT 2µF 100µF 0.002µF 10µF 100µF REFER TO FIGURE 5 2µF VOUT LT1054 • TA03 VIN R1 = = + 1|VOUT| ))VREF 2 – 40mV )) + 1 ,|VOUT| 1.21V LT1054 FB/SHDN CAP+ GND CAP OSC VREF VOUT 2µF 100µF VIN = –3.5V TO –15V VOUT = 2VIN + (LT1054 VOLTAGE LOSS) + (QX SATURATION VOLTAGE) *SEE FIGURE 3 VIN VIN VOUT LT1054 • TAO4 RX* 100µF LT1054 FB/SHDN CAP+ GND CAP OSC VREF VOUT QX* 1N4001 VIN = 3.5V TO 15V VOUT ≈ 2VIN – (VL + 2VDIODE) VL = LT1054 VOLTAGE LOSS VIN 3.5V TO 15V LT1054 • TAO5 1N4001 VOUT 50mA 100µF 2µF10µF +++ LT1054 FB/SHDN CAP+ GND CAP OSC VREF VOUT 100mA Regulating Negative Doubler 1N4002 HP5082-2810 VIN

3.5 TO 15V

1N40020.002µF LT1054 • TAO6 2.2µF 40k VOUT SET PIN 2 LT1054 #1 OUT IOUT ≅ 100mA MAX 500k 1N4002 1N4002 1N4002 , REFER TO FIGURE 5 VIN = 3.5 TO 15V VOUT MAX ≈ –2VIN + [1054 VOLTAGE LOSS + 2(VDIODE)] = = + 1|VOUT| ))VREF 2 – 40mV )) + 1|VOUT| 1.21V 10µF 10µF 100µF 10µF 10µF 10µF +10µF + LT1054 #1 FB/SHDN CAP+ GND CAP OSC VREF VOUT LT1054 #2 FB/SHDN CAP GND CAP OSC VREF VOUT

5V to ± 12V Converter Bipolar Supply Doubler Strain Gauge Bridge Signal Conditioner VIN 3.5V TO 15V –VOUT LT1054 • TAO7 +VOUT = 1N4001 VIN = 3.5V TO 15V +VOUT ≈ 2VIN – (VL + 2VDIODE) –VOUT ≈ –2VIN + (VL + 2VDIODE) VL = LT1054 VOLTAGE LOSS 100µF 10µF 10µF 10µF 100µF 100µF + + LT1054 FB/SHDN CAP+ GND CAP OSC VREF VOUT 20k 1N9141N914 VIN = 5V TO PIN 4 LT1054 #1 VOUT ≈ –12V IOUT = 25mA VOUT ≈ 12V IOUT = 25mA LT1054 • TAO8 2N2219 10µF 100µF 10µF 10µF 100µF 5µF100µF 5µF + + + + LT1054 #2 FB/SHDN CAP+ GND CAP OSC VREF VOUT LT1054 #1 FB/SHDN CAP GND CAP OSC VREF VOUT 1µF 200k 100µF TANTALUM LT1054 • TAO9 0.022µF – 2N2222 A = 125 FOR 0V TO 3V OUT FROM FULL-SCALE BRIDGE OUTPUT OF 24mV 100k 100k 10k ZERO TRIM GAIN TRIM 10k 10k 5V 40/uni03A9 301k 1/2 LT1013 5k 6 10k 2N2907 INPUT TTL OR CMOS LOW FOR ON 350/uni03A9 1/2 LT1013 10µF + + 10µF LT1054 FB/SHDN CAP+ GND CAP OSC VREF VOUT

3.5V to 5V Regulator Regulating 200mA, 12V to – 5V Converter Digitally Programmable Negative Supply 5µF 100µF 20k 1N914 20k 1N914 VIN = 3.5V TO 5.5V VOUT = 5V IOUT(MAX) = 50mA 1N914 1N5817 VIN 3.5V TO 5.5V LT1054 • TA10 LTC1044 1µF 1µF 0.002µF R2 125k 3k 1N914 125k 2N2219 VOUT = 5V 10µF LT1054 FB/SHDN CAP+ GND CAP OSC VREF VOUT 0.002µF HP5082-2810 VOUT = –5V IOUT = 0mA to 200mA 12V 39.2k 200k 20k 10/uni03A9 1/2W LT1054 • TA11 10/uni03A9 1/2W10µF 5µF 200µF 10µF LT1054 #1 FB/SHDN CAP+ GND CAP OSC VREF VOUT LT1054 #2 FB/SHDN CAP GND CAP OSC VREF VOUT REFER TO FIGURE 5 R1 = = + 1|VOUT| ))VREF 2 – 40mV )) + 1 ,|VOUT| 1.21V 20k VOUT = –VIN (PROGRAMMED) 20k 15V LT1004-2.5 2.5V LT1054 • TA12 AD558 DIGITAL INPUT 13 12 10µF 5µF 100µF+ LT1054 FB/SHDN CAP+ GND CAP OSC VREF VOUT

8-Lead CERDIP (Narrow .300 Inch, Hermetic) (Reference L TC DWG # 05-08-1110) J8 0801 .014 – .026 (0.360 – 0.660) .200 (5.080) MAX .015 – .060 (0.381 – 1.524) .125 3.175 MIN.100 (2.54) BSC .300 BSC (7.62 BSC) .008 – .018 .005 (0.127) MIN .405 (10.287) MAX .220 – .310 (5.588 – 7.874) 1 2 3 4 8 7 6 5 .025 (0.635) RAD TYP .045 – .068 (1.143 – 1.650) FULL LEAD OPTION .023 – .045 (0.584 – 1.143) HALF LEAD OPTION CORNER LEADS OPTION (4 PLCS) .045 – .065 (1.143 – 1.651)NOTE: LEAD DIMENSIONS APPLY TO SOLDER DIP/PLATE OR TIN PLATE LEADS 8-Lead PDIP (Narrow .300 Inch) (Reference L TC DWG # 05-08-1510) N8 1002 .065 (1.651) TYP .045 – .065 (1.143 – 1.651) .130 .005 (3.302 0.127) .020 (0.508) MIN.018 .003 (0.457 0.076) .120 (3.048) MIN .008 – .015 (0.203 – 0.381) .300 – .325 (7.620 – 8.255) .325 +.035 –.015 +0.889 –0.3818.255 ( ) 1 2 3 4 8 7 6 5 .255 .015* (6.477 0.381) .400* (10.160) MAX NOTE: 1. DIMENSIONS ARE INCHES MILLIMETERS *THESE DIMENSIONS DO NOT INCLUDE MOLD FLASH OR PROTRUSIONS. MOLD FLASH OR PROTRUSIONS SHALL NOT EXCEED .010 INCH (0.254mm) .100 (2.54) BSC

8-Lead Plastic Small Outline (Narrow .150 Inch) (Reference L TC DWG # 05-08-1610) .016 – .050 (0.406 – 1.270) .010 – .020 0°– 8° TYP .008 – .010 (0.203 – 0.254) SO8 0303 .053 – .069 (1.346 – 1.752) .014 – .019 (0.355 – 0.483) TYP .004 – .010 (0.101 – 0.254) .050 (1.270) BSC 1 2 3 4 .150 – .157 (3.810 – 3.988) NOTE 3 8 7 6 5 .189 – .197 (4.801 – 5.004) NOTE 3 .228 – .244 (5.791 – 6.197) .245 MIN .160 ±.005 RECOMMENDED SOLDER PAD LAYOUT .045 ±.005 .050 BSC .030 ±.005 TYP INCHES (MILLIMETERS) NOTE: 1. DIMENSIONS IN 2. DRAWING NOT TO SCALE 3. THESE DIMENSIONS DO NOT INCLUDE MOLD FLASH OR PROTRUSIONS. MOLD FLASH OR PROTRUSIONS SHALL NOT EXCEED .006" (0.15mm) S16 (WIDE) 0502 NOTE 3 .398 – .413 (10.109 – 10.490) NOTE 4 16 15 14 13 12 11 10 9 N 2 3 4 5 6 7 8 N/2 .394 – .419 (10.007 – 10.643) .037 – .045 (0.940 – 1.143) .004 – .012 (0.102 – 0.305) .093 – .104 (2.362 – 2.642) .050 (1.270) BSC .014 – .019 (0.356 – 0.482) TYP 0 – 8 TYP NOTE 3 .009 – .013 (0.229 – 0.330) .005 (0.127) RAD MIN .016 – .050 (0.406 – 1.270) .291 – .299 (7.391 – 7.595) NOTE 4 ¥ 45∞.010 – .029 (0.254 – 0.737) INCHES (MILLIMETERS) NOTE: 1. DIMENSIONS IN 2. DRAWING NOT TO SCALE 3. PIN 1 IDENT, NOTCH ON TOP AND CAVITIES ON THE BOTTOM OF PACKAGES ARE THE MANUFACTURING OPTIONS. THE PART MAY BE SUPPLIED WITH OR WITHOUT ANY OF THE OPTIONS 4. THESE DIMENSIONS DO NOT INCLUDE MOLD FLASH OR PROTRUSIONS. MOLD FLASH OR PROTRUSIONS SHALL NOT EXCEED .006" (0.15mm) .420 MIN .325 .005 RECOMMENDED SOLDER PAD LAYOUT .045 .005 N 1 2 3 N/2 .050 BSC.030 .005 TYP 16-Lead Plastic Small Outline (Wide .300 Inch) (Reference L TC DWG # 05-08-1620)

Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However , no responsibility is assumed for its use. Linear Technology Corporation makes no representa- tion that the interconnection of its circuits as described herein will not infringe on existing patent rights.

REVISION HISTORY

REV DATE DESCRIPTION PAGE NUMBER F 12/10 The L TC1054MJ8 is now available. Changes reflected throughout the data sheet 1 to 16 G 6/11 Correct error to part number from LTC7660 to ICL7660 1 (Revision history begins at Rev F)

Linear Technology Corporation 1630 McCarthy Blvd., Milpitas, CA 95035-7417 (408) 432-1900 ● FAX: (408) 434-0507 ● www.linear .com  LINEAR TECHNOLOGY CORPORATION 2010 LT 0611 REV G • PRINTED IN USA RELATED PARTS TYPICAL APPLICATIONS Negative Doubler with RegulatorPositive Doubler with Regulation 0.03µF VIN = 5V 50k 1N5817 1N5817 LT1054 • TA13 10k 10k 10k 5.5k 2.5k 0.1µF LT1006 100µF VOUT 50mA 2µF10µF + LT1054 FB/SHDN CAP+ GND CAP OSC VREF VOUT 2µF VIN 3.5V TO 15V 100µF R2 1N4001 1N4001 LT1054 • TA14 100µF 0.002µF –VOUT VIN = 3.5V TO 15V VOUT(MAX) ≈ –2VIN + (VL + 2VDIODE) VL = LT1054 VOLTAGE LOSS , REFER TO FIGURE 5R2 = = + 1|VOUT| ))VREF 2 – 40mV )) + 1|VOUT| 1.21V 10µF 10µF LT1054 FB/SHDN CAP+ GND CAP OSC VREF VOUT R1, 20k PART NUMBER DESCRIPTION COMMENTS LT C

1144 Switched-Capacitor Wide Input Range Voltage Converter with

Wide Input Voltage Range: 2V to 18V , ISD < 8µA, SO8 L TC1514/L TC1515 Step-Up/Step-Down Switched-Capacitor DC/DC Converters VIN: 2V to 10V , VOUT: 3.3V to 5V , IQ = 60µA, SO8 L T1611 150mA Output, 1.4mHz Micropower Inverting Switching Regulator VIN: 0.9V to 10V , VOUT: ±34V ThinSOT™ L T1614 250mA Output, 600kHz Micropower Inverting Switching Regulator VIN: 0.9V to 6V , VOUT: ±30V , IQ = 1mA, MS8, SO8 L TC3250/L TC3250-1.2/ L TC3250-1.5 Inductorless Step-Down DC/DC Converter V IN: 3.1V to 5.5V , VOUT: 1.2V , 1.5V , IQ = 35µA, ThinSOT MS10E L TC3252 Dual 250mA, Spread Spectrum Inductorless Step-Down DC/DC Converter V IN: 2.7V to 5.5V , VOUT: 0.9V to 1.6V , IQ = 50µA, DFN12 THE TYPICAL APPLICATIONS CIRCUITS WERE VERIFIED USING THE STANDARD L T1054. FOR S8 APPLICATIONS ASSISTANCE IN ANY OF THE UNUSUAL APPLICATIONS CIRCUITS PLEASE CONSUL T THE FACTORY