UDN-2950Z

ULN-2061M ETC2

Document overview

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SECTION 4—HIGH-CURRENT (21 A) INTERFACE DRIVERS Selection Guide 6... eee e eee eee e cree ee cee eec eee eeest eee seteetetn sees 42 UDN-2540B Quad 1.25 A Power Driver... oe e ccc eeeeee cette ceceeccereesveeeees del UDN-2906W 3-Phase 2 A Brushless DC Motor Driver . . eee 2) UDN-2935Z 2A Half-Bridge Motor Driver... o.oo e eee eee ee cee eec eee eeete eee ee reece ee 434 UDN-2941B Quad 2A Source Driver... oe e cece eee eee eeee eee eve en ress 448 UDN-2944W Quad 4A High-Voltage Source Driver ©... 0. ecco cece cee ce cence eee enn ee G55 UDN-2948W Quad 6 A High-Voltage Source Driver... ee cece cece ec eccceeeceeer nena reese 458 UON-29502 2A Half-Bridge Motor Driver... ook eee fences O84 UDN-2951Z 8 A Haif-Bridge Driver... o.oo eec eee e teeta ecce ee ee ects en ev eres 461 UDN-2953B and 2954W 2A Full-Bridge Motor Drivers... 0. eee ceeeeeeeeeeeeeeee eee ee 70 UDN-2998W Dual 2A Full-Bridge Motor Driver... eee cece e eee ee cece e eee e eee $89 ULN-3755B/W Dual Power Operational Amplifiers 0... eee ec ceeeeeceeeeceeeeeeeveeeees G07 UDN-7078 Quad High-Current Darlington Switches 2.0... eee eee ee cece nese eevee 4-121 Application Notes: See Also: ULN-70648 through 70748 Quad High-Voltage, 1 A Darlington ArrayS 0... cece eeceeeueeeee eee 215 4—1

HIGH-CURRENT INTERFACE DRIVERS eee erence SELECTION GUIDE (in order of tested output current rating) —_ COME errr tn Mn tpts_ vice Type Page +L0A 26V Half-Bridge UDN-2943Z 4-51 + LOA Linear ay Power Op Amp ULN-3751Z 4-93 +1L0A Linear 40V Dual Power Op Amp ULN-3753BW 4-98 + L.0A Linear 40V Dual Power Op Amp ULN-3755BAW 4107 104 50V Sink at UCN-5813/14B 5-41 10A TOV Sink 2 UDN-5725M ALT LOA 80V Sink 4+ UCN-5813/14B-1 5-41 LOA 150¥ Sink & ULN-7064/68/74B 2-15 125A 50V Source/Sink 2 ULN-2061M 43 125A 50 Sink 4 ULN-2064/66/68/70B 43 125A 50V Source/Sink 4 ULN-2074B 43 125A 60V Sink 4 UDN-2540B Ald -15A 35V Source 4 UDN-2941B 4-48 15A —50V Sink & UDN-2841/458 4-19 -15A -30V Source 4 UDN-28458 4-19 15a 80v Source/Sink 2 ULN-2062M 43 15a 80V Sink 4 ULN-2065/67/69/71B 4-3 LSA 80V Source/Sink 4 ULN-2075B 43 LI5A ov Sink 4t UCN-5825B 5-59 175A 80V Sink 47 UCN-5826B 5-59 +20A 15V 3 x Half-Bridge UDN-2906W * *2.0A 15V 3 x Half-Bridge UDN-2931B¥ 4-31 +20A 35V Half-Bridge UDN-2935/502 4-34 =2.0A 40v Full-Bridge UDN-2952B/0 4-64 =20A 50 Full-Bridge UDN-2953B/54W 4-70 =20A SOV 2 x Full-Bridge UDN-2998W 4-89 208 80V Sink 4 UDN-25458 4-17 =3.0A 45V 3 x Half-Bridge UDN-2936/37W 4-40 3.0A PWM 45¥ Source/Sink 2 ‘UDN-2962W 475 30A 90 Sink 4 UDN-7078W 4121 4.0K 50¥ Sink 4 UON-28780 4-25 40K 50V Sink 3 UDN-29380/39B 4-46 4.04 50V Source/Sink 2 UDN-2975W. 4-86 4.0APWM 50 Source/Sink 2 UDN-2965W-2 4-81 4.08 60V Source/Sink 2 ‘UDN-2976W 4-86 —40A 60 Source 4 UDN-2944W 4-55 408 80V Sink 4 UDN-28794 4-25 -6.0A 60V Source 4 UDN-2948W 4-58 =8,0A 50V Half-Bridge UDN-29512/55W 461 Current ratings shown are maximum tested condition; allowable peek, or start-up currents are generally higher; voltage ratings shown are maximum allowable, Devices with ratings of less than 1 A are listed in Section 3, ‘latched Smart Power drivers. “New product. Contact factory for information. 4—2

ULN-2061M THROUGH ULN-2075B

1.5 DARLINGTON SWITCHES

ULN-2061M THROUGH ULN-2075B 1.5A DARLINGTON SWITCHES FEATURES ‘ ee ws © TIL, DTL, CMOS Compatible Inputs < 2 Lc. © Transient-Protected Outputs va iE. © Loads to 480 Watts e <e . © Plastic Dual In-Line Packages ‘oy a © Heat-Sink Contact Tabs on Quad Arrays pore ULN-2061M ULN-2062M [{'SHVOLTAGE, HIGH-CURRENT Datling- are used for common-emitter (externally con- ton arrays ULN-2061M through ULN-2075B nected), or emitter-follower applications. Both de- are designed as interface between low-level logic vices are supplied in miniature 8-pin dual in-line and a variety of peripheral loads such as relays, so- plastic packages. lenoids, de and stepper motors, multiplexed LED and incandescent displays, heaters, and similar Quad drivers ULN-2064B, ULN-2065B, ULN- loads to 480 watts (1.5 A per output, 80 V, 26% duty 2068B and ULN-2069B are intended for use with cycle). TTL, low-speed TTL, and 5V MOS logic. Types The devices have a minimum output breakdown ULN-2065B and ULN-2069B are selected for the of 50V and a minimum Vezsus of 35 V measured at 80V minimum output breakdown specification. 100mA, or a minimum output breakdown of 80V Types ULN-2068B and ULN-2069B have pre- and a minimum Vegisus, of 50 V. driver stages and are most suitable for applications Dual-driver arrays ULN-2061M and ULN-2062M requiring high gain (low input-current loading). re ee a ® Tse ¢ °By Fig] ¢ Pes! Bs} xc ao eae op Fes! Ce: re <e tS Na aps) dh. ‘Oe ee Ol” “Gi a ULN-2064B ‘ULN-2068B ‘ULN-20748 ‘ULN-2065B ‘ULN-2069B ULN-2075B 443

ULN-2061M THROUGH ULN-2075B 1.5A DARLINGTON SWITCHES Sel Isolated Darlington arrays ULN-2074B and ULN- ABSOLUTE MAXIMUM RATINGS 2075B are identical to Types ULN-2064B and ULN- at +25°C Free-Air Temperature 2065B except for the isolated Darlington pinout and for Any One Driver the deletion of suppression diodes. These switches (unless otherwise noted) are for emitter-follower or similar isolated-Darling- Output Voltage, Very -..-. ees ceeeeeeeee See Guide All quad Darlington arrays (suffix “B" devices) Output Current, lyr (Note 1) oes ese eeeeeeeeeee es LBA facilitates attachment of external heat sinks for in- soar’, Tents Rate Tyeceneeee i are to se creased power dissipation with standard IC sockets POS rrrneeee and printed wiring boards. ios 1. Allowable combinations of output current, number of outputs conducting, and duty cycle are shown on following pages. 2. Input voltage is referenced to the substrate (no connection to other pins) for ‘Type ULN-206L/62M and ULN-2074/758; reference is ground for all other 3. it current may be limited by maximum allowable input voltage. ALLOWABLE POWER DISSIPATION AS A FUNCTION OF TEMPERATURE ATT TT EAL tT Part = MAK. Min, Max. . N Number Vex Veseuy Vo Application 2 , ULN-2061M 50Y 35 30¥ TIL, DIL, Schotthy TTL, a IN Ne xX an ULN-2062M 80Y SOY 60¥ and 5V.CMOS 3° %, ULN-2064B 50Y 35Y 15V_ TIL, DTL, Schottky TTL 5 Ls Kk S| ULN-2065B 80Y 50V 15V and SV.CMOS 3 eX ULN-2068B S0V 35V15V_ TIL, DTU, Schotthy TTL, 8 | | s \\ |_| ULN-20698 80Y SOV 15V and 5Y.CMOS Fao IN ULN-20748 50V 35V 30 General Purpose g AN ULN-2075B 80Y 50V GOV z > ‘eN\\ = |, __— S N Ne PT | PANN Pit °o 3 100 130 AONE EMPEATURE "C—O, no, Joo.808

ULN-2061M THROUGH ULN-2075B 1.5A DARLINGTON SWITCHES SS ULN-2061M AND ULN-2062M PARTIAL SCHEMATIC rs « Pe] xe . c = he Car: ox Ss Sha i" . ahs EE. ws * Dwg. No. Aq10,3628 Dv nO, he, 2308, ELECTRICAL CHARACTERISTICS at + 25°C (unless otherwise noted) Test | Applicable | 4 Leemite | gona | |" cunts Output Leakage Current a a Output Sustaining Voltage [fe |? [ao fee iok a= ov [aff | eae = inne oes Collector-Emitter Veesan 3 Both I= S00mA I, = 625yA | — ti | vif | Saturation Voltage | [k= 750mA 1 = 935 yA [2 | Vv 1p = LOA by = 1.25 mA v Tnput Current Tce a mA mA Input Voltage Von v | Tumn-On Delay ty thE OSE, =| CO Ss | [Turn-OffDelay ty [Both OS Ete dS us Clamp Diode uuv-206M [v= soy 50a Leakage Current ee remedies || TSR SE Forward Voltage Phaisaq *Pulse-Test 4—5

ULN-2061M THROUGH ULN-2075B 3502 c ar: ye Bor a [a5] Ne Fran} o> Se A 3x Gx n3]GNO a) | <Ha ‘Oe ee (SIMILAR TO ULN-20748 AND ULN-20758) Dg He MTA FLECTRICAL CHARACTERISTICS at -+ 25°C (unless otherwise noted) vet | nie Characteristic Symbol_| fig. Devices Test Conditions Output Leakage Curent ka 1) wneo68 | vem sov | 00 | aa | uu20658 | Ve=aov | 100 | ua Ve = 80V,T, = 70°C Ovtput Sustaining Voltage Voom | 2 | UUN-20648 | 1, = 100mA, Va = 04V uwN-206658 | k = 100mA,V, = 04V Collector-Emittr en Saturation Voltage le = 750 mA, by = 935 pA Input Curent tan Bits [Vee zav | ud |_| 3396 Ingut Voltage Yao |__oth_— | er = 20, le = LOA UN-20648 | Vor = 20¥,le = 1258 UUN-20658 Turn-0n Delay tw | — | both | 056, 1005E, Tun-Of Delay | tm | — | toh | 056, 1005.4 (Clamp Diode Leakage Current k uun-206¢3 |v, = 50V We soutaroee [| — 100 | na | y= ona — 10 | aa] Clamp Diode Forward Voltage | 7

ULN-2061M THROUGH ULN-2075B PARTIAL SCHEMATIC « Y Se c No ono Bore c ° ne aa ‘ vel oe nc sgl |< ee 3K NC a ‘2 oe pore ELECTRICAL CHARACTERISTICS AT +25°C, V, = 5.0 V (unless otherwise noted) Test | Applicable Characteristic Symbol Fig. Devices Test Conditions Output Leakage Curent bs 1 | uun-20688 UIN-20698 | Ves = 80 | — 100 | ua | | 4| Output Sustaining Voltage Vesus | 2 {| ULN-20688 | 1, = 100mA\\v¥=04v | 35 — | v_ | uun-20698 [ 1, =100mAvy=O4v | 50 — | v | Collector-Emitter Veasan t, = 500 mA, Iy = 275V — ou Saturation Voltage |, = 750 MA, ly = 2.75V _ 12 I = 125A y= 275V =u ly ULN-20698 [i = 15, ly = 275V = is |v Input Current ‘noo 4 Both Vu = 275V pA |. Va = 375V uA Input Votage Yoo | 5 |_ULN-206B ¥ ULN-20698 | Vor = 20V,[,= 158 Turn-On Delay ee ee | Turn-offdelay | tw | [ath | 05,05, b= 1258 Clamp Diode Leakage Curent ULN-20688 Va = 50V,T, = 70°C = 100 pA uLv-2068B |_Vy = B0V Ye = 80,1, = 10% Giamp Diode Forward Votage | Wy 7 [weia =e | b= 15h

ULN-2061M THROUGH ULN-2075B 1.5A DARLINGTON SWITCHES EEE ULN-2074B AND ULN-2075B PARTIAL SCHEMATIC 350 c zB 72k Aes! Az]: F suB sua sup ng Na A588 = He C - ETS Se. : fiz]: c Th 15) c Owe Ne AaTSSA (SIMILAR TO ULN-2064B AND ULN-2066B) ELECTRICAL CHARACTERISTICS at + 25°C (unless otherwise noted) Characteristic symbol_| Fig. Devices Test Conditions Min. Max Output Leakage Current lox 1 ULN-2074B | Voc = 50¥ — 100 ULN-20758 Output Sustaining Voltage Versus i, = 100 mA, Vy = O4V o ULN-20758 Colletor-miter Yeon | 3 Both Saturation Voltage | Input Voltage Yoon | 5 ULN-20758 [iuin-OnDely | te | | toth sets, to Tas 4—8

ULN-2061M THROUGH ULN-2075B 1.5. DARLINGTON SWITCHES A TEST FIGURES conn Yee ontn orew OPEN ‘cox “IE te ie Figure 1 Figure 2 Figure 3 oN conn Me | 4 hin * ——2orn vt le Srw 1 | in vee mao oem

1 Le tm i T i*T i

Figure 4 Figure 5 Figure 6 Vs OPEN . . Ni vue ye i + Figure 7 Figure 8 4-9

ULN-2061M THROUGH ULN-2075B PEAK COLLECTOR CURRENT AS A FUNCTION OF DUTY CYCLE HET PPP TT . g y PENI i LAAN TEAS po | NSS a. LOAN TT ati] eS eA ESS PLIT TTT TTT | eC) eee LETTE TTT tt} LT LTT | memevene rect a et of HL led LTT : LT OAN ET o COONS aut Sees i con a wf fei [TT wT Th TT os 7. NI J i LNA SS i} tT NAXEES 3 a s | | | NAEAN: WEEE WASNT att TT | UNSEEN e LETT ASS Ea i [~~ 7 COPECO? COP 4—10

ULN-2061M THROUGH ULN-2075B AS A FUNCTION OF DUTY CYCLE (Continued) oT PPT) CTT PT TTT F LET INNA NAT: LT ANN) pel OCS SSS COONS RSS ecLi Tt) | OA~BSH e COONS : waren a2 win star teat Sie Po? Cea COLLECTOR CURRENT AS A FUNCTION OF INPUT CURRENT AT +25°C Coe Het eye ice .0P 40a see Lf TAT TT TT INFUT CURRENT IN ma = Ip Dwg No, A098 INPUT CURRENT IN UA = 1 wg. No. Aet205 4—lL

ULN-2061M THROUGH ULN-2075B INPUT CURRENT AS A FUNCTION OF INPUT VOLTAGE AT + 25°C EEEET TY) Lett tty | tee Ty) Lee DZ . =e LA 4 AL 7. 4Gn eee 4ae INPUT VOLTAGE = Vig Bg. te. 4109698, w gna. 2.308 TYPICAL APPLICATION 7 ‘ULN-2061/62M 5 gp. rea . bn Ne Meat BIDIRECTIONAL MOTOR CONTROL 4-12

ULN-2061M THROUGH ULN-2075B 1.5. DARLINGTON SWITCHES SE a eininemainl TYPICAL APPLICATIONS (Continued) ‘s ‘ee “e “es unto : a a3 ae + te] qh G) Ha A“ OG Cy o" te & [ a ¥y¥y COMMON-ANODE LED DRIVERS. (Series UDN-2980A devices can be used in similar applications at currents of up | 4 to 500 mA) a foe ame wp oS =e | i an qo pe Balin wae | er f? - COMMON-CATHODE LED DRIVERS (Type ULN-2068B is also applicable) 4—13

QUAD NAND-GATE POWER DRIVER ES UDN-2540B QUAD-NAND GATE POWER DRIVER FEATURES ov A. IT GHoAy KC IN, © 1.5A Output Current 4 ij eC © Output Vottage to 60 K GA [7 CH pe 5 © Integral Transient-Suppression Diodes t | ¢ Efficient Input/Output Pin Structure ours | <}ps] ENABLE © TIL, CMOS, PMOS, NMOS Compatible GROUND rd a GROUND Combining NAND logic gates and high-current bi- GROUND Ls | 32] GROUND polar outputs, the UDN-2540B power and relay our y driver provides interface between low-level signal- 2 =F [i a ig “ec processing circuits and power loads to 350 W. Each K oa] C= Ie INg of the four independent outputs of this device can our, Ca CEA in, sink up to 1.5 A in the oN state. In the OFF state the — a drivers will withstand at least 60 V. Transient- esate suppression clamp diodes and a minimum 35 V out- ona Ne put sustaining voltage allow their use with many in- ductive loads. Each of the four outputs is recommended for contin- Typical applications include relays, solenoids, uous load currents to 1.25 A. Outputs can be paral- and de stepping motors. It can also be used to drive leled for higher load currents. high-current incandescent lamps, LEDs, and The UDN-2540B is supplied in a 16-pin dual-in- heaters. In display applications, the diodes can be line package With heat-sink contact tabs. This con- used to perform the “lamp test”’ function. figuration allows attachment of an inexpensive heat Inputs are compatible with most TTL, DTL, sink and fits a standard integrated circuit socket or LSTTL, and 5 V or 12 V CMOS and PMOS logic. printed wiring board layout. ABSOLUTE MAXIMUM RATINGS at + 25°C Free-Air Temperature Output Voltage, Ver... 6. 60v Output Current, kur ese see se vvvceesereeeeeeeesveeeeseteeeesseeeees LBA Supply Voltage, Voc. css c ese ce cece ee cee eeepc eee epee sete e rene es 18¥ Operating Temperature Range, Ty... .seeeececee eves eeveecees —20°C to +85°C Storage Temperature Range, Ty... .cceecce cece ees eeeceeee = 55°C to + 150°C 4-14

QUAD NAND-GATE POWER DRIVER SS ELECTRICAL CHARACTERISTICS at T, = +25°C, Tas = +70°C, Vq = 4.75 V to 12.6V (unless otherwise noted) sm | Characteristic Symaol Test Conditions Output Leakage Current [| Yor = 60¥, Vp = 0.7, Vewue = 20 — 100 Vour = 60, Vi = 2.0, Vans = 0.7 Output Saturation Votage Yeon | lr = 280mAVy=Vouw=20V | 0 | | [t= 10AYu= Your =20V | a | Input Votage [ocict | VanarVow TC Input Curent “Bie eet = 200 Yay OF Vase = 04V vA I 0Clwas = — 10 ma Total Supply Current lee Va" = Vewaz = 2.0, Vor = 5.0, Outputs Open — 20 | m | Va" = Veune = 2.0V, Vor = 15¥, Outputs Open — 3 | om _| [va =Voee=O7¥Yn=50V | — 20 | mA _| Va = Vewae = 0.7 V, Vos = 15¥ |= 70 | om _| Clamp Diode Forward Voltage ‘ = 10A = 125A v [Gamo diode Leakage Curent [iy |W = 60,4 = Vouns = 20,0, > 0.07040, | — 100 | yA | “All inputs simultaneously, all other tests are performed with each input tested separately. 5 1 LATT TI pL N TT | z¢ \\ ALLOWABLE AVERAGE PACKAGE POWER DISSIPATION é Zz 2 nn AS A FUNCTION OF TEMPERATURE Bs Xs 5 2a Ne \\ SL ee ON z hss nts \\ PT SS % 0 3 100 13 ~e TEMPERATURE IN °C Og. No A1.7888 4—15

QUAD NAND-GATE POWER DRIVER Leena e eee reece eee] INCANDESCENT LAMP DRIVER * ve

APPLICATIONS

Typical applications for this device include driv- ing incandescent lamps and de stepper motors. LON 25403 Q Lamps with steady-state current ratings up to 150 IO ry DSF ia 1 mA can be driven without current limiting or warm- INO Col Fe aI aa ing resistors (assumes 1.5 A peak in-rush). The inter- La. |e nal diodes can be used to perform the “lamp test" | I function as shown. Bifilar (unipolar) stepper motors 0 ann . 3 can be driven directly. The internal transient. + 1 Qa suppression diodes prevent damage to the output ENABLE Qa > er transistor from positive high-voltage inductive moa 1DY HG spikes as the output switches OFF. Mo a Re + A a jp—{_ P+ 3} a wr a. Ne A204 STEPPER-MOTOR DRIVER INPUT WAVEFORMS. Vv +28y 1@) Le) * JT LIELE 1 UDN-25408 ot TD ®> LI LILI ; fold eI es - Vee 1} A tI] LIU uu ht He ac ENABLE O——(a} > a Dag No. A785 10 A tp di C | BO ape wa.Ne. ATH 416

FEATURES a , © Output Current of 24 " We = “A © 80 V Min, Output Breakdown nie Sed, © 40 Output Sustaining Voltage muss li . 1 a \\ © PMOS, CMOS, TIL Compatible wD RE Phe] our ™S © Built-in Thermal Shutdown | 1 < © Output Transient Protection i a © CHIP ENABLE for Microprocessor Controt sue * eae © Under-Vottage Protection il al\\y aE SU “ T* UDN-2545B is a four-channel high-current, Se jf] high-voltage integrated circuit designed to pro- can \\. NA, St = THERMAL SHUTDOWN, vide the interface between stepper motors and mi- _#*\\ "SS Ny, Ute wr a cockout croprocessor or logic motor control circuitry. The N\\A UDN-2545B will accept most standard logic signa \\\\ \\ ‘eo inputs and provide motor drive current to both POG. \\ “dha hystersis. The thermal sbutdown with hys- 8 epiy ras. \\ NON Dtensisis to guard against damage to the device. CHIP The UDN-2545B is capable of sinking up tO8.54 “S, ,“” EX ABLE is especially good for use in microproces- and maintaining an output OFF voltage of 80 volts." wy" . ¢ maintain a \\ sor control. All outputs have clamp diodes for This device incorporates some unigyefeatures such, sion of indi load as under-voltage protection, tné}mal shutdown, afi suppression of Inductive loads. CHIP ENABLE control. Pifenthdgr-vo Bdpfofec- The UDN-2545B is supplied ina 16 pin plastic dual tion guards against supily“linestfadsient’samf has in-line package with heat-sink contact tabs. A cop- 1s 3 Pi — vy per-alloy lead frame provides maximum power dis- FUNG) ONAL “DIAGRAM sipation using standard cooling methods. This lead r YY configuration facilitates attachment of external heat ro ee Se sinks for increased power dissipation with standard om line Ben IC sockets and printed wiring boards. ans-= | @ or ABSOLUTE MAXIMUM RATINGS ‘y t ° S 4 aT, = +25°C I] i i} oan Output Voltage, Ver... eee eee ces eeeeeeeeeeees BOV ~Ore >I’ Emitter Supply Voltage, Veg eo... eee ee cece eens =2BV lim Logic Suppiy Voltage, Yo oe... ese ceeececeeeeveee 20¥ mots Bon Output Current, lyr oe ee eee eve eeeeeeee eee eeees 25A Fe > — Input Voltage, Vay... eee cece ee eceeceeeeeeeee 25V *Derate at the Rate of 22.2 mW/°C above T, = 25°C. 4—7

ELECTRICAL CHARACTERISTICS at T, = + 25°C, V, = 5V to 15V, Viz = OV (unless otherwise noted) Characteristic Symbol Test Conditions Min, Max Units Output Leakage Current [lex | Vour = 80V, Va = 2.0, Other Inputs = OV — 500 pA Output Sustaining Voltage lo = 2, Inputs = 5.0V,L = 3 mH Cutput Saturation Votage™ Clamp Die Leakage Curent | h [W=@V SST | Input Current ee — = 250 pA [hon [VeeWe Supply Current Allinputs = 0.8V, V, = 5.0V Alinguts = OBV,Vs = 15V Allinputs = 5.0V, Vs = 5.0V Alltnputs = 15V, Vy = 15V ee ce *Pulse Test STEPPER MOTOR APPLICATION Ns qe Ly ‘ 5 a | ¥| ae a We & Ey —u—- af ; Ee INs i se Fala ee Vg=5V "78=THERMAL SHUTDOWN *UVL= UV TL LOCKOUT 4-18

QUAD 1.5 DARLINGTON DRIVERS SN UDN-2841B AND UDN-2845B QUAD DARLINGTON 1.5 A DRIVERS FEATURES ¢ : © Inputs Compatible with DTL, TTL, LSTTL, CMOS a wo o @ —50V Darlington Outputs c ~} IN © Current-Sink or Sink-and-Source Combination w Ape!) © 16-Pin Dual In-Line Plastic Package Bis “ ae "2S PAIR OF QUAD DARLINGTON switches © Ll oe A t is designed for high-current, high-voltage peripheral driver applications. They provide solu- ono Ley She s tions to interface problems involving electronic IN 110] ¢ discharge printers, d-c motor drive (bipolar or uni- : oY B. polar), telephone relays, PIN diodes, LEDs, and — other high-current loads operating with negative DWG, NO. A~10,3238 voltage supplies. ‘Type UDN-2841B is for current-sink applications in which the load is connected to ground. The out- puts switch the negative supply. The input PNP tran- Current Sink sistor in each driver serves as a level translator. The first NPN stage provides current gain to drive the & Darlington-pair outputs. -v = Type UDN-2845B is a current-sink, current- sess 09 source combination in a single dual in-line plastic package. It can be used in bipolar switching appli- : cations in which neither end of the load is at ground Current Source potential. Types UDN-2841 and UDN-2845B are intended 7 for use with 5 V TTL, Schottky TTL, DTL, and CMOS logic. Both drivers reduce component count, & lower system costs, and reduce circuit and board soe, kon complexity.

QUAD 1.5 DARLINGTON DRIVERS Lee ence ence cn el ABSOLUTE MAXIMUM RATINGS at +25°C Free-Air Temperature For Single Darlington Output (Unless Otherwise Noted) Output Voltage, Vocgry «eseecteeeccseeeeeessreeererteeersrssees SOV Output Sustaining Voltage, Versus) -----0ec0ereeeeeee ces eeeeeees esses es 36 Substrate Voltage, Vigp ..- see eeeeeseeeseeeseeeeeeeeeeeeeeeeeeees TOV Supply Voltage, Vy... 2. eee cece eect rete e ee ere teers eeereeceeee 1OV Power Dissipation, Pp (one output)... sc .seeeecseeeeeeeceseesee See Graph SCHEMATIC ALLOWABLE POWER DISSIPATION (Each Driver) AS A FUNCTION OF TEMPERATURE 5.0 WE Rs Los io =, CERO IN 40 3, z * » IN Ki As 1K 7.2 ¥ 4, 5 ue, Wo, Ae20,083¢ 2 30 IN Ne. 3! Ley

2 Nl i, a el

S20 S\\;, Resistor Values inkO 4 Nhs, | Amplifer1&3 | Amplifier 284 2 aa Te Number [Ry ORR g, SY UON-2841B 33 15 3301S <" Sa) upn-28458 | 3.3 15 33 L ) NOTE: The substrate terminals must be tied to the most negative point in rt tits the external circuit to maintain isolation between transistors and to 0 provide for normal device operation. 0 50 100 150 TEMPERATURE IN °C DWG. NO. A-10,488C 4-20

QUAD 1.5 A DARLINGTON DRIVERS A ELECTRICAL CHARACTERISTICS at T, = -+25°C (unless otherwise noted) nits Characteristic Symbol Test Conditions Min, Typ. Max. | Units | Output Leakage — | lea, Ve = —50V,Vy = O4V,T, = 25°C [== 10 | na _| Current Vee = —50V, Vy = O4V,T, = 70°C Output Sustaining | Veesm | Vee = —S0V, Vy = O4V, lay = 100mA 3 9 — | Vv Voltage Oxtput Saturation | Voce Voltage log: = 1.08 (Note 1) lor = 1.5A (Note 1) Vv Ion HA input Voltage Vaan lor = 154 a (Note 1) Supply Current I, lo = 500 mA, UDN-2841B, UDN-2845B (Note 2) [253.75 | mA_| (Note 1) lax = 500 mA, UDN-2845B (Note 3) [= 3375 | ma_| Ry = 380, 15Vy 100.5 Vay Ry = 390, 0.5V 10 0.5¥o NOTES, 1. Each driver tested separately, 2. Drivers 2 & 3 (sink drivers) only, V; = OV, Ve = —40V. 3. Drivers 2 & 4 (source drivers) only, Vj = 5Y, Ve = —40V. TEST CIRCUITS UDN-2841B UDN-2845B Vege“ Vege ov OG}, ee Bay fe": Lm ST ae th. Ais! * aE nr TI ¢ [KS F she be che = , os : _ o—{7 io} ; Al So A Vee = 40 = Vee* -4ov = Ow. Wo, Ae04aTa Dw. NO. ALO 484k 421

QUAD 1.5A DARLINGTON DRIVERS SS ALLOWABLE OUTPUT CURRENT AS A FUNCTION OF DUTY CYCLE WITHOUT HEAT SINK Ly i N NY —

2 Lo S Ss

54 = é z ay 20 0 0 Ey Too PERCENT DUTY CYCLE. ae me i003 WITH STAVER V-7 HEAT SINK ! mre oF a 0 ao EF 100 PERCENT DUTY eYCE seve umn 4—22

QUAD 1.5A DARLINGTON DRIVERS SS TYPICAL APPLICATIONS BIPOLAR MOTOR DRIVER UDN-28458 1} Oe oe ” “Th ia “200 12 INS kG. NO. #19, $868 ELECTROSENSITIVE PRINTER INTERFACE OO — anrecenosss = DIO BAS B59 39. 39 UDN-2841B woe pl | Dis. 10. #10, 5868 V atv 414

QUAD HIGH-CURRENT DARLINGTON SWITCHES SS UDN-2878W AND UDN-2879W QUAD HIGH-CURRENT DARLINGTON SWITCHES

FEATURES

© Output Currents to 4A © Output Voltages to 80V © Loads to 1280 W © TTL, DTL, or CMOS Compatibie Inputs Internal Clamp Diodes VY co V/ © Plastic Single In-Line Package [> “= Lal [A | | By C; GND C2 Ki2 Bz Bs Vs Cs Kya Cy By "THESE QUAD DARLINGTON ARRAYS are OB Ne RTE designed to serve as interface between low- level logic and peripheral power devices such as solenoids, motors, incandescent displays, heaters, and similar loads of up to 320 W per channel. Both economical Type UDN-2878W-2 and Type UDN- integrated circuits include transient-suppression 2879W-2 are recommended for applications requir- diodes that enable use with inductive loads. The ing load currents of 3 A or less. These less expensive input logic is compatible with most TTL, DTL, LS devices are identical to the basic parts except for the TTL, and 5 V CMOS logic. maximum allowable load-current rating. Type UDN-2878W and UDN-2879W 4A arrays For maximum power-handling capability, all driv- are identical except for output-voltage ratings. The ers are supplied in a 12-pin single in-line power-tab former is rated for operation to 50 V (35 V sustain- package. The tab is at ground potential and needs no ing), while the latter has a minimum output break- insulation, External heat sinks are usually required down rating of 80V (SOV. sustaining). The for proper operation of these devices. Output Sustaining Output Device Voltage Voltage Current UDN-2878W 50¥ 35Y 4A UDN-2878W-2 50V 35 3A UDN-2879W 80V 50¥ 4A UDN-2879W-2 Boy 50¥ 3A 4—25

QUAD HIGH-CURRENT DARLINGTON SWITCHES a ABSOLUTE MAXIMUM RATINGS at + 25°C Free-Air Temperature for any driver {unless otherwise noted) Output Current, |; (UDN-2878W & UDN-2879W) 2... css eee ne eee eee eee eee BOA (UDN-2878W-2 & UDN-2979W-2) 00.00. eee eee AOA Input Voltage, Vy... eee eee eee e terete eee e ete erences LEV Input Current, Iy so... eect tte eee es 25 mA, Supply Voitage, Ves... 000s ccccccceeeeeeeeeeeeeeeeeeeeeeeeeeee 1OV ALLOWABLE AVERAGE PACKAGE POWER DISSIPATION AS A FUNCTION OF TEMPERATURE | PARTIAL SCHEMATIC. Pay f 4 Dri 4 \\ One of rivers zZb r z 5, % s s, \\ 8 =z Go A = “i ‘ 9002 FA No \\ é » Xe 1 K Fy “4 2.5K

8 So, in bot ¢

3 @ IS H z Qa, A \\ zk i te s | ' 70k 2 sh 2 \\ z ~ en s \\ \\ pa 3K s, “AS See aN Dus. NO. &-12,037 Sos "3a 5 To sD TEMPERATURE IN °C vg, Wo, 811,798 4—2

QUAD HIGH-CURRENT DARLINGTON SWITCHES a ELECTRICAL CHARACTERISTICS at V, = 5.0V,1, = +25°C (unless otherwise noted) SCS ee ee Characteristic | Symbol | Fig. Devices Test Conditions [ Min, Max. [Units | Output Leakage Current | lex [i [woven Pet [Va= SOV. R= +700 = 500 | wk] UON-2679WAN-2 [Vos = BOVE 100 Tt Output Sustaining Veswon | 2 UDN-2878W¥N-2| I, = 100mA Vy = OAV [35 T [ioc |“)? nam tometer —— Ss =} Collector-Emitter Veesin | 2 [= S00maVy=275V | Od vi Saturation Voltage =e = 1s [k=30AW=275V fT = gs | Vv | [Uon-2e7er2e7OW] |. = 4ORVW=275V | — 28 | Vid a ae ee Vy = 3.75 pm (Seat see ey | SuepiyCurentperDrver|"I, [7 [al [i = 800m, 275V «| 60) ma | [ Turm-On Delay [ts [= [a P05 t005 Ops | Tun-oFF bey [te | — [A OSE, tOSE = BOA) 1S | ps | Clamp Diode ¥, = 50V UON-2679WA-2 [y= @OV 0 | Clamp Diode i a Ta Foard Yotae [YS Tarai t= tot ——— = CAUTION: High-current tests are pulse tests or require heat sinking, on Yee orn TEST FIGURES == ? ‘ oh, £ c Figure 1 Figure 2 4-27

QUAD HIGH-CURRENT DARLINGTON SWITCHES nS TYPICAL APPLICATIONS STEPPER-MOTOR DRIVER UDN-2878W V7 VW el lA LT rnin} pet +28V rely} OWG. NO. A~11,975 INPUT WAVEFORMS

7 SLE LAL

‘LILI LS » LILI LS PPLE LE op te. 88 429

QUAD HIGH-CURRENT DARLINGTON SWITCHES A TYPICAL APPLICATIONS UDN-2879W [ererd| PRINT-HAMMER DRIVER | rl TA anh Mgdadada teat gt UDN-2879W VY aD Y IGIT DRIVER FOR MULTIPLEXED INCANDESCENT LAMP DISPLAY lal TA aaa ULATLTLITE AM IN Ns “2 me te HH co a] A a 4—30

3-PHASE BRUSHLESS DC MOTOR DRIVERS eS UDN-2931B AND UDN-2931W 3-PHASE BRUSHLESS DC MOTOR DRIVERS FEATURES. Vsense aT G5 No © Output Current of 28 ute es, © Internal Transient-Suppression Diodes Nea si Sees © Low-Saturation Output Drivers Ne al '2 Rn) outs” © Anti-Crossover Protection Sa SI 4 NS Braking and Chopping Functions (UDN-29318) ‘GROUND mi Cerk GROUND © Thermal Shutdown with Hysteresis RAE ‘I CA © External Current-Sense Capability CHOP AS vee | He sine © Input Lockout Circuitry come. aNe Pl AH Ste oN a Ova Ne. Akan ‘The UDN-2931B/W 3-phase brushless de motor a CS) UDN-2931B driver is designed for low output saturation-voltage \\ \\ levels. These drivers maximize motor capacity lim- » ited by power supply constraints. The output drives, ~ Ve features low output saturation source and sink Griy \\ \\\\, ers and integral output suppression diodes<Thig ott, SN \\ W] puts are capable of maintaining an output BFF, Sw voltage of 15 V and an on cursgat of 2A (h3 Oo ie ig es peak). ANY “> [te “ Crossover current progetfigh nahen ingot po- nl ; acs rated to guard against eomation sink ariel sbufoatiriv- Oo a ers being on at the sam tiger Cifcuitry bo-the input A La structure has beeii ad Ikegut sink driver 11 i i i la id if i ia L i ld when both ative inpufs hav beeprdctivated atthe oes ees ass eew same time. \\ oe S8z2525 22 BERR qwe UD ese hay extended flexibility with $3 3°38 " 7 hoe ange ar tions. The cop function af- ° iSyhe’solirce diiver by switching it on and oFF oun nanrasa whi ng cuop is being toggled. In utilizing the UDN.2931W BRAK ftyeton the source drivers are turned on while thé-Snk drivers are tumed OFF. The BRAKING The UDN-2931B is supplied in a 16-pin dual in- input is active low. Crossover-current protection is line package with heat-sink contact tabs. This pack- still in operation during BRAKING. age allows for ease of circuit-board insertion. The Both devices feature a common-emitter pin on the UDN-2931W is supplied in a 12-pin single in-line sink drivers. The emitter-current sense is useful in power-tab package. These packages allow for easy chopper-mode configurations. Thermal shutdown in attachment of an external heat-sink for extended these devices has been set to 165°C. power dissipation capabilities. 431

3-PHASE BRUSHLESS DC MOTOR DRIVERS SS ABSOLUTE MAXIMUM RATINGS atT, = +25°C Motor Supply Voltage, Yon... sss cceseereeeeettteeeeeeeeeeertenerss IBV Output Current, bur (Peak)... vec eee cece eee eeeeeeeeeeeeeeeeees EBSA (0. SEES S2.1,) Input Vottage, Vyp..eee eevee cceeeeeeeeeeeeeereeeeeeeeeeeneress DOV Sense Voltage, Vepaes.- ++. cseeveeeereeeeeeeseeeseereeessceeeeeee LBV Package Power Dissipation, Pp Storage Temperature Range, Ts .. . - cece eee renee 755 to + 150°C “Derate atthe rate of 2.22 miW/PC above T, = + 25°C. **Derate at the ate of 41.16 mW/C above T, = +25°C. FUNCTIONAL BLOCK DIAGRAM & = = sens ‘TOD = TURN ON DELAY, TS « THERMAL suuroown No, A4.209, 422 ,

3-PHASE BRUSHLESS DC MOTOR DRIVERS named ELECTRICAL CHARACTERISTICS at Tys = +70°C. V,5 = 15V Characteristic ‘Symbol Conditions Min. Typ. Max. Units Output Leakage Current lex —_<-10 -100] pA a CC [Witorsiony otagemange [We OSC~d = 75 120 | m_| [lenp ied estageGurent |_| y= 16 : A lay = 2A L = Di 0% Day Ol =p 1, Thermal shutdown typically has a hysteresis of 15°C. TYPICAL APPLICATION [hes e 5 <UFE 3sx Te eT = [SOE KEP DP TD a a snod_” ES oS. A 10K ea INPUT eS Of a | AB Soi __DEOREES = Rss O1uF se soe—S LI L120 ca) fac ~as srzt LI Lieo “as 1s *° SB 300 TODTURN OW DELAY TS THERMAL SHUTDOWN 4-33

BIPOLAR HALF-BRIDGE MOTOR DRIVERS LEE ee ee al UDN-2935Z AND UDN-2950Z BIPOLAR HALF-BRIDGE MOTOR DRIVERS @ 3.54 Peak Output © 37 V Min, Output Breakdown © Output Transient Protection © Tri-State Qutputs © TTL, CMOS, PMOS, NMOS Compatible Inputs © Internal Thermal Shutdown C4 i C4 © High-Speed Chopper {to 100 xz) ATA] LV TN] © UDN-29352 Replaces SG3635P > > R © UDN-29502 Replaces UDN-29497, SN75605 Ny AN © 10-220 Style Packages BOTH Type UDN-2935Z and UDN-2950Z D | ‘ | | | | | integrated circuits are designed for servo- SEZ EF ¥52: & motor applications using pulse-width modulation. bese a8 3 8 These two high-current, monolithic half-bridge 5 & g ia motor drivers combine a sink-and-source driver Manos mesnte 5 cso. anane with diode transient protection, input gain, level UDN-2935Z UDN-2950Z shifting, logic stages, and a voltage regulator for sin- gle-supply operation. ‘The UDN-2935Z output goes high with an active times for the sink drivers. The motor drivers can be low input at pin 2; it is especially desirable in NMOS used in pairs for full-bridge operation, or as triplets microprocessor applications. The UDN-2950Z out- in three-phase brushless d-c motor-drive applica- put goes high with an active high input at pin 2; its tions. They can also be teamed with the Sprague inputs can be tied together for single-wire control. Electric UCN-4202A stepper motor translator/ The input circuitry of both devices is compatible driver for bipolar d-c stepper motor control with TTL and low-voltage CMOS, PMOS, and The motor drivers’ single-chip construction and NMOS logic. Both ICs have logic lockout (tri-state power-tab TO-220 package enable cost-effective output) that prevents source and sink drivers from and reliable system designs supported by excellent turning ON simultaneously, power-dissipation ratings, minimum size, and ease In typical applications, the chopper-drive mode is of installation; because the package's heat tab is at characterized by low power-dissipation levels, low ground potential, several devices can share a com- saturation voltages, and short chopper-storage mon heat sink without insulating hardware. 444

BIPOLAR HALF-BRIDGE MOTOR DRIVERS Ce es ABSOLUTE MAXIMUM RATINGS Supply Voltage Range, Vy... eee cece ee eee BOW 1035 Output Voltage Range, Vout ooo. e rece ceecce cee ee cece @2OVIO Ve +2.0¥ Input Voltage Range, Vy oo... eee eee cee ce ceeeevevecveses “O30 +70 Peak Output Current (100 ms, 10% d-0), lop. oe eee cece cece ee ees EBSA Continuous Output Current, ly... sees cece ceccececeeeeea ee vee 208 ALLOWABLE POWER DISSIPATION AS A FUNCTION OF AMBIENT TEMPERATURE » 7 ANGHLGn 4 | Es a ¥ Nig, Nee : ZZ X \\

2 Gy, i

Z| NY SO) : a NW | he. N 8s «one NX | | | ToteN a a ao AMBIENT TEMPERATURE, Ty, IN °C TRUTH TABLE Source Driver, Sink Drive, © ____Output, Ping Pin 2 Pin 5 UDN-29352 UDN-2950Z Low Low High Low Low High High HighZ . High Low Low High High High High Z High 4—35

BIPOLAR HALF-BRIDGE MOTOR DRIVERS BIPOLAR HALFBRIDGE MOTOR DRIVERS FUNCTIONAL BLOCK DIAGRAMS UDN-2935Z. Ons SOURCE inure © [> . C4 ai, © be 3) GROUND UDN-2950Z © +Vs SOURCE 21, oD {4 @ GROUND 4—36

BIPOLAR HALF-BRIDGE MOTOR DRIVERS Oe ELECTRICAL CHARACTERISTICS at T, = +25°C, Trp = +70°C, V, = 35'V (unless otherwise noted) Source Driver nput,Pin2 | sink Driver | Output, EE Characteristic UDN-29357 Input, Pin § Pind | Other_| Min, Max, | Units | Output Leakage Current | 24v [ogy fav ov = 500 [ak] 2aV gv [500 Tea O8io24V | 208 Output Saturation Voltage | oav [av av [-20a Ts | 2av [ogy TP ogy on Po Output Souroe Current pay [aay Tay a Output Sink Current [| 24v [aay | oy Po [ Input Open-CircuitVortage | 250uA | —250uA | — 250A | — | 7s Tv ‘nput Current po — | aay [aay nc = 70 ea | osv [av oav nc | te Tm Propagation Delay ogw2av | 20a [ — [= 750 Tas 2.4t008¥ gay | zon | = [20 Tas | Clamp Diode Forward Voltage Ne 208 no | — | — 35 ma NOTE: Positive (negative) current is defined as going into {coming out of) the specified device pin. TEST FIGURE 1 TEST FIGURE 2 | 4) +E Opt f|4 fla TI Vs

6 O p-2av

veto. A-12,297 4—37

BIPOLAR HALF-BRIDGE MOTOR DRIVERS a APPLICATION NOTES It should be noted that an additional power dissipation component may arise from crossover currents flowing from supply to ground when current direction through the load is reversed. This is due to differences in the switching speeds between the source and sink drivers. Although the inter- nal logic lockout protects these devices from catastrophic failure, the crossover power component can cause device operation at substantially higher junction temperatures. If timing conditions are ignored, the magnitude of this power can be approximated as: Pp=VsX lox txf where Vs = supply voltage Ie = crossover current (= 3.5.A max.) 1 = crossover current duration (~ I us) f = frequency of direction change In some applications (high switching speeds or high package power dis- sipation), it is recommended that the inputs be driven separately, and that the sink driver not be turned ON for at least 2 4s (maximum source typ) after the source driver input is turned OFF. The sink driver should be turned OFF at least 750 ns (maximum sink tp) before the source driver is turned ON. RECOMMENDED TIMING CONDITIONS (UDN-2950Z shown) DIRECTION Ne >750 ns [+> 750 ns fe > 2us ke ens SPEED (PWN V5 | | | +. Ey = <-2h agua, 412120 SOURCE INPUT, rr SINK ad tps be 4] 50 as INPUT, s— a ong. 12409 4—38

BIPOLAR HALF-BRIDGE MOTOR DRIVERS a iieeinestechaeniidletahlatd TYPICAL APPLICATIONS 3-PHASE BRUSHLESS DC MOTOR DRIVE

7400 UON-29507 ON-29507, UON-29507

ram! aru 0 *5V a oO =F fe] kl & i a Siam ht Mn UgN-20307 aa i re 21 sense U] —— as 7 oe oS eo ‘UGN-3030T Tso ay ail Sia Oe ced 4 SINGLE-WINDING DC FULL-BRIDGE DC OR STEPPER MOTOR DRIVE SERVO MOTOR DRIVE UDN-2935Z UDN-2950Z K 3 F 5, C4 7 nN i rh k 5, | a le NTT binecTiON © gine, Aet2,tt4 oiRectiON © eae S BBo 4—39

UDN-2936W AND UDN-2937W : 3-PHASE BRUSHLESS DC MOTOR DRIVERS Leena ee eee ee el UDN-2936W AND UDN-2937W ' 3-PHASE BRUSHLESS DC MOTOR CONTROLLERS = tht Opt LO 20] = 4APeak Output Current @ Internal Clamp Diodes « internal PWM Current Control © 60° Commutation Decoding Logic COMMIETITION ‘© Thermal Shutdown Protection . © Compatible ith Single-Ended or biferenal al let ers Y vy AAA Vos Y ‘© Braking and Direction Control (UDN-2936W Only) | I i j 1 | I i i ! | Combining logic and power, the UDN-2936W and the ,zseoee a UDN-2937W provide commutation and drive for a three- 23 ge3 get £38 phase brushless de motor. Each of the three push-pull g & 8 2. 8 outputs are rated at 45,V and +3 (4A peak), and 5 j have internal ground clamp and flyback power diodes. UDN-2936W Dwg. No. WB These drivers also feature internal commutation logic, f PWM current control, and thermal shutdown protection. The UDN-2936W is compatible with single-ended digital or linear Hall effect sensors. The commutating logic is programmed for 60° electrical separation (other separation sequences, such as 120°, are available via mask programming at the factory). Current control is accom- plished by sensing current through an external sense LOGIC resistor and pulse-width modulating the source drivers. Voltage thresholds and hysteresis can be externally set V vV.AAA Y by the user. If desired, internal threshold and hysteresis defaults (300 mV, 7.5 percent) can be used. The UDN- i i k J i i i l i l tI 2936W also features braking and direction control. weeee eyes We ane eexzrertitiza sy Internal protection circuitry prevents crossover current s 2ak 1+ ttt = Be when braking or changing direction. g 3 & ‘The UDN-2937W is compatible with linear differential UDN-2937W wa. No. wrt69 buffered and unbuffered Hall effect sensors. By changing sensor output polarities, various commutation sequences, For maximum power-handling capability, the UDN- such as 60°, 120°, or 240°, can be set. The PWM current 2936W and UDN-2937W are supplied in 12-pin single control threshold and hysteresis is set at 300 mV and 7.5 in-line power tab packages. An external heat sink may percent. The peak output current is determined by a user- be required for high-current applications. The tab is at selected external sense resistor. ground potential and needs no insulation. 4-40

3-PHASE BRUSHLESS DC MOTOR DRIVERS Ln ABSOLUTE MAXIMUM RATINGS at Tis = +70°C Input Voltage Range, Vin ....secsssssssesscssssersvinsesseesnseneessensves —03¥t0 15¥ Package Power Dissigation, Pp ....esccccsssscsssesevsssssssenvevvenennessssesess $886P@ph Operating Temperature Range, Tk vesessssssssssssssmsesssssisesseeecees —20°CtO + 85°C Storage Temperature Range, Ts ...ccccsecsesssssssrssrsmumnseneees 55°Ct0 + 180°C NOTE: Output current rating may be limited by duty cycle, ambient temperature, and heat sinking, Under anysetof conditions, donot exceed the specified peak current anda junction temperature of + 150°C. FUNCTIONAL BLOCK DIAGRAM UDN-2936W @voe sev ——— ‘ep fe Sem. asv—b © op pte He PY z ++) < lp | TED SEs me= 2a iy 8°" 8 | pe ES |’ r +) > PD @, DIRECTION Ai 4 Rs 4 ths fax R%feiom pan 8! } | © aay ‘ia ores JeROUND } of Dg. No, vet80 COMMUTATION TRUTH TABLE UDN-2936W Tal sensors He He Hs Direction Brake _——OUTa._—<OUTs OUT fhe Hs irection Brake OUTs OUT OUT. High High High Low Hign low High High High Low Low High High «= bow Z High Low Low Low High = High SZ Low low Low Low Low Hign Z High Low low Low Hign Low Hign = Low High «7 low High Hin Low igh Low High High High High High Hin 2 High Low High High Low High hizo = Low High ign Low Low High High Low Z High tow Low Low High ign = Z low High low Low High High Hign = High Low Z low High High High high High, Z Low x x x x low tow Low Low X= Teeent — SS 1 = High Impedance 441

3-PHASE BRUSHLESS DC MOTOR DRIVERS i FUNCTIONAL BLOCK DIAGRAM UDN-2937W @Vos 4,60 2 —< 7 “ep ET TRL his iCeFP 1 pK! Ob ® pi) én fre GROUND [ sort t bon te COMMUTATION TRUTH TABLE UDN-2937W Hall Sensor [nputs* Outputs +H +Hz +Hs OUTS OUTs OUTe High High High 1 Low High igh High Low High Low Z igh Low Low High 1 Low Low Low Low 1 High Low Low Low High Low igh z Low High High Low 2 High * Inputs are with respect to — Hx inputs. 7 = High Impedance TYPICAL HALL EFFECT SENSOR LOCATIONS. / x r a s i X~ LAS &— ON a, wg news 4-42

3-PHASE BRUSHLESS DC MOTOR DRIVERS A ELECTRICAL CHARACTERISTICS at Ta = + 25°C, Trap < 70°C, Vas = 45V [tinits Characteristic Symbol | Test Conditions Supply Current Tes Outputs Open Vanaxe = 0.8¥, UDN-2936W Onl Output Drivers lex [Vout = Vos Vour = OV Output Saturation Voltage Vos san [GutputSustaningVottage [Veen [lor = 3A4L= 2H CBS SOC] (CY | Clamp DiodeLeckage Curent [te [Ve=45V = 50] pa] Output Switching Time lour = = 2A, Resistive Load [= 20 Ts | lout = = 2A, Resistive Load = 20 =| ps _| Turn-ON Delay ten = 125 = [wearer | | Sink Drivers, Oto + 2A Ss ee | 4 edit Tew [Source Drivers, —2Atoo Po 7 Tas] [Resisowe Load) [SinkDrivers, -2AtoO gs | UDN-2936W Control Logic [Viwo» [VororVerxe CY [ SensorInputVoltge Threstold [Vv [Hn,Haors dT CC Input Curent Niwa [Vom = 2V 150200 Wanaxe = V5. Irs [Vrs <3.0¥ Vsense> Vrs. | 20060 | pA [Curent LinitThreshold T Wrus/Veenseattrip point, Vus<3.0V |B io 05 [| 270 300-330 | DetauitHysteresis [as 3.07 _ BRAKE or DIRECTION = 20 = UDN-2937'W Control Logic [eptcomoreapengs/ Mex [gg eT Input Voltage Hysteresis a ( [nputGurrent Tw [WV COC OU | [SenseTripVottage Veewse | SSC«d OCS [Histeresis 443

3-PHASE BRUSHLESS DC MOTOR DRIVERS Sl APPLICATIONS INFORMATION The UDN-2936 and UDN-2937W power drivers provide 3.0, the trip point is internally set at 300 mV with 7.5 commutation logic and power outputs to drive a three- percent hysteresis. Load current is then determined by phase brushless DC motor. the equation: Tmax = 0.3/Rs UDN-2936W With Vrs < 3.0, the threshold, hysteresis per- The UDN-2936W is designed to interface with single- centage, and peak current are set with external reisistors ended linear or digital Hall effect devices (HEDs). according to the equations: Internal pull-up resistors on the UDN-2936W inputs Threshold Voltage (Vrs) = Vrer*Rr/(Ru + Rx) allow for direct use with open-collector digital HEDs. Hysteresis Percentage = Ru/50 Vrer ‘The Hy inputs have 2.5 V thresholds. Load Trip Current (Imax) = Vrus/(10Rs) ‘The commutation logic provides decoding for HEDs Percentage hysteresis is a fixed value independent of with 60° electrical separation (other separations available load current. The chopping frequency is a function of via mask programming). Atany one step in the sequenc- circuit parameters including load inductance, load resis- ing, one half-bridge driver is sourcing, one driver is tance, supply voltage, hysteresis, and switching speed sinking, and one driver is in a high-impedance state (see of the drivers truth table). Changing the logic level of the DIRECTION pin inverts the output states, thus reversing the direction UDN-2937W of the motor. A logic low on the BRAKE pin turns ON all The inputs of the UDN-2937W are designed to interface three sink drivers and turns oFF al] source drivers, directly with the outputs of differential buffered or dynamically braking the motor. An internally-generated unbuffered HEDs. Various commutation sequences (60°, dead time (ta) of about 2 js prevents potentially destruc- 120°, 240°) can be set by using appropriate HED output tive crossover currents that can occur when changing polarities shown in the truth table. direction or braking. In some high supply voltage appli- ‘The UDN-2937W load current control circuitry works cations, it may be necessary to brake the motor before the same as in the UDN-2936W except that only the changing direction. internal threshold and hysteresis settings can be used. Motor current is internally controlled by pulse-width With the threshold of 300 mv and hysteresis of 7.5 per- modulating the source drivers with a preset hysteresis cent, load current is determined by: format. Load current through an external sense resistor Imax = 0.3/Rs (Rs) is constantly monitored. When the current reaches Both the UDN-2936W and UDN-2937W outputs are the set trip point (determined by an external reference rated for normal operating currents of up to 3A and start- voltage or internal default), the source driver is disabled. up currents to4 A. Internal power ground clamp and fly- Current recirculates through the ground clamp diode, back diodes protect the outputs from the voltage transients motor winding, and sink driver. An internal constant- that occur when switching inductive loads. Both devices current sink reduces the trip point (hysteresis). When the also feature thermal protection circuitry. If the junction decaying current reaches this lower threshold, the source temperature reaches 165°C, the thermal shutdown cir driver is enabled again and the cycle repeats. cuitry turns OFF all output drivers. The outputs are re- Thresholds and hysteresis can be set with external enabled when the junction cools down to approximately resistors or internal defaults can be used. With Vins > 140°C. 444

3-PHASE BRUSHLESS DC MOTOR DRIVERS eens UDN-2936W_ TYPICAL APPLICATION lO Oo] LOGIC. Wie ieee as yey SHALL EFFECT O10 csv SENSORS rake4® 7 NSE es ALLOWABLE AVERAGE PACKAGE POWER DISSIPATION AS A FUNCTION OF TEMPERATURE a \\ iy N S S ¥, a an 5 19 . \\

3 Ne, oR

2 sh dg) “1 27S, SS VS Z 7 °F Ei 75 100 [ry 150 TEMPERATURE |N °C: ne i SATO 4—45

3-PHASE BRUSHLESS DC MOTOR DRIVERS SS UDN-2938W AND UDN-2939B 3-PHASE UNIPOLAR BRUSHLESS DC MOTOR DRIVERS FEATURES et as © Output Voltage of 30 one ce | oeior, \\SS © Output Current of 4A pase, | ¢] RR : © integral Transient-Suppression Diodes ad eee “ay © External Output Driver Capacitor Pins aR oUn> [Sony [28 hark] OnStar © Thermal Shutdown Circuitry nec i rT yee © TIL, DTL, CMOS Compatible Inputs ING mT INa NY ‘Ya Sy ease _ NN, ‘ The UDN-2938W and UDN-2939B are three- CREA in ag No. A88 phase unipolar brushless de motor drivers capable ON SR Suen 29898 of handling 4A drive currents, anovtputorF voltage i of 50 V, and a sustaining voltage of 30V. The output {\\ M “J My drive structure of these devices have been designed, “W%.*Sy 1S) O for low saturation voltages (less than 1.0V at fads \\ WS NM UDN-2938W and UDN-2939B are function ib Yay tical except that the UDN-2939B has ENaBg tapud \\YS. for extended control flexibility. The bases of thigobt- ‘ ~ put drivers have been brought ok tOgxternal pindsds, that capacitors may be canta dager to sign V| Y | LY late anac drive and toprGie'EM}an aPiproblems. aa Output transient-subprbssi6p diodes haye’been in- ial |] lel Ll lal corporated Tape Hh ei ups Inputs are 28seeeerrerss active high"and AGyBow The Seedfiputs are TTL, 3° 8 e38ege3° DIL, and SYNBY EMDR iBatible. The ENABLE & ees type Na is*active high and, when “Se THERMAL SHUTOOWN n,n. vase ) pinetiodas BLOCK DIAGRAM UDN-2938W \\ \\ vec VK pulled low, will turn oF all output drivers. These wis] devices have thermal shutdown circuitry with hys- F| | terisis to guard against overheating. This thermal INAo => © OUTA shutdown circuitry is designed to operate at a tem- perature of 165°C. A logic supply current regulator has been introduced into these devices to maintain a INg o-fosie > 0 0UTa relatively constant output base drive over the logic supply (Vec) operating range. Neo > o oun The UDN-2938W is packaged in a single in-line c 12-pin power-tab SIP package with lead centers at b sasce 0.100 inches. The UDN-2939B is packaged in a 16- O BASES pin dual in-line batwing package with heat-sink con- OBASEa 52 THERMAL SHUTOOWN tact tabs. wg No. 45 446

3-PHASE BRUSHLESS DC MOTOR DRIVERS SS ABSOLUTE MAXIMUM RATINGS TYPICAL APPLICATION at + 25°C tov, Output Voltage, Vee eee eveceeeeeeecseeeeseee SOV 30N Output Sustaining Voltage, Versus --- ++ +e eeeeeeees 3OV ‘| Output Current, br .eesesessecsvesseeseeceseeee BA INKO > Logie Supply, Veg esse seeseseuseeeeeeeeeeeee IBV RL Input Voltage, Vie. cece eeeeseeeeee sess IBV Le Package Power Dissipation, Pp Neo ch, (BPACKABE) eee cece eceeee cee RITWE *Derate at the rate of 41.16 mW/°C aboveT, = +25°C. Ca, Ce TS= THERMAL SHUTOOWN **Derate at the rate of 22.22 mW/°C above T, = + 25°C. tpr = Dwg. No. A14,193. ELECTRICAL CHARACTERISTICS at T, = + 25°C, Vcc = 5.0V (Unless otherwise noted) Characteristic Test Conditions Logi Suppy Voltage Range A Output Leakage Current [tx | Yor = 50 — <0 (100 Output Saturation Voltage Versi lar = 108 = 09 Ll log = 4.0 = 19 20 Clamp Diode Leakage Current a Clamp Diode Forward Voltage Input Voltage v au ee Input Curent hey Va = 24¥ a ee ee Supply Curent | beow | One Diver ON Notoad [1S |oma | [boon | alive fF | 50m Thermal Shutdown Temperature a 165 = °c 447

QUAD HIGH-CURRENT SOURCE DRIVER SS UDN-2941B QUAD HIGH-CURRENT SOURCE DRIVER outs C1} 116] OUTD © 1.5. Output Source Curent | } a © Minimized Saturation Voltage Vsa a ig Vso © 30 Output Sustaining Voltage Na {ia} IN © Transient-Protected Outputs © TTL or CMOS Compatible Inputs GROUND ae cI GROUND Plastic Dual In-Line Package GROUND GROUND With Heat-Sink Contact Tabs NB = Ce INe Vea \\7 \\ AHI vec F'SH-CURRENT SOURCE DRIVERS are de- our, | \\ a signed to serve as interface between low-level se ge OTe logic and a variety of peripheral power loads, in- Dep. Nos Ael2 58 cluding solenoids, d-c or stepper motors using pulse-width modulation, and multiplexed LED or maximum power dissipation with standard cooling incandescent displays. methods. It fits a standard IC socket or printed wir- The UDN-2941B high-current source driver has _ing board layout. The heat sink is at ground potential four independent emitter-follower drivers. Special and needs no insulation. circuit design techniques, resulting in reduced Similar devices, for operation with load currents output-saturation voltages, allow any one driver of up to —500 mA, are the 8-channel source drivers to source up to —1.5A continuously with minimal _ of Series UDN-2980A. voltage drops and package power dissipation. The device’s high switching speed prevents ABSOLUTE MAXIMUM RATINGS plexed displays. All outputs are rated for operation Peak Output Current, lyre ++ vv veeeeeeereee res 7208 to 35 V (30'V sustaining). The low-level inputs are Input Voltage, Vv vv eveeeeee cece eens 15V compatible with most TTL, DTL, LSTTL, and low- Package Power Dissipation, Py... seve» See Graph The UDN-2941B integrated circuit is supplied in a SUa6e Temperature Te»... oe sink contact tabs. The lead configuration facilitates of conditions, do nol exceed the —2.0 peak curent and a junction attachment of an inexpensive external heat sink for — temperature of + 150°C. 448

QUAD HIGH-CURRENT SOURCE DRIVER SS PARTIAL SCHEMATIC ALLOWABLE AVERAGE PACKAGE POWER DISSIPATION One of 4 Drivers AS A FUNCTION OF TEMPERATURE NA a BIN =. NG IN 5 ee 3 "aS Drasee |, O ‘Av12,515 : a “Ses es aN a a rs a a TEMPERATURE IN °C Dwg. No. Act 7088, ELECTRICAL CHARACTERISTICS at T, = +25°C, V; = 35V, Tus = +70°C Characteristic Symbol Test Conditions Min. Typ. Max Output Leakage Current lex Wy = OAV, Voor = 0V,T, = +25 = <= 10 = 100 Ta Vu = 0.8V Vor = OV,T, = +70 = <=10 500 | yA Output Sustaining Voltage Vu = 24, lay = —100 mA on -— = Output Saturation Voitage Veesm | Yo = 24V, lon = — 108 — 13.15 i= 2A = =15A [Sis is Input Current [tow | Yu = 24¥ — 15500 Output Source Current [lar | Y= 24V “0 A Total Supply Current Vu. = 2.4 (Note 3), Outputs Open = [oma Clamp Diode Leakage Current Wy = 35¥ — <0 100 [ pa Clamp Diode Forward Current = 15a = i420 Turn-On Delay 0.5 Vi, t0 0.5 Vaq, Resistive Load — 08 25 bs Tum-Off Delay tee 0.5 Vg to 0.5 Vay, Resistive Load — 05 50 | us NOTES: 1. Each driver tested separately. 2. Negative current is defined as coming out of (sourcing) the specified device pin. 3, All inputs simultaneously. 44g

QUAD HIGH-CURRENT SOURCE DRIVER TYPICAL APPLICATIONS MULTIPLEXED COMMON-ANODE LED DISPLAY DRIVER +*12V +12V Ps) DIGIT DRIVER fe SEGMENT DRIVER UDN-2941B ULN-2003A . —--4 a ose) wt A sas) See co 7 og ona Ts] | og i oo} {>o 13} on HE ee | eu Te A ne 3 oP oe} pit ot on ie! a OF eS aY \\_E a Lt EA ---4 cA FULL-BRIDGE MOTOR DRIVER {One of 2 Windings) +28V +5V s 3 Na © ULN-2068B UDN-2941B i ULN-2069B Gls Shall] (ball hal? “bel b bel" phe aa vv <| TA RAL cA AAU ee Tt Lr err F 7 q INBO 7 4—50

HIGH-CURRENT HALF-BRIDGE MOTOR DRIVER UDN-2943Z HIGH-CURRENT BIPOLAR HALF-BRIDGE MOTOR DRIVER © =1A Output Current ; ~\\ © 8.5V to 24 V Operating Range fn © Withstand 45 V Supply Transients Pa. NY © Crossover-Current Protected Le™ |) Me © Logic-Compatible Inputs. an © Saturated Output Drivers (4 > © Output Transient Protection ds " © Tri-State Output <a © Internal Thermal Shutdown rae ait > i © Internal Over-Voltage Protection ‘SN Cy A © Internal Short-Circuit Protection on. \\ 7. © High-Speed Chopper (to 50 kHz) “ Ye M We © 10-220 Style Package mn ws ~~ ™ { a ‘y, Lt [DESIGNED for use as a general-purpose motor \\ “ ‘ SS FERES driver, the UDN-2943Z half-bridge driver com", WY \\ ‘> eee Re bines high-current sink and source drivers WBE \\ \\, #5 3k stages, level shifting, diode transient protectign) ch ~ \\, v g a a voltage regulator for single-supply operatio’y, Ca- ~ ed 8 pable of operating in extremely apsenvironme aN, we wo to. this device can withstand high ainbient tempera > tures, output overloads, andTepeatel ver supbly transient voltages withtit,damage, TI drideyeean short-circuit protection, activated at load currents be used in pairs for fall bridlgo“operat for as above 1 A, protects the source driver from acciden- triplets in thespefhgsh Dshless i photor driver tal short-circuits between the output and ground. rotenone’ aan \\ wae The UDN-2943Z driver is rated for continuous op- The input dire it decoingaile with TTL, low- eration with inductive loads at supply voltages of up Se 6zic. Logic lockout pre~ to 24V. With the application of increased supply Geico sgurcevantd, sink drivers from turning ON voltages (to 45 V maximum), a high-voltage protec- a ean Eatif driver is tured ow by an ac- tive circuit becomes operative, shutting orF both tive-lqw (put, making the UDN-2943Z especially output drivers. The internal thermal shutdown is desiraBig ty many microprocessor applications, An triggered by a nominal junction temperature of accidentaf'input open circuit will turn OFF the cor- 160°C. responding output. The device also provides an in- Single-chip construction and a modified 5-lead ternally-generated dead-time to prevent crossover JEDEC power-tab Style TO-220 plastic package currents during output switching. Monolithic, provide cost-effective and reliable systems designs. space-saving construction offers reliability unob- It also features excellent power dissipation ratings, tainable with discrete components. minimum size, and ease of installation. The heat- Saturated output drivers provide for low satura- sink tab is at ground potential and does not require tion voltage at the maximum rated current. Internal insulation. 4—51

HIGH-CURRENT HALF-BRIDGE MOTOR DRIVER aS ALLOWABLE POWER DISSIPATION AS A FUNCTION OF AMBIENT TEMPERATURE Ey v ABSOLUTE MAXIMUM RATINGS . Output Voltage, Veriu <-0e0eceveeeeeeereereees 24V 2a Continuous Output Current, lyr vo e+e eeeeeeeeeee BLOA ek Ke nw “Internal high-voltage shutdown above 26 V. BMPS oN : | Set S, \\ LOGIC TRUTH TABLE 3 |_| RAL | Source Driver, Sink Driver, Output, é | . \\ Pin 2 Pin 5 Pin 4 _ ake SAI Low Low High [22 a. ey BR Low High High t NX High Low Low ~~. IN High High HighZ °9 3 30 3 100 ey cy AMBIENT TEMPERATURE IN °C. ag. Ne 2.008 FUNCTIONAL BLOCK DIAGRAM Me SENSE “ VIA aav ROUND Deg. Ne 8 4—82

HIGH-CURRENT HALF-BRIDGE MOTOR DRIVER a EE _ eel ELECTRICAL CHARACTERISTICS at T, = +25°C, Tys = 70°C, V, = 24 V (unless otherwise noted) Source Driver | Sink Driver | Outpui oman | aa | | Sms | 98% | oe Fs ip a Ta ne ee [| 2av [aay [av [ — [ot | pa | ee ee | ast2av | aay [19a [figs | 2 Tv a | 2av | oav [oa [ — [oso Tv | Shot-cieuit SouceGurent [iz [aay | 2av [| ov [| — [ou is Ta | Di. = a a a Input Curt J | 2av [ zav [one [fo t00 Ta | |» | osv [nay [ne [P50 180 ua | Clamp Diode ForwardVotage | vp | nc | nc | 0a | rg [ — 15 0 | Lege Supply Curent Bip we [se | zavToav |e [Tso [osv [av Tue [sas a | Thermal Shutdown Temperatue [| — [Pte | 4 | | Overvotagestutdown [yf TT og Pronagation Delay ts ws [ 2einosv | 2av | -19a| figs | — 06 10 | us Loedtime TTT Tt as NOTE: Positive (negative) current is Gefined as going into (coming out of) the specified device pin, INPUT vy SINK INPUT v5 oureuT aa “ag POT pats rat Dg. No. A137 4—53

HIGH-CURRENT HALF-BRIDGE MOTOR DRIVER HOR-CORRENT MALE-IDGE MOTOR DRIVER

7 A 7 7

“TA cia [A 2 4 5 1 3 4 Ve Ve | f if NC NG NC y atin avm =, y 24v Dap. Ne. An4st0 FIGURE 1A FIGURE 1B FIGURE 2 7 7 clA (iA 3 4 2 3 6a 4 4 4 2av = ain an | dav Jour Dwg No. 14,142 FIGURE 3 FIGURE 4 4—54

QUAD HIGH-CURRENT, HIGH-VOLTAGE SOURCE DRIVER a UDN-2944W QUAD HIGH-CURRENT, HIGH-VOLTAGE SOURCE DRIVER © Output Current to 4A © Output Voltage to 60V * Loads to 960W * Integral Output Suppression Diodes TTL and CMOS Compatiole Inputs Cs * Plastic Single In-Line Package Heat-Sink Tab QO ‘ay “a a) om | ig ay a ose es see ye ee ee & = a Capable of driving loads to 4A at supply volt- i Brn Ro, IS 58 ages to 60V (inductive loads to 35V), the UDN- 2944W is a quad high-curent, high-voltage source driver. Each of the four power drivers can inline, power-tab package that allows efficient provide Space- and cost-saving interface between attachment of an external heat sink for maximum low-level signal-processing circuits and high- allowable package power dissipation. An exter- Power loads in harsh environments. nal heat sink is usually required for proper opera- tion of this device. The tab is at ground potential Individual supply lines have been provided for and needs no inculation each pair of drivers so that different supplies can be used to drive multiple loads. The controlling inputs are TTL or GMOS compatible. The outputs ABSOLUTE MAXIMUM RATINGS include transient-suppression diodes for induc- at + 25°C Free-Air Temperature tive loads. This quad Darlington array is designed to serve Output Current, ly: (DC)... eevee teense eee MOA as an interface between low-level circuitry and (Peak)... eee SBA peripheral-power loads such as solenoids, Input Voltage, Vij eee. ve eee eeeeee eens IV quad 4A sink driver. Outout current rating willbe limited by ambient temperature, duty cycle, heat sinking, air flow, and number of outputs conducting. Under any set For maximum power-handling capability, the of conditions, do not exceed the —5.0 peak current and aluncton UDN-2944W driver is supplied in a 12-pin single temperature of + 150°C. 4—55

QUAD HIGH-CURRENT, HIGH-VOLTAGE SOURCE DRIVER See eee eee ee ence nee el PARTIAL SCHEMATIC On Vs nes. | To omen InPuT STAGES 105 1m, | ou euapue ETE LOM oe a V 136 De Ne. 19.058 Ld ALLOWABLE AVERAGE PACKAGE POWER DISSIPATION AS A FUNCTION OF TEMPERATURE Fy | NOTE: Pin 3 must be connected to Vs for g \\ operation of input logic gates. FS a ‘es iN AL Fs a ‘ z <s \\

3 Xe A

2 Ne, mh TRUTH TABLE

g ey anit — : Se wy Input Enable Output 2 ob | Ss.) —— & a, Soy ‘ L L L Z Seca PAY H U H oa a AN L H L Mean H 4 L Sa Ts TEMPERATURE IN °C wg. No, A.78¢8 4—56

QUAD HIGH-CURRENT, HIGH-VOLTAGE SOURCE DRIVER ELECTRICAL CHARACTERISTICS at T, = +25°C, Trap <70°C, Vs = GOV, Venasie = OV (unless otherwise noted) Characteristic Test Conditions [ Min. Max. | Units | | wr spiesew f= a Output Sustaining Voltage fur = —4A, L = Omi fs - |v | [eo | Westewas ——P= ae Logic 0 | Ving) OF Veusea = 0.8V a NOTE: Negative current is defined as coming out of (sourcing) the device being tested. | O O QU] a TYPICAL APPLICATION Q ay aa) 0 QUAD RELAY DRIVE n r Using 2 Voltage Sources Taal oT | and Optional PWM Current Limiting ULE e2ey av = ~— °INe Nao ‘ Ff Ce pee, en oe ee ae bg = 05/Tour imax} 30S 457

UDN-2948W . QUAD HIGH-CURRENT, HIGH-VOLTAGE SOURCE DRIVER cn UDN-2948W QUAD HIGH-CURRENT, HIGH-VOLTAGE SOURCE DRIVER © Output Current to 6 A per Channel © Output Voltage to 60 V O OC j * integral Output Suppression Diodes * TTL and CMOS Compatible Inputs Plastic Single In-Line package . © Heat Sink Tab | ‘7 ‘i /s Y a) mim i te gig ergs? bg Fe 3 3 $8 3 3 2 3 3 p °? ee wg. No. 13.955, Providing space and cost-saving interface be- troublesome transients and noise currents on tween microprocessor/LSI circuits and high-power common logic/load ground lines. In addition, high peripheral loads such as solenoids, dc or stepper ground currents produce IR drops that can shift motors, incandescent displays, heaters, and the ground rail, affecting logic input levels, similar loads, the UDN-2948W quad high-current, thresholds, and noise immunity. The use of source high-voltage source driver can drive loads to -6 A drivers can minimize many of these concerns by at supply voltages to 60 V (inductive loads to separating the logic and power returns. 35 V). The low-level inputs are TTL or CMOS com- patible. The outputs include transient-suppression For maximum allowable package power diodes for inductive loads. Individual supply lines capability, the UDN-2948W driver is supplied in are provided for each pair of drivers so that dif- a 12-pin single in-line, power-tab package that ferent supplies can be used to drive multiple loads. allows efficient attachment of an external heat sink. The external heat sink is usually required for The application of source drivers for X-Y ad- proper operation of this device. The heat sink tab dressing of multiplexed power loads are obvious. is at ground potential and needs no insulation. Amore subtle advantage of high-current source drivers is with inductive loads or incandescent Similar 4 A devices with an input ENABLE con- lamps. Both types of load normally generate trol are supplied as the UDN-2944W. 458 :

QUAD HIGH-CURRENT, HIGH-VOLTAGE SOURCE DRIVER A FUNCTIONAL BLOCK DIAGRAM | (ONE OF FOUR DRIVERS) OM an ~ 10K Ny © a eon GROUND ah veg No, A18,058, ALLOWABLE AVERAGE PACKAGE POWER DISSIPATION | 4 AS A FUNCTION OF TEMPERATURE F ABSOLUTE MAXIMUM RATINGS at + 25°C Fres-Air Temperature . \\ Output Current, lpr (dc). 2 BA = 5. ~ (Beak) 7A 2 \\“, 12 Operating Temperature Range, T, ....—20°C to +85°C

2 NZ _—_—

a ‘ "Derate at the rate of 41.6 mW/°C above Ty = +25°C.

3 Me OY Output current rating will be limited by ambient

8 Ko, r temperature, duty cycle, heat sinking, air flow,

2 So aah and number of outputs conducting. Under any 3 i | NLA set of conditions, do not exceed the —7.0A peak = ; 2 4p Se, ‘ current and a junction temperature of + 150°C. z en [Sy wh “s, “A AN ee! % 0 5 10 1 BO TEMPERATURE IN °C wg. No. £3,794 4—59

QUAD HIGH-CURRENT, HIGH-VOLTAGE SOURCE DRIVER EEE, ELECTRICAL CHARACTERISTICS at T, = +25°C, Trg < 70°C, Vs = 60V, (unless otherwise noted) Characteristic symbol Test Conditions [ Min, Max. | Units _| ‘Output Leakage Current [lex _[ Vor = OV. Vy = 04V [-% [oa | Output Sustaining Voltage lor = -6A,L = 3mH fs -— | v | [Won f[ fT a Total Supply Current |__| One Driver ON, All Outputs Open f- 48 | ma | [cane se nies coree |b [wee T= | NOTE: Negative current is defined as coming out of (sourcing) the device being tested. APPLICATION NOTES Power-tab packages are efficient thermal dissipators when properly utilized. In application, the following precautions should be taken: 4. Always fasten the tab to the heat sink before the leads are soldered to fixed terminals. 2, Use appropriate hardware including a lock washer or torque washer. 3. Thermal grease (Dow Corning 340 or equivalent) should always be used. 4. Mounting torque should be between 4 and 8 inch pounds (0.45 to 0.90 Nm.) 5. The mounting hole should be as clean as possible with no burrs or ridges. 6. The mounting surface should be flat to within 0.002 inch/inch (0.05 mmimm). 7. Strain relief must be provided if there is any probability of axial stress to the leads. 8. If insulating bushings are used, they should be of dialyiphthalate, fiberglass-filled polycarbonate, or fiberglass-filled nylon. Unfilled nylon should be avoided. 4—60

8A HALF-BRIDGE MOTOR DRIVERS SS UDN-2951Z AND UDN-2955W 8A HALF-BRIDGE MOTOR DRIVERS FEATURES rated sink and source outputs, and a DISABLE input Ss PAcupacarauny ie) that can be used in high-speed chopper application. © 50V Operating Range The UDN-2951Z is supplied in a TO-220 power- © Thermal Shutdown Cirultry tab package for enhanced power dissipationypabil- © Built-In Crossover Delays ities and minimal size. The UDN-2955W is upplied Disable and Emvitter-Sense pins (UDN-2955¥) in a 12-pin single in-line plastic pqWémtal hack- © Overvoltage Protection age for exceptional power handling capabilities. © TIL, CMOS, PMOS, NMOS Compatible Inputs This power-tab confisnop ows or cxsy ug . Internal Linear-Overcurrent Limiter ment of an external Aéat“sinf ox extentted ower-handling capabilitiés, Sw, The UDN-2951Z and UDN-2955W half-bridge Pp mere \\v OND motor drivers can handle 8 A continuous load cur- a rents and output voltages up to 50 V. Both devices Th < feature TTL, CMOS, PMOS, and NMOS compati- re \\ ble inputs, level shifting, and an internal voltage reg- ‘ \\ CO ulator for single-supply operation. Output transient- or, ‘ suppression diodes in both sink and source drivers a “ have been incorporated. - ~ The UDN-2951Z and UDN-2955W both have in- ¢” SS ‘Oy S ternal delay times to guard against hazardous cross; by, ‘ ‘sy over currents. Both devices maintain intewtal Ps AN , ’ current limiting, overvoltage protection updo JS Ny W. “\\O b> and thermal shutdown at 165°C. ‘ ~ mie ant A The UDN-2955W has extended flexibility ae ie ‘i \\ ia} i \\ external emitter sense pin on theibk driver, sea, Jee oy "B52 8 ia Ne £Oo5 5 coe, i 35 0 _ MY ta td Y cz no. Ho Aa soe SS [CBS 3] UDN-2951Z, ) ) > ABSOLUTE MAXIMUM RATINGS A/| &? EB att, = +25°C < cc Supply Voltage Range, Vy... eee ceeveveees 1OVH0 75 VF Z ay 2a 2 Package Power Dissipation, P, 3 geisgR 2 (ZPackage) o.oo. ee eeeceeeeeceeeceees 31250 tad Seana % WPACKABE) eee cece eee eee SZ WM Gi tseTHERMAL SHUTDOWN “Derate atthe rate of 25 mit/°C above T, = + 25°. Dg. ba, Abi t8 **Derate at the rate of 41.66 mW/°C above T, = + 25°C. UDN-2955W ‘internal over-voltage shutdown above 50 V. 461

8A HALF-BRIDGE MOTOR DRIVERS SS FUNCTIONAL BLOCK DIAGRAM UDN-2955W

1 UDN-20512

\\ — H SOURCE out i | DISABLE 0 >d Cb oobrput | | ] | I ] SINKour =—_ —_ ax ° ani! +> ) > j EMITTER SENSE Looe ees TOD = TURN ON DELAY, TS = THERMAL SHUTDOWN Ova No. A4190 ELECTRICAL CHARACTERISTICS at T, = + 25°C, V, = 50V, DISABLE (UDN-2955W) = 0V Characteristic Conditions | Min. Typ. Max | Units | Output Leakage Current |= | Vou = 50¥ a Output Sustaining Voitage [Views | lon = 8A, L = 3mH [so — — |v | Output Saturation Voltage Ig = 8A Shor-Circuit Source Current Fl | —30 — -2| A jroteret Le weeny fs [le | vasosy i 50 Tt Propagation Delay [te | _ tur = 8A Resistive Load, Sink Driver — 2 lor = BA, Resistive Load, Sink Driver =o = ly: = —BA, Resistive Load, Source Driver..| — 25 — [tu | Ig = —8A Resistive Load, Source Driver | — 25 — | ys _| Clamp Diode Forward Voltage Clamp Diode Leakage Current Ve = 50V ;— — 50 | pa | Supoly Curent [Ve 20V | em Vax = Venass = 08 V [0 ma Thermal Shutdown Temperature Over-Voltage Shutdown a 1, Therma! shutdown has a typical hysteresis of 15°C. 482

8A HALF-BRIDGE MOTOR DRIVERS TYPICAL APPLICATION 3-PHASE BRUSHLESS DC MOTOR DRIVE UDN-2951Z UDN-2951Z UDN-2951Z > > it > tt | fe) Ll a (Tre i i is if iy is f adi . Sov 5QV 50VO OSIi1 O OsI2 O OsI3 Oso1 os02 Oso3 A vs) \\e BAY Bo Sc vp. No. Asa INPUT WAVEFORMS sot ee SIt LJ sep— UW. so3 TT SI3 L__] ep. Ne. Ang 8 4—63

FEATURES YK 116] “eB © High Output Current Vss) CaM BS) Yop © Adjustable Stor-Circuit Protection Rw © Thermal Protection oun, GS [22] PHASE ¢ Internal Ciamp Diodes SUB o TIL DTL, PHOS, CMOS Compatible ‘ | “ © DIP or SIP Packaging sus Ls sta SUB Ya [al ENAGIE FFULLBRIDGE MOTORDRIVER integrated \\ss2 fio} GROUND circuits, Types UDN-2952B and UDN-2952W ot) cal Ho Ve8 combine low-level logic circuitry and Darlington ——AS output power drivers for bidirectional control of d-c Ora. to, Het 3688 motors or solenoids operating with continuous load currents of up to 2A and peak start-up currents as UDN-29528 high as 3.5A. cost devices are identical to the basic parts, except For applications requiring load currents of 14 or for the maximum allowable load-current rating. less (2A peak), the economical Type UDN-2952B-2 . _ and UDN-2952W-2 are recommended. The lower- These monolithic integrated circuits have exten- sive circuit protection. Both drivers have thermal shutdown networks that disable motor drive if the package power dissipation ratings are exceeded, In- ternal diode transient suppression is provided on- chip. Output-current limiting is determined by the user’s selection ofa sensing resistor. Ww ‘The Type UDN-2952B full-bridge power driver is CT +40] 13 supplied in a 16-pin dual in-line plastic package with E{ tosic } copper heat-sink contact tabs. The lead configura- Cleattt iD tion enables easy attachment of a heat sink while fitting a standard integrated circuit socket or printed i i i i | I A ! wiring board layout. Type UDN-2952W, for higher Zi} Wi is is y a ua power requirements, is in a 12-pin single in-line Ss Be 8 z Sees 2 power tab package. The tab is at ground potential se = mao. peateaegn and needs no insulation. For output currents above mene eis 700 mA at normal ambient temperatures, both driv- UDN-2952W ers require an external heat sink. 4—64

atTys = +70°C TRUTH TABLE Logic Input Voltage, Vowge Of Vewgug. oe2es se vveeeeees 30¥ low High = <08V ->45V High Low (UDN-29528-2 and UDN-2952W-2),. . 2A x X 09 >45V Open Open ELECTRICAL CHARACTERISTICS at T, = + 25°C, Ves = 40V, Voo = 5V, Tus = +70°C, Figure 1 (unless otherwise noted) Characteristic Symbol Test Conditions [ Min Tyo. Max. | Units | Output Drivers (QUT, or OUT,) ! Output Leakage Current [vas = SV Var = OV.Noter [| — 500] | Output Saturation Voltage | Vezsm | 4 [rine ei teem PSs jeer Tg a Te [Tawoin [ Veuse = 24V, Outputs Open, Note? | — 3.050 | mA] Giamp Diode Forward Votage | Vy [r= 2A Note 3 [= is 22 Tv | Control Logic (PHASE or ENABLE) _ Logie Input Current [tao | Vows Voor = 24V T= 80 = 100A [ine | Vou Vins = 08018 | | a a a [oeieSuppy Curent [ts | Sd || [Sense Tggervotage [Vs | Voi = 080 SSS |r Toran Daley Tne Se | SaueeDves Cs [sities 4 Turn-OFf Delay Time | SouregDrivers ns | [SinkDrivers Ts | [Thermal Shutdown [Ps Te NOTES: 1 Tet peromed with og = OBV andthe epeted Vu = 2A 2. Output measurement at 1A are applicable to the UDN-2952B, UDN-29528-2, UON-2952W, and UDN-29624-2. 3. Output measurements at 2A are apolicabe only to the UDN-2952B and UDN.2952W. 465

+ Vs 9 2 g (gee fie | ee i) 2) @ f fe, ba /\\ On BO erase ry, e nme BD wD, LS an THERMAL ) 4} —4 a | Chr © @ G 2) GED me 28 3 & 82 TSUBSTRATE T ROUND my ar 2g {SUBSTRATE 4 a en ae oe © = vON-29528 (DIP) Deg. Mo. Ax11,367¢ DD = upn-2osaw (sip) ALLOWABLE AVERAGE PACKAGE POWER DISSIPATION ‘AS A FUNCTION OF TEMPERATURE UDN-2952B UDN-2952W P\\ | ‘ \\ s 3 \\ 2° \\ ZB 2 i o Veo é Ne é %, gs os Pa ‘A 4h z Xe = a MS é z %, te

2 IN ’ a wet ON

= NG, h | 2 %. \\ NG ‘ aa Wee ‘ Fy we San | ON 8 “ h. é Nee | Fa ie, NOR Fr ce 5 ” 2? PINs z a Nh é "orate [Ny 4 i am! 2 4 ets, be AY 2 5p <4 = caste = fee se i = & 2 5 Se 4 Say Se LLNS 0 ~., wi Ou rr a re Se NY TenpeRaTuRe in 8 “Hoos Dwg. No, A-t1,7838 oF 30 i 100 ry 150 TEMPERATURE IN °C ng. No. AoD8 BEA 466

sast | aes | Freres | seth mi Tne av aie: ourpur 8 | CNA #8V jy Th. SK o fect e a oe ey o STEP ENABLE Ii || vga, 151 +5V STEP INPUT +5v INPUT A INPUT B + ns -4 — L - —) — Dagolo, Ae 982 NOTES: 1. This is ota bipolar chopper application. 2. Resistor Ry sets the maximum allowable output current for protection against crossover currents and short circuits. Rs = 0.6/ljpur. 4—68

FULL-BRIDGE DC SERVO MOTOR APPLICATION

0 Vep=36V

i) . wa —_ i} pt 0 Vpn =5V [__ai- f— © DIRECTION amp FES | Piet a —_ . Dwg.No, A-11,984 4 ee ee ee _ > sus | > Sus SPEED (PWM) |p. I ¢-2A 4-69

FULL-BRIDGE PWM MOTOR DRIVERS ee ] UDN-2953B AND UDN-2954W FULL-BRIDGE PWM MOTOR DRIVERS @ 50V Output Voltage Rating xc Oi) ie K © 2A Continuous Output Rating ‘BRAKE Internal Fiyback Diodes “oar/ BARE Cay eo © Thermal Shutdown RC (TIMING) pa] A © Crossover Current Protection BRAKE, ENABLE, and Current-Limit Functions GROUND Bl [= ia GROUND GROUND if GROUND The UDN-2953B and UDN-2954W are designed Ye UG) es SENSE for bidirectional control of de or stepper motors PHASE 110] our, with continuous output currents to 2A and peak OUTPUT ENABLE [B4 1S] Voy start-up currents as high as 3.5 A. For pulse- (active Low) width modulated (chopped-mode) operation, the wp, No. Aa.024 output current is determined by the user's selec- UDN-2953B tion of a reference voltage and sensing resistor while the OFF pulse duration is set by an external RC timing network. PWM operation is character- ized by maximum efficiency and low power-dis- sipation levels. Extensive internal circuit protec- tion includes thermal shutdown with hysterisis, transient-suppression diodes, and crossover current protection. When the Vazr/BRAKE pin is low (<0.8 V, the- braking function is enabled. This turns both sink rs drivers OFF and the source drivers are turned ON. ye When Vaz/BRAKE is set above 2.4 V, that voltage (| 8 & (and the current sensing resistor) determines the a load current trip point. An Rc TIMING pin is avail- able to use for an internal one-shot to control load current decay time. j j i i I i ll | I I I I The UDN-2953B driver is supplied in a 16-pin s w dual-in-line plastic package with copper heat- 2% 3 A gSeyesg sink contact tabs. The lead configuration en- 2 6 Fa FS zs ° 8 ables easy attachment of a heat sink while fitting ° ys 5 a standard integrated circuit socket or printed ca z wiring board layout. The UDN-2954W, for higher 3 package power dissipation requirements, is sup- plied in a 12-pin single in-line power tab package, Pwo: No atau In both package styles, the heat sink is at ground UDN-2954W potential and needs no insulation. 4—70

FULL-BRIDGE PWM MOTOR DRIVERS el ABSOLUTE MAXIMUM RATINGS at Typ S +70°C Output Current, Iouy (Peak)... cece eee e eee eteeeeeeees SRB Logic Supply Voltage, Voc... esse ese evee rere terete reer sere DOV Logic input Voltage, Vewuse, Venseie: +--+ seer eee ceeeeeeeseeeeene ees Wpp. Sense Voltage, Veiuse..--- 000s cece e eee eect eee ree eee eee TEV Reference Voltage, Vac/BRAKE oo. c crete eee cece ee TEV ELECTRICAL CHARACTERISTICS at T, = + 25°C, Tras = + 70°C, Vee = 50V, Voc = SV, Veense = OV, 5k RE to Ground Output Drivers (OUT, or OUT.) Output Leakege Current mune [6 eee —t=—= eo [ Output Sustaining Votace | Vey | len = 22AL=2mH Ty TV Output Saturation Voltage Vessan [Geno DiodsleaageCwes | [W=8V SSS | [ Clamp Diode ForwardVokage [V, [w= 2A Motor Supply Current te | oes SR us Be eles Sea Veer = 4725 Control Logic CT Logie Input Current [ty | allinputs= Qa at 10 Ta eeewten Aah Logic Input Voltage (Wee alipus [Nee Oper-CirouitVokage [| Vaan [w= 0 | [_GurrentLimit Threshold [| Vawangeat Tip Point [8 tt | = io a ea Logie Supply Current [& PimeeSties 240, ___= sg ak | [Voue=O8V Vee 24v [=e 0 ma | Note: Tests performed at OUT, With Vewse = 0.6 Vand at OUT, with Vovage = 2.4V

FULL-BRIDGE PWM MOTOR DRIVERS By aly, 50 oO Bre FUNCTIONAL BLOCK DIAGRAM aaa \\7 Eat e we — Dae a VA ENRSLE d (ACTIVE Lom iC} Bi = zosaw sir) a DH Gt 20 TK TRUTH TABLE a OUTPUT 2 ENABLE PHASE VnyiBRAKE OUT, OUT, Ow a Tow High >24V High Low low low >24V Low High R High X BRAY Ooen Ooen X x <0.8V High High XeWeevat—OSOS~S~S ah Qrecrnonss Qe onan Aono bug, Ho 18088 ALLOWABLE POWER DISSIPATION AS A FUNCTION OF AMBIENT TEMPERATURE UDN-2953B UDN-2954W — 2 ft NO Fs E 2 °, 8 a = 4 EN ’ a | k “o A s Ve v

3 PN NN ‘, 3 Ne OY

3 ~~ my 8 ‘eo, h,

5 NOE g ey | Sh

~~ s 4 ‘. F} ee ihe Ss, 2 5h o Ni >, , SS i oe a oa, Seed “MD

3 SC see PNY

TEMPERATURE IN °C ~ 2s Dwg. No, A-11,7934 oy 30 75 100 13 180 TEMPERATURE IN °C vo, No A844 1-2

FULL-BRIDGE PWM MOTOR DRIVERS SS The UDN-2953B and UDN-2954W full-bridge For external current control, Vage can be be- drivers are ideal for driving 2-phase bipolar step- tween 2.4V and 15V. If left unconnected, Vice per, bidirectional de servo, and brushless dc mo- defaults to Vo¢/2 (Fig. 2). tore with various pulse wisi modulation (pwm) Average motor current can also be adjusted by earemecont formats. 3 pu baited 's San external pulse-width modulation using the ouT- rolled by using an external sense resistor and an PUT ENABLE pin, Toggling the OUTPUT ENABLE line optional RC network and reference voltage for shuts OFF both the source and sink drivers. Both an internal (ose eayerey PWM cirouit, or by the flyback and ground-clamp diodes conduct, using an external source. resulting in very fast current decay. In this mode, The output current trip point is set by: the RC pin should be connected to ground Jour = Vner!10 Renee through a5 kQ resistor. When the current in the sense resistor (typically With the RC pin connected to Voc Vnee and 30.5) reaches the set point, an internal one- Reexse Selected for a trip point greater than nor- shot turns OFF the sink drivers for a time period mal operation, but less than 3.5A, over-current (tay) determined by an RC time constant. The ac- protection is provided (Fig. 3). ‘tual peak load current will be slightly higher than Alo i" . : ' gic low at the Vaes/BRAKE pin turns ON both ihe do) because ot tre Interne lege and suateh, source drivers and turns OFF both sink drivers, a th h ing the motor. ing delays. This delay (t,) is typically 2 us. us dynamically braking the m . : An internally-generated deadtime of about 3 The ty» time interval (see Fig. 1) is approxi- 7 mately RC within the range of 20k. to 100 kQ and ue feces Crosser currents that ean occur 200 pF to 500 pF. If the RC pin is tied to Veo, inter- fen switching phases or braking. nal delay circuitry is activated, allowing PWM op- Thermal protection circuitry is activated and eration without the external RC network. Under turns OFF all drivers at a junction temperature of this condition, Ico will increase approximately 6 typically 165°C. It is only intended to protect the mA. The internaily-generated t, is approximately chip from catastrophic failures due to excessive 12s at Veg = 5V and T, = +25°C, increasing junction temperatures. The thermal shutdown slightly with increasing temperatures. has a hysteresis of approximately 8°C. TYPICAL APPLICATION UDN-2953B +36V Gy 116] BRAKE ee th 330pF F | = 14] poe ae | C | mal! = ao | ove iA i PHASE © 110} ENABLE o (a) | (ACTIVE LOW) Dag, No. 26408 473

DUAL PWM SOLENOID/MOTOR DRIVERS Cel UDN-2962B AND UDN-2962W DUAL SOLENOID/MOTOR DRIVERS Pulse-Width Modulated Current Control @ 4A Peak Output vee G 16] THSa e 45 V Min. Sustaining Voltage A © Internal Clamp Diodes SOURCEg [2 | 15] SOURCE, © TTL/PMOS/CMOS Compatible Inputs e* rit © High-Speed Chopper SINKS 54] SINK, © DIP or SIP Packaging LL] l GROUND i 13 | GROUND GROUND j 42 | GROUND Fe Using PWM to minimize power dissipation and Np [Bb —~op+ pga] INA maximize load efficiency, the UDN-2962B and Hs AL a UDN-2962W dual drivers are recommended for 8 GROUND impact printer solenoids and stepper motors. SENSEg [B | T] SENSE, Each device is comprised of two source/sink driver pairs rated for continuous operation to 3A. They can be connected to drive two inde- UDN.29628 pendent loads or a single load in the full-bridge configuration. All drivers include output clamp/ wg. No, o1000 flyback diodes, input gain and level shifting, avolt- age regulator for single-supply operation, and pulse-width modulated output-current control cir- cultry. Inputs are compatible with most TTL, DTL, LSTTL, and low-voltage CMOS or PMOS logic. The peak output current and hysteresis foreach source/sink pair is set independently. Output cur- the user's selection of external resistors. At the specified output-current trip level, the source Th aaa driver turns OFF. The internal clamp diode then ey ot allows current to flow without additional input a | | ‘ from the power supply. When the lower current trip —— ba ral point is reached, the source driver turns back ON. 1 i i 1 . J The UDN-2962B dual solenoid/motor driver is ’ J ha | supplied in a 16-pin dual in-line plastic package sic Ss F SES PSB with copper heat-sink contact tabs for medium 3 2eeFf7> eee °E package power dissipation levels (2.2W to >SW at s o 3 3 a +50°C). The lead configuration enabies easy ° ° Continued next page UDN-2962W wg, No. D901 475

DUAL PWM SOLENOID/MOTOR DRIVERS ee attachment of a heat sink while fitting a standard FUNCTIONAL BLOCK DIAGRAM printed wiring board layout. The UDN-2962W, for (One of Two Drivers) higher package power dissipation requirements, is in a 12-pin single in-line power tab package. The Veo tab is at ground potential and needs no insulation. With either package, for high-current or high- frequency applications, external heat sinking may SOURCE be required. — Loap SINK ABSOLUTE MAXIMUM RATINGS. SENSE at Trap S + 70°C GND 4 oC Supply Voltage, Veg... cceseeee cee eeeeeeeee ee 45V ? -| VReF Peak Output Current, loz... 0.0 cece eee EAA a (rv Operating Temperature Range, T, .... —20°Cto +85°C { Ornonronrnocnnes OTE: Output current rating may be limited by duty cycle, ambient temper- = ‘ature, and heat sinking. Under any set of conditions, do not exceed the + specitied peak current and a junction temperature of + 150°C. Dwg, No. Dd0 ALLOWABLE AVERAGE PACKAGE POWER DISSIPATION AS A FUNCTION OF TEMPERATURE UDN-2962B UDN-2962W 8 y » 5 “ Zu \\ = 4 oa Ve zs fs \\s, 4S = A %, ‘ = 3 4 » | = z Ne 4 BANS a ut POSEN} INT) we afNoe Z g Kos \\ = ce NS s : Sh = a) Se ee, NS = Oe 5 Seg | OS \\ 2 [Paps Se ane M \\ 1 = on ‘ LOCO m ‘i |] | Sy > Sy "5 73s sz a rs) TEMPERATURE IN ®o TEMPERATURE IN °C Dwg. No. A-11,783A Dg. Ne AC 708A 4—T6

DUAL PWM SOLENOID/MOTOR DRIVERS Sd ELECTRICAL CHARACTERISTICS at T, = +25°C, Tru S +70°C, Voc = 45V, Vsewe = OV (unless otherwise noted) Output Drivers Output Leakage Current | pena} ae Gupat Saturation VoTage | Vem Sink Drvers, Nyqg=3.0R Output Current Regulation [Alpi | Figstarecsttssear | == =i [oututfiseTine | 1. | hag 3.0A 10% 50%, Pesto Load | — 05 1.0 | ae _| [outpurFal Time | ts | hauy=5.0A, 90% 10 10%, Resistive Ld | — 05 1.0 | | | 4 | Control Logic Lege npufVolage@ [Van | ee Ca Ta ae =i [no [Wa=OBY Sd TO] [WrsrVaneRate i [Vre=tovesOv «OOS | Supa Curent ae (otal Device) [Wa=0.8V,Outats Open 05 ma] (sitive Loz) [B0% Val0S0% Van. TUMOR *Where Vsense 2VTHs/9-5 NOTE: Negative current is defined as coming out of (sourcing) the specified device pin. TRUTH TABLE Vow Vecuse DRIVER DRIVER High NA off off Low <Ving/10 on On Low DViyg/10 or on 4-11

DUAL PWM SOLENOID/MOTOR DRIVERS eel The UDN-2962B/W driver is intended for use as set by R;. The chopping frequency is asynchron- a free-running, pulse-width modulated, motor or ous and a function of the system and circuit solenoid driver. parameters, including load inductance, supply The source and sink drivers are both turned ON voltage, hysteresis setting, and switching speed by a low level at the input. When the load current of the driver. teaches the trip point (set by external resistors), | the comparator output goes high and the source Maximum load current and hysteresis percent: driver is turned oFF. The internal clamp diode then age are determined by the user: allows current to flow without further input from Ry = 50VaccH the power supply. An internal constant current Ru(10 Invax Re) sink reduces the trip point (hysteresis) until the Rr = 70 Iya RO)

2 Vaer— (10 Iivax Rs)

decaying current reaches the lower threshold, when the comparator output goes low and the where 10 Imax R= Vris=0.6 to 5.0V source driver is again turned ON. Hysteresis per- and H = desired hysteresis in percent. centage is a function of the external resistance Ry, Graphical solutions for Ry, and Ry, with Vaer= and is independent of the peak output load current 5 V and Rs=0.1 , follow. TYPICAL WAVESHAPES VIN — Veo VSINK aid Vsource “ee 7 — GND lLoap J s RANA) MARS = VTHSIT0 LLL ee VTHS wg. No. D008 4-78

DUAL PWM SOLENOID/MOTOR DRIVERS SS RESISTOR Ry VALUE. AS A FUNCTION OF HYSTERESIS |e] ; Ss ee £15 aq pee °5 20 “40 Ey 20 700 HYSTERESIS, H, IN PERCENT Dip, No. A267 RESISTOR R, VALUE AS A FUNCTION OF PEAK LOAD CURRENT J TTT TTT 4 J Veer * SV ef-Leset | Tot tT VY eee Zz o 05 «10 1S 20 28 30 35 a0 LOAD CURRENT, Imax, IN AMPERES ag. No. A218 For optimum operation of the UDN-2962B/W, the following design guidelines should be observed: 1. The Vcc supply should be decoupled with an electrolytic capaci- tor (10 uF or greater). This capacitor should be placed as close to the driver as possible. 2. To minimize IR drops in the ground line, the printed wiring board should utilize a heavy ground plane; the driver should be soldered into the board, not used in a socket. 3. When using the UDN-2962B/W in an H-bridge configuration, a high-speed discrete diode must be used in series with each sink driver. 4—79

DUAL PWM SOLENOID/MOTOR DRIVERS ST TYPICAL APPLICATION BIPOLAR, PULSE-WIDTH MODULATED, STEPPER-MOTOR DRIVE +36V Ye UDN-2962B/W Ya UDN-2962B/W nes in Pvgg 7 4 1 ] \\ 1 JL! a | nM! Dp a Nod e——° IN | i ! fe e| | sev, | 8 we S| i tev $1 ' ant 1 1 z ] i Tus! San og 3 Pr + af 4 Dg, No, D100 Ry AND Ry DETERMINE HYSTERESIS AND PEAK CURRENT NOTE: Each of the drivers within the UDN-2962B/W includes an intemal logic delay to prevent potentially destructive crossover currents within the driver during phase changes. However, never simultaneously enable both inputs in the full-bridge configurations: A destructive short- circuit to ground will resutt MOUNTING POWER TAB DEVICES Power-tab packages are efficient thermal dissi- pators when properly utilized. In application, the 5. Brute force mounting to poorly finished heat following precautions should be taken: sinks can cause internal stresses which 1. Always fasten the tab to the heat sink before damage silicon chips and insulation parts. the leads are soldered to fixed terminals. Mounting torque should be between 4 and 8 2. Strain relief must be provided if there is any inch pounds (0.45 to 0.90 Nm.) probability of axial stress to the leads. 6. The mounting holes should be as clean as 3. Thermal grease (Dow Corning 340 or equiva- possible with no burrs or ridges. lent) should always be used. Thermal com- 7. Use appropriate hardware including a lock pounds are better heat conductors than air washer or torque washer. but not a good substitute for flat mating 8. If insulating bushings are used, they should surfaces. be of dialylphthalate, fiberglass-filled 4, The mounting surface should be flat to within polycarbonate, or fiberglass-filled nylon. 0.002 inch/inch (0.05 mm/mm). Unfilled nylon should be avoided. 4—80

DUAL PWM SOLENOID/MOTOR DRIVER EEE UDN-2965W-2 DUAL SOLENOID/MOTOR DRIVER —Pulse-Width Modulated Current Control © 5APeak Output © 50 V Min, Output Sustaining Voltage ‘© TTLPMOS/CMOS Compatible Inputs © Low Input Current ar. © Internal Clamp Diodes Fou © Internal Thermal Shutdown [| ‘@ High-Speed Chopper Le (il Plastic SIP With Heat-Sink Tab ete | | TT DESIGNED TO DRIVE impact printer solenoids f i i i I ! I | ey) L l and stepper motors, the UDN-2965W-2 in- 2 zg Pa Pe a8 a Pa f2g cludes two independent driver pairs rated for contin- 8 £58 F BREF uous operation to +4.A. Each half-bridge driver 6 % ¢ Rg 4 includes diode transient protection, input gain and oa. AB4r84 level shifting, a voltage regulator for single-supply . . ; operation, thermal protection, and pulse-width operation. The tab is at ground potential and needs modulate (PWM) output-current control. Inputs are no insulation. compatible with most TTL, DTL, LSTTL, and low- Devices with sustaining voltage ratings of 60 V are voltage CMOS or PMOS logic. presently in development as the UDN-296SW (no The PWM mode helps minimize power dissipation suffix). Similar dual 4 A solenoid drivers, for non- and maximize load efficiency. The peak output cur- PWM applications, are available as Sprague Types rent and hysteresis for each half-bridge is set inde- UDN-2975W and UDN-2976W. pendently. Output current, threshold voltage, and hysteresis are set by the user's selection of external ABSOLUTE MAXIMUM RATINGS resistors. If desired, internal threshold and hyster- atl, = +70°C esis defaults (400 mV and =10%) can be used. At the = specified output-current trip level, the source driver Supply Voltage, Voc. oe .eece cess ceeeeeeeee ee SOV turns OFF. The internal flyback diode then allows Peak Output Current, lu, sereeeeeeseees ESR current to fiow without additional input from the pee ate fangs “i ppc baw +70y eenche 4 the source driver turns back on PP Operating Temperature Range, T, = 20°C to +85°C ari or ie sapolied Loner andling capability, the NOTE: Output curent rating may be limited by duty cycle, ambient iver is supplied in 12-pin single in-line power tab ‘temperature, and heat sinking. Under any set of conditions, do not exceed package. An external heat sink is required for proper ‘the spectid peak current anda junction temperature of + 150°C, 481

DUAL PWM SOLENOID/MOTOR DRIVER SSS vee FUNCTIONAL BLOCK DIAGRAM {ONE OF TWO DRIVERS) ; > @ SOURCE fiom ‘SINK IN O--4 O-==9 sAcrbown << ov Siar oe 5] lax "3h GND RSF 1 << 045V 3m tee L o og. #12604 ALLOWABLE AVERAGE PACKAGE POWER DISSIPATION ‘AS A FUNCTION OF TEMPERATURE 20 \\ : \\ é el Ys TRUTH TABLE o ° a eSSFSFSFSSSSSSSSFSSeSeSF z Ne Ve Source Sink 3 % ; = A, \\s Vw Vous Vsexge Driver _Driver Hysteresis 5 eg ‘ High NA NA of Off NA Z 4 ‘ low <0.4V NA Of = On NA 2 cd . Low 0.6Vt04.0¥ <Vpg/l0 On On Set by Ry 5 \\S L Low 0.6Vto4.0Y >Vyg/l0 Off On _— = ‘o0 , low = >45V 0 <04V On On 8% to 10% < Se, ‘, low >45V>O4V OFF = s a Sit oo = Ni \\ \\ a 4 6 a 2 5R a Roo =z “26°, ~. ‘ Se “ MA ot ‘wl ON men, ‘. Rak 0 aS a 30 i 100 15 150 TEMPERATURE IN °C og. Me, Rs 7868 4—82

DUAL PWM SOLENOID/MOTOR DRIVER OE Ee nee eee ELECTRICAL CHARACTERISTICS at T, = + 25°C, Tyg = +70°C, Voc = 50V, Viase = OV (unless otherwise noted) Pe Chatacteristic Symbol | Test Conditions [Min Typ. Max. | Units | Pome eT ‘Output Drivers Output Leakage Curent a Output Saturation Voltage Versin Sink Drivers, oo = 4.0 A — 2 Sink Drivers, yo = 4.0 A — 10 12 Output Curent Regulation Abr [Vos =06VinLOVU=35mi | — ea | | [Vas =10Vin20V.L= 35m | et | | | Voe=20Vt040V.L=35mH | — 80 |_| | clamp bade Fonvardvotage |) | b=a0A |) = 0530 Control Logic | 4 | Logic Input Voltage [aoe Ae} f# = A Logic Input Current = 10 10 to _[ Ya = 08 Fase | Vee = 400mV | = 80 Tn | Output Disable Vatage | Voom || 8m [ Ween Ratio | | eg 20veaov | 51 its | — Ci Vag = 4.5 380_400_420 | Defauittystersis TH Vas = 85 | 59 = |e | Supaly Current ke [aes | cee t= eta Propagation Delay Time — = 5 100% Voge to 50% Van [TremalShutdown Cd Ce Where Vaaysr = Vpg/9.5, NOTE: Negative current is defined as coming out of (sourcing) the specified device pin, logic delay to prevent potentially destructive crossover currents within the driver during phase changes. However, never simultaneously enable both inputs in the full-bridge configuration: A destructive short-circuit 10 ground will result. 483

DUAL PWM SOLENOID/MOTOR DRIVER LEE enna ne eee The UDN-2965W driver is intended for use as a Maximum load current and hysteresis percentage free-running, pulse-width modulated, motor or so- are determined by the user: lenoid driver. Ry = 50Vgep H The source and sink drivers are both turned ow by Ry(10 Iuax Re) a low level at the input. When the load current Re = Vee — 00 Tax RO reaches the trip point (set by external resistors or internal default), the comparator output goes high where 10 Imax Rs =Vris = 0.6 to 4.0V and the source driver is turned orF. The internal and H = desired hysteresis in percent. flyback diode then allows current to flow without Graphical solutions for Ry, and Ry, with Vase = further input from the power supply An internal sVand R, = 0.1 0, follow. constant current sink reduces the trip point (hyster- . . esis) until the decaying current reaches the lower Pulling Vrus down to less than 0.4 V disables the threshold, when the comparator output goes low and source driver, turning the load oF. With Vrus the source driver is again tured ow. Hysteresis per- greater than 4.5 V, the hysteresis is fixed at (defaults centage is a function of the external resistance Ry voypemveen 5% and 10% and the peak load current and is independent of the peak output load current is fixed at: set by R,. The chopping frequency is asynchronous Tuax = 0.4/Rs and a function of the system and circuit parameters, including load inductance, supply voltage, hyster- esis setting, and switching speed of the driver. TYPICAL WAVESHAPES Vin — Vee Vsink —— GND Vsource —— GND ILoaa ] mn \\ NM AY Ha Bs = Vis /10 Vrs UU nn — Dro. Aves 484

DUAL PWM SOLENOID/MOTOR DRIVER SS | Ty eT Sis RESISTOR R,, VALUE z AS A FUNCTION OF HYSTERESIS = = 10 t-7| [TT T °O 20 40 60 BO 100 HYSTERESIS, H, IN PERCENT Dag.No. Ae12,437 J TT TTT Ty 20) /| Vier = 5V z PEAK LOAD CURRENT Ex AS A FUNCTION OF . es RESISTOR R, VALUE S LF ZEA A LU A _S—— 0 a —— | Ci” fe) 05 1.0 15 20 25 3.0 35 40 LOAD CURRENT, Iyax, IN AMPERES pete, Maze BIPOLAR, PULSE-WIDTH MODULATED, STEPPER-MOTOR DRIVE +48V Va UDN-2965W-2 vf UDN-2965W-2 Poe Pe 4 1 | i | tl Gi smi [ a | \\ i} oO Oo 45v 8 8] fl asv. sv; | gy ig i ] paced T 1g, Rul 1 ory i " Irs 2's | ! ‘a THs! Lo IS i R R fr 3 ong 3 | ' * + . + Ry AND Ry DETERMINE HYSTERESIS AND PEAK CURRENT ee wat 485

© 5APeak Output © TILPMOS/CMOS Compatible Inputs © Low Input Current © Output Voltage to 60 © Single-Ended or Split Supply © Adjustable Short-Circuit Protection © Interval Clamp Diodes [hy [rer] ne © Plastic SIP With Heat-Sink Tab pe ea TS LTT COBRENT CONTROL for operation of a pair of - 2 . a print solenoids is provided by both Type UDN- $28 223 .3 2975W and UDN-2976W. Each IC’s dual driver sec- Bsg23b 2325 28 tions operate directly from the printer control line. bagsho, 822,108 The two devices differ only in output-voltage rat- ings. They can be used at currents of up to4 A. in-line power tab packages. For proper operation, Type UDN-2975W is rated at 50V. Type UDN- an external heat sink is required. The tab is at Vex 2976W is rated at 60 V or +30 V. Inputs are compat- potential and must be insulated from ground when ible with most TTL, DTL, LSTTL, and 5 V to Type UDN.2976W is used with a split supply. 15 V CMOS and PMOS logic. Current is controlled by a current-sensing latch ABSOLUTE MAXIMUM RATINGS method that uses only one external sensing resistor at Ty = +70°C for each driver. The load current is compared with Tap without further input from the power supply, result- input Voltage Wit tw cress nsereessesenresss ge ing in maximum efficiency. The latch is reset by pull- Ways ing the input high, Reference Voltage, Var». eee eveeeseeeerreeees SV 4-86 i :

(ONE OF TWO DRIVERS) o¥ec N ia . )> a SOURCE LOAD SINK OM GND ° C SENSE B d or SENSE RESISTOR <J (TYPICALLY 0.192) Vs <_J 5-4 ORS RS SUB OREF Dg So, At2.1068 ALLOWABLE AVERAGE PACKAGE POWER DISSIPATION ‘AS A FUNCTION OF TEMPERATURE ( To maintain isolation between integrated circuit Fa components and to provide for normal transistor op- = \\ eration, the substrate (pin 1) must be connected to Zz the most negative point in the external circuit. é “I e z 2, BS 2 Ke. 8 = S 12 = te. ‘ B Ne \\ 5 | 4 B “4 TRUTH TABLE

8 Ro, MOON Source Sink

g Sh, ay Vw Vecnse Driver Driver Function

3 Xe, YA High NA Off Off Off

2 Pr es aes Low <Vyer/10 On On On

g <o we \\ Low >Vpu/10 Off On Flyback 2 eae POY tw VieelQ Off On Flyback _ Se ‘~ \\ 1 ss, “UNS aoe oN BX: 0. <% 2B 50 5 100 125 150 TEMPERATURE 1N °C Oa. Ath. 74 4-87

ELECTRICAL CHARACTERISTICS at T, = + 25°C, Trg <S +70°C, Voc = 45V (UDN-2975W) or 55 V (UDN-2976W), Vez = Vseuse = 0 V (unless otherwise noted) rd ree Characteristic Symbol | Devices Test Conditions | min, Mex. | Units | SupalyVotage Renge Ve Senne tt Pen [ig [path [outputs open | 20 Ta Output Drivers [Vu=24V Vow =Ve= Sov | — 300 | aa | uoN-2976W [Vu = 24V. vor = 60VVowe= OV | — 100 | wa_| [Ya=24W Vow =Ve=60V | — 100 | ya | Output Saturation Vottage | Vexam Ow [getty at | Output Sustaining Voitege | Vera (Seure vers ony SEE ea Bath [outovtRiseTine [tbat | ao = 4A, 10% t 90% Resistive Load | — 20 | s | Loutoutrantine ts ]toth [ho = 44, 90% 10 10% Resistive load | — 2.0 | us| Control Logic _ Logic Input Voltage Vou wh | C—“<~mCS CT [Yoo [Both seenotes Tt Logic npct Curent [iw [Bath wa eav Po [bo [bth [vw=oav | 20 [how | Both [v= sov | 20 |_| Reference/Sense Ratio [=| Both [ve =20tesov 855 | — | Propagation Delay Tine ee Winimum Reset PuseWwath | t, [poh P| Ts FWhere Vane = Vogll0.5 NOTES: Negative curent is defined 2s coming out of (sourcing) the specific device pin For improved noise immunity, hysteresis insures Vg of 0.8 Vmax afer V, is 0.5 Vor ess, 488

DUAL FULL-BRIDGE MOTOR DRIVER el UDN-2998W DUAL FULL-BRIDGE MOTOR DRIVER © 3A Peak Output Current © Output Voltage to 50V Integral Output Suppression Diodes © Output Current Sensing © TTL/CMOS Compatible Inputs © Internal Thermal Shutdown Circuitry Pe ft a © Crossover-Currént Protected HY Loaic | Ht ee ey Asan interface between low-level logic and sole- noids, brushless de motors, or stepper motors, the UDN-2998W dual full-bridge driver will operate ; inductive loads up to 50V with continuous output Sue =F Ss 8 BF Bu - currents of up to 2A per bridge or peak (start-up) 3 28 8 > 3 3 nr! ¢ currents to $A. The control inputs are compatible & Es Ze with TTL, DTL, and 5V CMOS logic. Except for a ow. No.0 common supply voltage and thermal shutdown, the di i ki independent in each package are completely requires the use of an external heat-sink. The tabis For external PWM control, an ouTPUT ENABLE for aground porn ne meee no insulalion. h each bridge circuit is provided and the sink driver fi neload ual nt st aes Ina “ SUDN29905, emitters are pinned out for connection to external Inuous load currents to #: S00 mAIs the UDN~ . current-sensing resistors. The chopper drive mode is characterized by low power dissipation levels and maximum efficiency. A PHASE input to each bridge ABSOLUTE MAXIMUM RATINGS determines load-current direction. Supply Voltage, Vap canes cececeseecess SOV Both ground-clamp and flyback diodes for each — 6 (Peak) oe SA disables the load drive if chip temperature rating Logic Input Voltage Range, ~0.3Vt018V (package power isan) i exceeded. nial vacate Sheer Be Bosco eae generated delays provide crossover-current Operating Temperature Range, Ta .... —20°C to +85°C The UDN-2998W is packaged in a 12-pin single hore Output current rating may be imited by chopping trequency, 4 it ambient temperature, air flow, or heat sinking. Under any set of condi- in-line power tab package for high power capabilties. fons, do ot xced the sexed carton ang or mctan tempera Driving either of the bridges at the full 2A de rating ture of + 150°C. 4—89

DUAL FULL-BRIDGE MOTOR DRIVER el FUNCTIONAL BLOCK DIAGRAM (ONE OF TWO DRIVERS) OMe8 THERMAL |, SHUTDOWN ENABLE [) CI (ACTIVE LOW) © oO TURN-ON DELAY a | PHASE Ove ong Ne WI07A ALLOWABLE AVERAGE PACKAGE POWER DISSIPATION AS A FUNCTION OF TEMPERATURE Ey \\ g To maintain isolation between integrated circuit = N\\ components and to provide for normal transistor Zz. operation, the ground tab must be connected to the 5 os Yeo most negative point in the external circuit. é “| es z Ne ye 2 | AS = %, ve

8 Ne ‘

2 0 Xe \\

5 Ve ry

s “oe, H Ss Si, ‘ 8 nd Si TRUTH TABLE z 2 STN EE g Ne VI 4 Enable Phase =P Se Input Input Output 1 Output 2 z oe c q 1 tp put 2 2 Se 2240 .. a Low High High Low Se | INN tow Low Low High as i NN High High Open Low or ROA} High Low Low Open <2y Ae 9, 50 B 100 135 150 TEMPERATURE IN °C Og. Ne At 17844 4—90

DUAL FULL-BRIDGE MOTOR DRIVER EE ELECTRICAL CHARACTERISTICS at Ty = +25°C, Tras < +70°C, Vos = 50V Limits [awnsnite |v Test Conditions Min, Typ. Max. _ Output Drivers Opt Leatge Curent | es peters Rane |S Output Saturation Voltage Voexsan) — 12 «14 lout = ~ 1A, Source Driver lour = —2A, Source Driver [— 20 22) Vi Source Driver Rise Time t lout = —2A [— 500 ~—| os| ‘sisi — ji ferss tl ee inh por Venastecty = Venaate) = 2.0V mA | 4 Control Logic (PHASE or ENABLE) Logie Input Voltage ~ [os — =] Vd A Vonase OF Venasue = 2.0 = <10—-10 ENABLE Input to Source Drivers NOTES: 1. Each driver is tested separately. 2. Testis performed with Veuase = 0.8V and then repeated for Veuase = 2.0V. 3. Negative current is defined as coming out of (sourcing) the specified device pin. Vose ap. No.4 gre 491

DUAL FULL-BRIDGE MOTOR DRIVER ———— TYPICAL APPLICATION 2-PHASE BIPOLAR STEPPER MOTOR DRIVE (Chopper Mode) Frere] feet H toa ]]) || [coach Cre re | nonnnnnnnn pore ed ak 1K +8V0 Dwg. Mo. W108 ° 4ev io) +5V INPUT B | os met 4—92

POWER OPERATIONAL AMPLIFIER Ce ULN-3751Z POWER OPERATIONAL AMPLIFIER © High Output Swing © Peak Output Current to 3.5.8 © Low Input Offset © 90 dB Typical Open-Loop Gain © Interna! Thermal Shutdown © High Common-Mode Input Range > © Unity Gain Stable © Pin Compatible with L166, L465, SG1173 | As a combination general-purpose operational am- plifier and power booster, the ULN-3751Z inte- ul grated circuit simplifies circuit design, reduces component count, and enhances system reliability. 2 z Fae The power op amp features high-impedance dif- 22 zg 3 ferential inputs, a unity-gain stable amplifier that = 52 needs no external compensation, and a high-current B23 power output. Typical applications include use as a Zz voice-coil motor driver, linear servo amplifier, 2 owe na ataaee power oscillator, bipolar voltage regulator, and audio power driver. The ULN-3751Z is for applications demanding up This power op amp operates over a recommended to +3.5 A of output current. Itis furnished in a mod- supply voltage range of +3 V to +13 V. Dual power ified Sead JEDEC-style TO-220 plastic package. ‘op amps are available as the ULN-3755B (16-pin Lead forming for vertical or horizontal mounting is DIP) and the high-power ULN-3755W (12-pin SIP). available (ULN-3751ZV or ULN-3715ZH). The Both of those devices include output current sensing heat sink tab is at substrate potential and must be and a voltage boost connection to maximum output insulated from ground when the device is used with voltage swing to +20V supplies at up to +3.5A a split supply. peak output current. 4-93

POWER OPERATIONAL AMPLIFIER el ABSOLUTE MAXIMUM RATINGS atT, = +25°C Peak Output Current, lyr... -.ssecccceeceeeeceecceeeeeeeteeeeeeees #35A Input Voltage Range, Vy... cecccccceecvseeecva seesaw ees FV540 —Vp 03 ALLOWABLE POWER DISSIPATION AS A FUNCTION OF AMBIENT TEMPERATURE Loy ! AT 3 <. N § Nau Ses, \\ & Reg | Ne \\ 8 IN No. \\ 3 een iS rN ES we NS 4 si FA S., g PE See... > LT SSS °o 3S 307570072180 AMBIENT TEMPERATURE IN °C Og. No A849 4—94

POWER OPERATIONAL AMPLIFIER Ce ELECTRICAL CHARACTERISTICS at T, = + 25°C, Tyg < +70°C, V, = +6.0V (unless otherwise noted) Characteristic Test Conditions [Min Typ. —« Max] Unit _—| Functional Supply Voltage Range 60 — 26 Quiescent Supply Current P= 40 60 | Input Bias Curent | Wn = Ob =O CSCO =60 = 1000 [mA Input Offset Vottage PV = Oly = 02010 mv] Input Offset Current Vu = Olay = 0 — 10 a a Input Noise Voltaget BW = 40 Hz to 15 kHz BW = 40 Hzto 15 kHz | pA | Pog = 50m, R = 40 Common Mode Rejection Te 85 — | 8 | Input Common Mode Ranget Open-Loop Vortage Gain a Gain-Bandwidth Productt Ay = 40cB [| — 3 ie Output Voltage Swing ly = 1A Supply Voltage Rejection +V¥;, AV = 1V 60 35 = | 68 [ =V,AVSTy 80 80 — | we] Thermal Shutdown Temp.F rs “This parameter is tested to a lot sample plan only. ‘Typical values given for circuit design information only. TYPICAL APPLICATIONS WIEN BRIDGE VIDEO MONITOR OSCILLATOR/MOTOR DRIVER VERTICAL DEFLECTION MAP , gr18v = ~ IQ On ° O "t 0.33 82K ~ 3088 OMT 8.2k 7 3 + “= = Dwg. No. A12,9758 bo. 495

POWER OPERATIONAL AMPLIFIER eel TYPICAL APPLICATIONS UNITY GAIN VOLTAGE FOLLOWER NON-INVERTING POWER AMPLIFIER +6v +6 ° ye OL Ea aia > = ° = INPUT > INPUT g z > = = ff ia RL 7] id we eh oat = + Re 7 T oy = = a+

6 Aysl*

CAPACITANCE VALUES IN uF. og Ne. A2851 wg No. 12.858 LINEAR VOLTAGE REGULATOR HIGH-POWER LINEAR REGULATOR (Short-ireut Protected)

9 Voc = 6V 10 25¥

26 [I cna Voc = 8V TO 25V REF, = ° Tual a1 = VBE OR EQUIV. Ld > Yo Tt L 3 Rso= Tee + 205 22708 Re RF. . Tan [J 2NBOSSI2NGT72 on EQUIV. VOLTAGE Fa = v = CAPACITANCE VALUES IN uF. pS VOLTAGE ADJUST Re Dw. NOAEBSSA 1 vor2 tov [1 +82] CAPACITANCE VALUES IN uF. Dg No. AMBSS4B 4—96

POWER OPERATIONAL AMPLIFIER A TYPICAL APPLICATIONS SINGLE-ENDED POSITION SERVO WITH SENSE POTENTIOMETER FROM uP CONTROL SeDeGeCene ences B oa ADSSS. DIA oS e t £ Eiij 6V D-C MOTOR +5V0 T > eo aa a | postTion-sEnsine i = zr [| POTENTIOMETER Fpl Sie i = a \\ ; 4, 1 \\ 01 1 ! T 1 ! - Lo ECHAMOML DRIVEL RI, R2 DEFINE D-C GAIN, R3, Cl PICKED TO PROVIDE LOOP COMPENSATION. CAPACITANCE VALUES IN uF. wg No. 12556 ‘SIMPLIFIED SERVO APPLICATION WITH CONTROL TRANSFORMERS conTROL, CONTROL reANeuitren —reaNStORaee oe et seavo Bi OE Oxo. / / ssntean —/ £ ~~~ input 4S Néte f ee] tes ng No. 14280 497

DUAL POWER OPERATIONAL AMPLIFIERS LL SS ULN-3753B AND ULN-3753W DUAL POWER OPERATIONAL AMPLIFIERS © Operating Supply Range +3V to +20V + s]- © Output Current to +3.5A Peak Oy gin vsuestaare © Output-Current Limiting oureuTLay OUTPUT * Output-Current Sensing CURRENT SENSE[S } 117 CURRENT SENSE, © High Output-Voltage Swing r : anit fa + {ou Creare Paterton ~vgsvasreae | © -vgsunsrasre © Externally Compensated © High Open-Loop Bain COMPENSATION ry aN LSP COMPENSATION © Output Protection Diodes INV. INPUT! | | ae INPUT © Thermal Shutdown Protection © Excellent Supply and Common-Mode Rejection NONI Ne NOMI INEST Single or Dual In-Line Power Packages Dwg, No, A-13, 636 ULN-3753B © Dual Hali-Bridge and Full-Bridge Motor Drivers Linear Servo Motors Voice Coil Motors ‘@ O AC and DC Motors Microstepping Applications © Power Transconducting Amplifier © Audio Power Amplifier, Stereo or BTL © Power Oscillator/Amplifier ’ © Dual Bipolar Voltage Regulator [7 ) High-current linear servo loads, such as voice coil motors used in disc-drive applications, are ideal iW 7 applications for the ULN-3753B and ULN-3753W ge 225 FF 53355 dual high-power operational amplifiers. Their building Be Ee EgEe+E S FE; 22 block design concept also makes them ideal for a Zz 2 3 5° 8 ° E22 wide variety of other motor drive applications, audio z Zz: 2 2 8 power amplifiers, power oscillators, and linear volt- 2 o8 ' 88 e age regulators. External compensation permits user Dwg. No. A+13, 622 adjustment of bandwidth and phase margin at any ULN-S753W gain level. single supply applications) to within approximately The ULN-37538 is furnished in a 16-pin dual in- 2V of the positive supply. Common-mode and power line package with copper heat-sink contact tabs. For —_ supply rejection are in excess of 60 dB. The ampli- higher power requirements, the ULN-3753W is fiers’ wide output swing is complemented by current supplied in a 12-pin single in-line power tab package. sensing, which is referenced to the negative supply The inputs are designed to allow a wide common and allows for feedback as required to produce a mode range from the negative supply, (or ground in transconductance characteristic. 4—98

DUAL POWER OPERATIONAL AMPLIFIERS a The ULN-3753B (batwing DIP) can typically dis- ABSOLUTE MAXIMUM RATINGS sipate 6W at a tab temperature of 70°C. The lead layout. The ULN-3753W (SIP) can safely dissipate Continuous Output Current, four is = ey 3 oA significantly higher power levels with appropriate Pe: se =e heat sinking. With either package configuration, the Package Power Besant Pp. . cereses See Graphs heat sink is at the negative supply, or at ground ina Operating Temperature Range, Ta.... —20°C to +85°C ALLOWABLE AVERAGE PACKAGE POWER DISSIPATION AS A FUNCTION OF TEMPERATURE. ULN-3753B ULN-3753W . aw , 26 . = Lb 7 . é < 4 a e Ve = ro 3 \\s Lv z Ni E | = Ne a Mi \\ aN \\ 2 | 4 e | NG 5 3 Ne 4

2 Le %

Es a ‘ a Yoo h 3D Noo} Ne s a ‘. i 2 aoe y = Cy. S48 = eh Ne V 4 ~ @ \\ \\ Se > 52 Ss, 2 sp m $190 g “ered MS |S Z i * 290 ‘.. ant z Spe | oy | PN 1 aa SS 8, ON aA See TSN Sigh m3 0 0 : 3 30 75 100 160 B 50 75 T00 15 150 TEMPERATURE IN °C TEMPERATURE IN °C Ong. No At, 7838, Dig No, At 7888 4—99

DUAL POWER OPERATIONAL AMPLIFIERS ny ELECTRICAL CHARACTERISTICS at Tx = +25°C, Tras <+70°C, Vs = +6V, Co = 0, each amplifier tested separately (unless otherwise specified) Test Conditions |_in. Typ. Max. [Units _| Functional Supply Voltage Range Quiescent Supply Current Vour= Ola = 0 Over Op. Temp. Range [input Offset Current | Vor= Olur=0 =| S| | [Input NoiseCurrent®™ | 8W= 40HetotoxHe ———SS«dY SSCS | Common Mode Rejection” [Vew=3V SSCS SC Input Common Mode Range* Open Loop Vatage Gain Hes er Slew Rate : [Channel Separation” [lar = tomAf= te «| SiS | [OstoutVotage Swing [lr=1A_—SSCSCS~SCi | Supply Voltage Rejection +Vs, AV = 1V [60 5 s—CS dCi ]SCXd Serene ive | Thermal Resistance, Our ULN-3753B [Dente 6 liners a (ThemalShutdowatems” —[ SSCSCSSC~‘iSC“‘ HCY! “This parameter is tested to a lot sample plan only. “Typical values given for circuit design information only. NON-INVERTING AMPLIFIER INVERTING AMPLIFIER a7 Riv Re Eour : St ist Re Ry = Eo _ _ Be Eour Re Ew Rin Dwg. No. WHIS6 Ev 7 * Re IF Re = Oor Ry = %, Eour = Ein Dwg. No. W185 4—100

DUAL POWER OPERATIONAL AMPLIFIERS A TYPICAL CHARACTERISTICS OPEN-LOOP VOLTAGE GAIN AS A FUNCTION OF TEMPERATURE ET TT Fe et} | Pe Pr) ws g 60 8 40 Fry a o -20 oO 20 40 60 80 100 4 TEMPERATURE IN °C. ws. No, Wise SUPPLY CURRENT AS A FUNCTION OF SUPPLY VOLTAGE DIFFERENTIAL 140 | | | eo tt] | | Te tL | LEFT = 10 —r | Pollet TT 3 8 a a ett t ty ty OEE TTT TT a~ALT TT | | tf | ° 5 a 5 20 25 30 35 40 50 SUPPLY VOLTAGE DIFFERENTIAL, 4Vs IN VOLTS Dg, No. Wa61 4—101

DUAL POWER OPERATIONAL AMPLIFIERS GANS TYPICAL CHARACTERISTICS INPUT BIAS CURRENT AS A FUNCTION OF TEMPERATURE -20 2-40 3 -60 Fa g Fs 5-00 —100 -120 -20 oO 20 40 60 80 100 TEMPERATURE IN °C Dig No. so INPUT OFFSET VOLTAGE AS A FUNCTION OF TEMPERATURE : | 5.0 | | | ff z z uw 40 > 30 © 20 [~~ = 1.0 -20 o 20 40 60 80 00 TEMPERATURE INC og. No, W960 4—102

DUAL POWER OPERATIONAL AMPLIFIERS. ed I s © @ py | JoveR-cunREN AND THERMAL H D/A t SUB contre @ Cc Te | + © ® ® H i | 1 t \\ ' sup | sa! F 1 i LOO OF - wg, No. WH6S FIGURE 2 DIGITALLY CONTROLLED POSITION SERVO Ina position-contro! application, a microprocessor protection, matching and thermal tracking inherent is often used to control a servomotor's shaft angle to monolithic construction. The configuration shown or to control position as in a disk drive application. in Figure 2 uses a ULN-3753W dual power opera- The circuit requires small-signal input op amps, tional amplifier whose two independent outputs are drivers, and power output stages. The circuit derives connected in a push-pull, H-bridge arrangement. its input from the D/A converter whose output is The IC's outputs also include clamping diodes with determined by a code from the controlling micro- current-handling capacity equa! to that of the output processor and related digital control circuitry. The drivers. sensed position signal normally undergoes pro- cessing and comparison with the desired position, The current-sense pins (4 and 9) provide access through the microprocessor system that produces to the emitters of the H-bridge current sinks, thereby an error signal to control the servo amplifier’s output. providing convenient output current sensing, while The circuit includes thermal and short-circuit allowing separate low-current signal ground returns. 4—104

DUAL POWER OPERATIONAL AMPLIFIERS aS re) ev %e) «ok . am 3 56.F 56,F to 2 oer 5 8 + Th Vv q a } > apo | 10K ona O-sv = / = O -8v CR / 10K / Onur r (A wororisatose toonsssiiavog) + Re Ry, + 4 ug. No. 68 FIGURE 5 DC MOTOR SPEED CONTROL In addition to the synchronous ac motor drives tiometer at the amplifier's noninverting input. The described above, the ULN-3753B/W can be used motor speed, in rpm, is given by the following to provide accurate speed control of dc motors. Fig- expression: ure 5 shows a closed-loop system for controlling the = Vex , speed of a 12V de motor. The circuit provides bidi- S = Veer(Rr + Re)/.0027 Re rectional speed control. The amplifiers’ push-pull The ReC; feedback network prevents oscillation configuration ensures a full rail-to-rail voltage swing by compensating for the inherent dynamic mechan- (minus the output stages’ saturation drops) across ical lag of the motor. The RrCr time constant is the motor in either direction. selected to match the particular motor’s response The circuit uses a mechanically-coupled tach- or dynamic time constant. This should yield a good ometer to provide speed-stabilizing feedback to the starting point for stabilizing the system with optimum first amplifier section. The motor's speed and direc- response achieved by varying the compensating tion of rotation is set by adjusting the 10k poten- capacitor. 4—~106

DUAL POWER OPERATIONAL AMPLIFIERS ee] ULN-3755B AND ULN-3755W DUAL POWER OPERATIONAL AMPLIFIERS % =v, /SUBSTRATE © Operating Supply Range +3 to +20 Volts © Output Current to +3.5 A Peak oureut [ag jourpur © Output Current Limiting cunaent sense [3] CURRENT SENSE @ Output Current Sensing @ High Output-Voltage Swing % . © Low Crossover Distortion M5 /SURSTRATE we | ne tRTRATE © Low Input Offset Voltage © Unity-Gain Stable Vacosr Lg vy @ High Open-Loop Gain soos rN LS] Boost © Output Protection Diodes INVERTING INPUT a | |e INVERTING INPUT @ Thermal Shutdown Protection NON-INVERTING Cat {5} NON-INVERTING Excellent Supply and Common-Mode Rejection wwpuT wNPUT ‘@ Single or Dual In-Line Power Packages ULN-3755B >¥3-No.A52.089 @ Dual Half-Bridge and Full-Bridge Motor Drivers Linear Servo Motors Voice Coil Motors AC and DC Motors Microstepping Applications © Power Transconductance Amplifier @ Audio Power Amplifier Stereo or BTL © Power Oscillator/Amplifier © Dual Bipolar Voltage Regulator I Consisting of two high-power operational am- A BER: & PR e B38 3 plifier circuits in a single in-line power-tab pack- oe ht 228 & af Mee age or a batwing dual in-line package, the ULN- BE: FA Fe 8 EE 3755B and ULN-3755W are specifically designed 38 5 2 3 $2 to drive high-current linear servo loads such as z _ z voice coil motors used in disc-drive applications. = ws. No. ateoee Their building block design concept also makes ULN-3755W " them ideal for a wide variety of other motor drive applications, for use as audio power amplifiers, The ULN-3755B is furnished in a 16-pin dual in- power oscillators, and linear voltage regulators. _ line package with copper heat-sink contact tabs. Low crossover distortion eliminates servo hunt- For higher power requirements, the ULN-3755W ing under null conditions and is required for _is supplied in a 12-pin single in-line power tab most audio applications. package. Continued next page 4—107

DUAL POWER OPERATIONAL AMPLIFIERS SS The inputs are designed to allow a wide com- printed wiring board layout. The ULN-3755W. mon mode range from the negative supply, (or (SIP) can safely dissipate significantly higher ground in single supply applications) to within power levels with appropriate heat sinking. With approximately two volts of the positive supply. either package configuration, the heat sink is at Common-mode and power supply rejection are the negative supply, or ground in a single-ended in excess of 60 dB. The amplifiers’ wide output application. swing is complemented by current sensing, which is referenced to the negative supply and allows for feedback as required to produce a ABSOLUTE MAXIMUM RATINGS transconductance characteristic. Supply Voltage Differential (+V, to —V,) .. 40V level input and high-level output circuits to allow Continuous Ouput Current voitage boost or bootstrapping to maximize out- four (Vg = H15V) occ cece £2.04 Put swing. (V5 = #6V) oo 25A lead configuration enables easy attachment of a Operating Temperature Range, T,.. —20°C to +85°C heat sink while fitting a standard socket or Storage Temperature Range, T; ... —55°C to + 125°C ALLOWABLE AVERAGE PACKAGE POWER DISSIPATION AS A FUNCTION OF TEMPERATURE ULN-3755B ULN-3755W A 2 s z° ‘ BB \\ - a oa Ye z - | zg Ve, Ve S> & \\, \\ z é | OY 2 aIN = 5 wo Sp B ‘ 1 = Sy nN ‘ i 8 3p Noo, Zi \\, 8 ‘< KN z se Ke) Bi Xe, aay Fa fe Ne \\ = Cn, yt = Sg NE \\ ay <6 am ge > se SS, 2 sh 24 ‘ 2 “AEN DSE ‘. = fein | SEs ‘ s 4 sa, ‘. EE} 2 8 S, \\ E aNzsced s LY Z 2242 . at costa LN Sv | WO NA 1 an “ast OSD NA SRY SA, ve “Sey “hs 0 3 a 30 75 100 1 150 3 Te a TEMPERATURE IN °C TEMPERATURE IN °C wg. Ne As 798 Dg. No, A1.2648 4—108

DUAL POWER OPERATIONAL AMPLIFIERS i ELECTRICAL CHARACTERISTICS at T, = +25°C, Try = + 70°C, Vs = +6.0V, Veoosr = +9.0V, each amplifier tested separately (unless otherwise specified) Pr ee ee Characteristic Test Conditions Functional Supply Voltage Range Quiescent Supply Current [+b (ota) 5 180m Vour = 0, tour = 0 a [Input Noise Voitaget | BW = 4OHzto toe | [nputNoise Currentt | BW = aOHztotbKHe | [ Crossover Distortiont | Por = SOmWR =A | RT [Open-LoopVoltageGain | f=o Tt TY [Channel Separationt | w= 100mAf=thHe | 0 a ese ee lour = 1A, Vocosr = +9V Supply Voltage Rejection [+veavetv | 60s | Thermal Resistance, ©," [Thermal Shutdowntemot | HO *This parameter is tested to a lot sample plan only. +Typical values given for circuit design information only. NON-INVERTING AMPLIFIER INVERTING AMPLIFIER Four Rn RE Four Re Ry = Four. _ Re Ew Rin ove No 8 Four ys Ew Py IF Ry = OorRy = @ THENE, w Ey brn to ter 4108

DUAL POWER OPERATIONAL AMPLIFIERS el TYPICAL CHARACTERISTICS INPUT OFFSET VOLTAGE AS A INPUT BIAS CURRENT AS A FUNCTION OF TEMPERATURE FUNCTION OF TEMPERATURE JTTTTT) JT TTT z 50 ¢ 20 et | | Up Py ey TT g 49] 2° 8 3.0 5 60 as : = 5 2 CN | | p¢ | 1 Do | pet 210 2 00 ee ee ee TEMPERATURE IN *C TEMPERATURE IN °C Dep. No A9.8e a, No. A. OPEN-LOOP VOLTAGE GAIN AND PHASE OPEN-LOOP VOLTAGE GAIN AS A AS A FUNCTION OF FREQUENCY FUNCTION OF TEMPERATURE 100 120 PINE | TT Td, : 2 80) 9 2100 ft IN | TT de Zz 60 45 2 60 & 6 z a ge 3 ws 2S ao Pt NAAN g 8 z 0 180 2 2 Pte | | | NT OE -20 5 ° 101 10? 108 104 108 108 107 220 ° 20 40 60 80 100 FREQUENCY, 4, IN He TEMPERATURE IN °C Dag. Ro. 3.208 Dog, Ne An3.97 4-110

DUAL POWER OPERATIONAL AMPLIFIERS ee aaenaiesnieinentsilaii TYPICAL CHARACTERISTICS OUTPUT VOLTAGE SWING AS A FUNCTION OF OUTPUT CURRENT Sal Loo 2 avs-2 i: é Veoost = Vs g eo oo a o 10 2.0 35 4 uteur cunecit 1 aweenes SUPPLY CURRENT AS A FUNCTION BOOST CURRENT AS A FUNCTION OF SUPPLY VOLTAGE OF BOOST VOLTAGE tT TI “EET TTT TT) Patt tte et Z 120) “19 — ; cl ft} gj | | pe .aae>= CCCP Eee Pdi ear eo ZT et EET TT TT a © 40 PT EE ? a0 B 20 ~liiT TTT) Ltt itt tl o 5 10 15 20 2 30 35 40 50 ° 5 10 15 20 2 30 35 40 50 SUPPLY VOLTAGE DIFFERENTIAL, QVs, IN VOLTS BOOST VOLTAGE, Vaoost, IN VOLTS ong mn ous ms se 4—H1

DUAL POWER OPERATIONAL AMPLIFIERS ST Current-Sense Transconductance Amplifier The ULN-3755B/W current-sense terminals can be used to obtain a transconductance func- tion. This characteristic is commonly used in +Ve motor control applications such as voice coil GF ARAL POWER servo or micro-stepping positioning systems ined eee | found in many computer disc drives. 1 H Figure 1 shows a ULN-3755W dual amplifier \\ a 1 connected as a transconductance amplifier. In veo! c_| R this example, amplifier B is used as a slave to REF H amplifier A. Feedback from the current sensing rn resistors (Rg) in the emitters of the output current 1 sinking transistors, is applied to the summing Vyo—! R network and scaled to the inverting input of am- H plifier A where it is compared to the input voltage. Vp, 1 The current sensing feedback imparts a trans- 1 1 toy ! Rp conductance characteristic to the amplifier’s LLL LW Ry ry transfer function. That is, the voltage developed al > across the sensing resistors is directly propor- R, tional to the output current. Using this voltage as Rg ia Rs a feedback source allows expressing the gain of the circuit as output current in amperes vs. input J 4 . voltage in volts. The gain thus assumes the di- Ve OR GROUND Vaer , mensions of a transconductance function, ex- pressed in mhos. uw No. 13.052 The negative-feedback forces the amplifier to adjust the output current to attain a value such that the feedback voltage equals the applied FIGURE 1 input voltage. The transfer function of the trans- CURRENT-SENSE TRANSCONDUCTANCE AMPLIFIER conductance amplifier is approximately: 1. = (Viv — Veer) = Re/ReRs. In the figure, resistors R,, Rs, and Rs define the transconductance gain. To avoid limiting the transconductance amplifier's output compli- ance (swing capability), fow-value current- sensing resistors (R.) should be used. ‘ 4—112

DUAL POWER OPERATIONAL AMPLIFIERS A Digitally Controlled Position Servo In a position-control application, a micropro- The circuit includes thermal and short-circuit cessor Is often used to control a servomotor's protection, matching and thermal tracking inher- shaft angle or to control position as in a disk drive ent to monolithic construction. The configura- application. The circuit requires small-signal tion shown in Figure 2 uses a ULN-3755W dual input op amps, drivers, and power output stages. Power operational amplifier whose two indepen- The circuit derives its input from the D/A con- dent outputs are connected ina push-pull, verter, the output of which is determined by a H-bridge arrangement. The IC's outputs also code from the controlling microprocessor and include clamping diodes with current-handling related digital-control circuitry. The sensed po- capacity equal to that of the output drivers sition signal normally undergoes processing and The current-sense pins (4 and 9) provide ac- comparison with the desired position, through cess to the emitters of the H-bridge current sinks, the micro-processor system that produces thereby providing convenient output current an error signal to control the servo amplifier's sensing, while allowing separate low-current sig- output. nal ground returns. gvs 9 Veoost Lt | 4 ronnie PoP i FROM POSITION SENSE ' 1 i © > © I {fver-cunne eo "AND THERMAL = 1) Protection | ve . OA ee, eS nO ® T i | i 1 z i suB sel = t i LOO = Dwg. No. W-123- FIGURE 2 DIGITALLY CONTROLLED POSITION SERVO 4—113

DUAL POWER OPERATIONAL AMPLIFIERS eS Increased Output-Voltage Swi: re: utput-Voltage Swing +Vs Ifa voltage higher than the supply is applied to e) the ULN-3755W's boost pins, as shown, the pos- itive output swing is limited only by the saturation resistance of the output transistors (typically less than 0.5 ohms). For example, with a 12V supply, the circuit typically supplies a 10.5 Vp output swing at 1A output current. Note that the exter- nally-supplied boost voltage should be at least 3 V higher than the load supply voltage. This crite- 4 >) - rion satisfied, the boost voltage can be any value @ ® ce 71 + it within the IC’s 40 V absolute maximum rating. 1 Although the boost feature provides important ' additional output swing at the amplifier’s full 6) rated current, the IC’s boost input requires only alow, unregulated current. This can be obtained cb from inexpensive, modular dc to de converters, +Vs C) a simple overwinding in the motor, or a voltage doubler from the motor's driven phases. T An example of a simple voltage doubler boost (8) supply is shown in Figure 3. This circuit affects T the doubling by connecting a series diode- 1 capacitor between the main supply and each Dwg. No. 13,088 end of the load. FIGURE 3 VOLTAGE DOUBLER BOOST SUPPLY 4—114

DUAL POWER OPERATIONAL AMPLIFIERS. a _E_EE EEO Because of its high amplification factor and built-in power-output stage, an integrated power son 509 ny 2K operational amplifier makes a convenient driver for ac motors. One op amp can be configured as [| ford vm| oe Re an oscillator to generate the required ac signal. en os < oi The power-output stage, of course, supplies the ig Bri high-current drive to the motor. bd oe | O ls £ see As shown in the motor-drive circuits in Figure x4. gy OE 4, the controlling op amp is configured as a i rt fe 03s" ass Weinbridge oscillator. The R.C,, R,C, feedback - pel* gs networks determine the oscillation frequency, ~ according to the following expression Dwg, Wo, 18.088 f, = W(2n RRC) FIGURE 4a By varying either R, or R,, the oscillator fre- TWO-PHASE 60 HZ AC MOTOR DRIVER quency can be adjusted over a narrow range. son son, Ry 8.5K The R,/R, ratio sets the second amplifier's gain ‘3 on to compensate for signal attentuation occuring q roe 20) (3 oe in the phase shifters. A separate boost supply) Digi tye | 4 can be used to obtain additional output-swing cn be Fs capability. Las Toes ” aK The circuits can be driven from an external eos] gaz oR ¥ —~ source, such as a pulse or square wave, setting T = = - the gain of the left-hand amplifier to a level less == = Oak ooze than that required for oscillation. The RC feed- wa nev8080 back networks then function as an active filter causing the outputs to be sinusoidal. FIGURE 4b THREE-PHASE 400 HZ AC MOTOR DRIVER APPLICATION TIPS 1. Due to the nature of the composite PNP/NPN output structure, all applications of these devices require use of an output R-C compensation network, as shown in Figures 2, 4, and 5. Values shown are typical and will vary somewhat depend- ing on load impedance. 2. Asis the usual practice in high-gain power circuits, input and output grounds should be kept separate. 3. The current sense pins are the emitters of the power driver output totem poles and must be grounded or returned to the negative supply if not used for current sensing. 4, Provide good high-frequency supply bypass (ceramic or film capacitor). 5. Allinput, output, and supply leads should be properly dressed and kept as short as possible. 6. If the boost or bootstrapping capability is not used, the boost pins must be connected to the positive supply. 4—5

DUAL POWER OPERATIONAL AMPLIFIERS el {n additional to the synchronous ac motor mechanical lag of the motor. The R-C; time con- drives described above, the ULN-3755B/W can stant is selected to match the particular motor's be used to provide accurate speed control of de response or dynamic time constant. This should motors. Figure 5 shows a closed-loop system for yield a good starting point for stabilizing the sys- controlling the speed of a 12V de motor. The tem with optimum response achieved by varying circuit provides a bidirectional speed control. the compensating capacitor. The amplifiers’ push-pull configuration ensures ww a full rail-to-rail voltage swing (minus the output stages’ saturation drops) across the motor in g either direction, z a The circuit uses a mechanically-coupled tach- eK Sea ‘0: Can ometer to provide speed-stabilizing feedback to 6 “4 “J 1a PS au - the first amplifier section. The motor’s speed and v oe, a F direction of rotation is set by adjusting the 10k oy OF g potentiometer at the amplifier’s noninverting on input. The motor speed, in rpm, is given by the ts (7) rt following expression: Re = S = Voer(R, + R,V/.0027 R, + MOR ee wg. No, 13.09 The R.C, feedback network prevents oscilla- FIGURE 5 * tion by compensating for the inherent dynamic DC MOTOR SPEED CONTROL, MOUNTING POWER TAB ‘W’ DEVICES Power-tab packages are efficient thermal dissipators when properly utilized. In application, the following precautions should be taken: | 1. Always fasten the tab to the heat sink before the leads are soldered to fixed terminals. 2. Strain relief must be provided if there is any probability of axial stress to the leads. 3. Thermal grease (Dow Corning 340 or equivalent) should always be used. Thermal com- pounds are better heat conductors than air but not a good substitute for flat mating surfaces. 4. The mounting surface should be flat to within 0.002 inch/inch (0.05 mm/mm). 5. Brute force mounting to poorly finished heat sinks can cause internal stresses which damage silicon chips and insulation parts. Mounting torque should be between 4 and 8 inch pounds (0.45 to 0.90 Nm.) 6. The mounting holes should be as clean as possible with no burrs or ridges. 7. Use appropriate hardware including a lock washer or torque washer. 8. If insulating bushings are used, they should be of dialyphthalate, fiberglass-filled polycar- bonate, or fiberglass-filled nylon. Unfilled nylon should be avoided. 4—1l6

DUAL PERIPHERAL /POWER DRIVER el UDN-5725M DUAL PERIPHERAL/POWER DRIVER —Enhanced Output Capability FEATURES ease Oy [3] veo * DTL/TTL/PMOS/CMOS Compatible 4 | U [ * Low Input Current neers Cag Y pe + Continuous Output Current to 1A outers [BG 7 _ 7X pS ourure #70 V Outout Standoff Voltage ROUND aS P * Low Supply-Current Requirement wg, No, 13,242 The UDN-5725M power driver combines NAND lamps with peak load currents of up to 1.2A. ang NOR logic gates in a configuration particularly Each of the output transistors is capable of sink- useful with small brushless de motor drivers. The ing 800 mA continuously at 55°C, or 650 mA at integrated circuit includes high-current saturated gsc In the OFF state, the drivers will withstand output transistors and transient-suppression at jeast 70 V. diodes. It can be used in many applications beyond the capabilities of standard logic buffers: The UDN-5725M is supplied in a miniature 8-pin With inputs tied together, one of two loads is dual-in-line plastic package with a copper lead energized by a single input signal. frame for superior package power dissipation Additional applications include driving pe- ‘atings. ripheral loads such as solenoids, light-emitting For applications requiring output currents of up diodes, memories, heaters, and incandescent to 700 mA, Series UDN-5740M is recommended. ABSOLUTE MAXIMUM RATINGS atT, = +25°C Output Off-State Voltage, Vow ....eeeeeveeeceeee ce TOV Output On-State Sink Current, Igy (continuous) ceeeeee venues 1.0 AT (peak) vee cece ee LOA Logic Supply Voltage, Voc. bees bees . BY Suppression Diode On-State Current, lox. . sect reece veee 1.04 Allowable Package Power Dissipation, Py... . eves oe 15 WT Operating Free-Air Temperature Range, T, ese, = 20°C to +85°C “*Derate at the rate of 12.5 mW/9C above T, = +25°C. ‘Limited by Pp, 4—117

DUAL PERIPHERAL/POWER DRIVER SS ALLOWABLE AVERAGE PACKAGE POWER DISSIPATION ‘AS A FUNCTION OF TEMPERATURE E20 TYPICAL APPLICATION = A z \\ o 5 \\ ENABLE O ae ae OVec=12V a & 1.0) \\ mh 15) w t go Sg 0.5 18V QO N. < ‘ O Vs =12V Ww x. A 5 a \\ go wg, Na, 19,064 ic} ° 25 50 75 100 125 150 Zz AMBIENT TEMPERATURE IN °C Dg. No, 19,248 RECOMMENDED OPERATING, CONDITIONS Operating Condition [Min Wom. Max. [__Unils _ Supply Vottage, Voc 475 12 4 Output Current, Tow Operating Temperature Range 0 +25 +85 TRUTH TABLE STROBE PHASE INPUTS OUTPUTS INPUT 1 2 1 2 H x H Lou H H L Lou H L L ROL H L H HOH L x x H_H 4—118

DUAL PERIPHERAL /POWER DRIVER A ELECTRICAL CHARACTERISTICS over recommended operating temperature range (unless otherwise noted) Test Conditions | Somint_| Temp. | vg_"inpt |i owput| in, Typ, wa | unis | nas Output Reverse [475 [osv| 20V[ mv [=~ t00 [AT = | Current [osv[osvT ov { — = 100 [wa |= Output Vottage {20v[20v[o6a[ = 04 06 [ Vv [=| [20v| 20V[oBA[ = 07 40 Fv [4 [20v[2ov[ioal — os 12 v3 | [ 4 [20vosv[osa yt — 0406 | v [= | [4 [20v[osviosal = 07 40 [ v= | [ 14 | 20v[oav[ioa]| — os 42 [|v [3 | | Vorwy [+25°C[ 14 [= 1} ov[osal $0 ~ = Jv 34 | [4 [7 tf 2oviosa | a= v3.4 | iS eee Vw [| = [= [av | — [6 foav{ gov = [= soe A [yy [= [6 | sov | ov y= 605 AT Enable Input [uy | = [126 fosvy ov = [=o 0 A | Grew H§ efor or =} = | Input Clamp Vor [Vane [=| 4.78 [=tamal— [= =v =] a ad Current Diode Forward Vv +25°c/ 5.0 | ov{ ov[osal — "is 20 [vt | ome YP yee = Supply Current +25°C| 126 | OV] ov ~ [= 39 50 | mA [= | {Total Package) [| [126 | ov| 20v{ — | — 39 6.0 ma | = | [ee | +25eC| 126 | 20V[ OV =f — a 30 [maT | NOTES: 1. Except ENABLE input, each input tested separately. 2. Diode leakage current measured at V, = 70 V. 3. Pulse Test. 4.L, = 3mH. 4-119

DUAL PERIPHERAL /POWER DRIVER Leen a eee SWITCHING CHARACTERISTICS at T, = +25°C, Voc = 5.0 V [limits Characteristic | symvot | Test Conditions [ Min. Max. | Units | Tum-On Delay Time | to |Vs=30V,R, = 100(10W),C, = Spr) — S00 | ms | 1,2 | Tum-Off Delay Time Vs = 30V, R. = 100 (70 W), 0, = 15 oF NOTES: 1. Capacitance value specified includes probe and test fixture capacitance, 2. Voltage values shown in test circuit waveforms are with respect to network ground. 24V Voc OPEN Vs tr te jours Hl) ont’ tea GENERATOR 50% cL ted ‘tpdo 508 T = = = OUTPUT 2 50% \\ Dg, No. 18288 wg. No. 93288 INPUT-PULSE CHARACTERISTICS Vivo = OV { = 7ns = 1 ys Voy = 35V t= 1408 PRR = S00kHz 4—120

QUAD HIGH-CURRENT DARLINGTON SWITCH eS UDN-7078W QUAD HIGH-CURRENT DARLINGTON SWITCH FEATURES. © Output Voltage to 90¥ O @ © 90V Sustaining Voltage Output Current to 3A ‘TTL, DTL, or GMOS Compatible Inputs « Internal Transient-Suppression Diodes V co \\/ * Plastic Single In-Line Package i> * Heat-Sink Tab 2 This quad Darlington array is designed to serve as inter- i i g fh A by face between low-level logic and peripheral power GND B; C; Cz Kiz Bz Bs Vs Cs Kou G: Be devices such as solenoids, motors, incandescent lamps, : heaters, and similar loads up to270 W per channel. The wp. No. DS016 integrated circuit contains internal transient-suppres- sion diodes that enable use with inductive loads, The input logic is compatible with most TTL, DTL, LSTTL, and $V CMOS logic. The Darlington array is rated for operation to 90V and is recommended for ABSOLUTE MAXIMUM RATINGS operation with load currents of 3 A or less. Ot Te < +70°C For maximum power handling capability, the device is supplied in a 12-pin single in-line plastic package with Output Voltage, Vox tet eeeeeee eens av an integral power tab. The tab is at ground potential Min Sustaining Vag, as freee PH required for proper operation of this device. Supply Voltage, cos lov vite : . Input Voltage, Vy... feet tee renee IBV operation with supply voltages to SOV or 80V (35V or Operating Temperature Range, ++ 20°C to 485°C 4—121

QUAD HIGH-CURRENT DARLINGTON SWITCH emma! Vs 9002 PARTIAL SCHEMATIC k One of 4 Drivers 8 23K c t t 7.2K H i a 3k we. Ne Azo ELECTRICAL CHARACTERISTICS at T, = + 25°C, Ty, < +70°C,V, = 5V Fs re ree es Characteristic symbol Test Conditions Output Leatge Cuet a se Output Sustaining Voltage = 258 o -f[¥ Output Saturation Votage sn I= 05 A, y= 2.75 - uly = LOA, Vy= 2.759 v = 20 A Wy= 2758 [- 16 |v ee Lb= 25 A Wo 275V v Input Vage e308 v [en | Input Curent In wen W= 2750 Y= 3.750 = 10 Supply Gurent per Driver a | i= 500 mk = 60 | ma | Clamp Diode V,=90¥ — 0 | aA Leakage Current clamp Diode % Pensa ts Forward Vltage SEXY) Daa Turn-On Deley tho 0.5 fy t0 0.5 Ee ;- 10 | ws Turn-Off Delay 05 Eto 0.5 Eye, em 3.0 A 1s CAUTION: High-current tests are pulse tests or require heat sinking. 4122

QUAD HIGH-CURRENT DARLINGTON SWITCH SSSA ALLOWABLE AVERAGE PACKAGE POWER DISSIPATION ‘AS A FUNCTION OF TEMPERATURE FN TEST FIGURE , ‘ 2 ol 2 v ‘ a ¥, +90) H \\ Fa on 4 24 , ‘ +8V 2.5 mH an) i “OY 278V- 8 <2 iN : 362 g Xen | Nf Fa <a Noh zh ot AL ov

5 Sean | SS t

re [OTN sm, ‘sl OM Dwg. No. BS-1016 Mest . mos Sa | 4 TEMPERATURE IN °C . Do, No. ASIA TYPICAL APPLICATION PRINT-HAMMER DRIVER =O ommeme) fo} INy IN2 IN3+5V. INg 1 3oV 3 4 O + 36V wg. No. 081017 4123

HIGH-CURRENT INTERFACE DRIVERS ES POWER INTEGRATED CIRCUITS FOR MOTOR-DRIVE APPLICATIONS [MPROVED SYSTEMS PERFORMANCE microprocessor-controlled servo and stepper and reliability, lower component counts, and motors. reduced cost are among benefits offered by space-saving Sprague power interface ICs. Combining logic, power, and control in an Many of the following devices are specifically integrated circuit requires special design tech- designed for motor-drive applications. The niques and experience. Sprague Electric has development of these devices is especially sig- Jong been a leader in peripheral power interface nificant in view of the increasing use of technology. UCN-4204B AND UCN-4205B STEPPER-MOTOR TRANSLATOR/DRIVERS UN 12048 & UCN-4205B INTEGRATED ion, and step-inhibit are selected by connec- circuits drive permanent magnet stepper tions at pins 9 and 10. The sequence of states is motors rated to 1.25 A and 30 V with a minimum determined by the DIRECTION CONTROL (pin of external components. 14). Internal step Jogic activates one or two of the RECOMMENDED MAX. OPERATING CONDITIONS four output sink drivers to step the load from Output Voltage, Voy: (UCN-42048) occ. eee ceca 15V when STEP INPUT (pin 10) is allowed to go HIGH. Output Current, lor... c eee cece eee eres eee ee L25R CD), or half-step (A-AB-B-BC-C-CD-N-DA) opera- Input Voltage, Vy ee... e eee cece eect DOV L/R STEPPER-MOTOR DRIVE +BY FINS PIN 10 ? i i TWO-FHASE L t | ; | ONE-PHASE =H t HAce-ste> 5 E STEPINHIBIT Hi 4 Hae: 7 HL 2 ee co Gee pip bened | > a a UcN-42048 bana bie 4—124

HIGH-CURRENT INTERFACE DRIVERS a UDN-2953B AND UDN-2954W FULL-BRIDGE MOTOR DRIVERS THE UDN-2953B AND UDN-2954W are designed for bidirec- . tional, chopped-mode current control of d-c motors with peak start-up currents as high as 3.5 A. The output-current limit is deter- mined by the user’s selection of a sensing resistor. The pulse dura- tion is set by an external RC timing network. The chopped mode of operation is characterized by low power-dissipation levels and max- imum efficiency. Internal circuit protection includes thermal shutdown with hys- teresis, output transient-suppression diodes, and crossover current protection. The UDN-2953B is supplied in a 16-pin DIP with heat-sink con- tact tabs. The UDN-2954W , with increased allowable package power dissipation, is supplied in a 12-lead single in-line power tab package. In both case styles, the heat sink is at ground potential and needs no insulation. RECOMMENDED MAX. OPERATING CONDITIONS Continuous Output Current, lou... be eeeeeee es B20K Logic Supply Voltage, Ves... see eee eee ++ 45 V to 15V +5V UDN-2953B +36V l a 13} rare oY | PALE mae = mo EE PHASE © ic ENABLE o fa} | (ACTIVE Low) np. Wo. A12,649 4—125

HIGH-CURRENT INTERFACE DRIVERS eT UDN-2878W AND UDN-2879W QUAD DARLINGTON SWITCHES Tre UDN-2878W AND UDN-2879W drive motor windings at up to 200 watts per channel. The integrated circuits include transient-suppression diodes and input logic that is compatible with most TTL. LS TTL, and 5 V CMOS. The 12-pin single in-line power-tab package allows maximum power-handling capability. RECOMMENDED MAX. OPERATING CONDITIONS Load Voltage, Vec (UDN-2878W) sees seteeeee es BEV (UDN-2879W) Pe reerrerry 50¥ Continuous Output Current, |p... 66. eee eee cccecee eee 4A Peak Output Current, lop... 0eeee ee vevceee neces SA Input Voltage, Vy... -- see ceseeceeeeeeene es Vs STEPPER-MOTOR DRIVE UDN-2878W 2-PHASE, UNIPOLAR INPUT WAVEFORMS V V x ol AT mie. es ¥ Y bd Lorna ag. No. A114 795 as *28V rely} O48, NO, H013,978 4—126

HIGH-CURRENT INTERFACE DRIVERS SSS UDN-2965W-2 DUAL HIGH-POWER MOTOR DRIVER [iE UDN-2965W-2 INTEGRATED CIRCUIT drives stepper motors in the full-bridge configuration. It is a high-power, multi-function interface driver that combines sink and source drivers, gain and level shifting, ther- mal shutdown circuitry, and pulse-width modulated current control. Output current, threshold voltage, and hysteresis are preset or may be externally set by the user. The UDN-2965W-2 is also well-suited for use as a dual high- power hammer driver. RECOMMENDED MAX. OPERATING CONDITIONS Supply Voltage Range, Vor -.-...e es eeeeeeeecceeeeeees 200 50¥ Output Current bors sees eee ceeteeeeseteeeeeeeses AOA Input Voltage, Vy... eee eee eee eee ees SOV BIPOLAR STEPPER-MOTOR DRIVE (Pulse-Width Modulated) +48V Ye UDN-2965W-2| Ve UDN-2965W-2 r q DP Ve TT 4 | | ! @ ! Smo BP _ i t a) a oe] | 1] 3s aly +5V ° fey +5V o | | 4 uw] Sy] ot ! | peed 1 i Rul 7, 1 ery 1 1 gRe IrHs. t ! 1 F Ltusl Lo see] L fesse $e zh OAR + L L + Ry AND Rr DETERMINE HYSTERESIS. AND PEAK CURRENT oN. sas 4-127

HIGH-CURRENT INTERFACE DRIVERS ST UDN-2993B DUAL FULL-BRIDGE MOTOR DRIVER THe UDN-2993B MOTOR DRIVER contains two independent H-bridges capable of operating with load currents of up to 600 mA. An internally generated deadtime prevents potentially destruc- tive crossover currents when changing load phase. Internal tran- sient-suppression diodes are included for use with inductive loads. Emitter outputs allow for current sensing in pulse-width modulated applications. RECOMMENDED MAX. OPERATING CONDITIONS Load Voltage Range, Veg... ee eee e eee cece eee eee sees LOVIO4OY Output Current, lour Seeks see ceeee ss eeeesansy +500mA Logic Voltage Range, Vog 2. ese ceceeveceeeeeeceeees 45Vt0 5.59 2-PHASE BIPOLAR STEPPER-MOTOR DRIVE (Pulse-Width Modulated) +5V +36V +5V om rn cc | 5.6K 5.6K en 0] — te ° 8 || 8 tayo CT ea sih 12 a Ce <J oe 470K 10K o1 10K 470K +5V0 1K sen L ng. Noe A253 +5V INPUT A +8V INPUT B fg. No Ae2s484 4—128

HIGH-CURRENT INTERFACE DRIVERS Ce UCN-5800A, UCN-5801A, UCN-5813B, AND UCN-5814B UNIPOLAR MOTOR DRIVERS DRIVING UNIPOLAR motors is one of many Date Packege Drivers Features successful applications for the UCN-S800A, JCN-58008.-—«depin DP =S:SCSC«Cer, Stabe, UCN-5801A, UCN-5813B, and UCN-5814B BIMOS Output Enable I latched sink drivers. Selected devices, for higher UCN-S801A -—22-pinDP_«=S«B~—SCiear, Strobe, voltage operation, are available as the UCN- Ouput Enable 5813B-1 and UCN-S814B-1. UCN-S8138 —«I6-pin DIP. A Strobe and All devices contain CMOS data Jatches, CMos —_‘UON-$8136-1 Output Enable vices conte 7 UCN-S814B -22-pin DIP = 4 lear, Strobe, contro! circuitry, high-voltage. high-current bipolar on 3s4B-1 Outpt Enable, Darlington outputs, and output transient protection & Chip Select : diodes for use with inductive loads, The UCN-S800A is a direct replacement for the _¢,,REMMEIDED MAK. OPERATING CONDITIONS original UCN-4401A. The UCN-5801A replaces the Pe eN-S80AR UCN-S8O1A 38y 12V, significantly higher speeds are obtainable. __Gontinuous Output Curret, lyn BiMOS IIT drivers, with output voltage ratings to UCN-S8OOA & UCN-S80IA. eee eeeeee es 350 mA 150V, will be supplied as UCN-5900A and UCN- UCN-S819B RUCN-SBMB ss LOA S901A. UCN-S8198-1 &UCN-SBI4B-1 LOA Input Voltage, Vy... ooo e eee ee ee ee Voy UNIPOLAR STEPPER-MOTOR DRIVE —*20¥ 4 OUTPUT ENABLE (ACTIVE LOW) rT | at our 6 fe Se aE we Ain oure Pe ae Ne AH our 4 ~UCN-58004 a a ne 23097 Lov UNIPOLAR WAVE DAVE UNIPOLAR 2-PHASE DRIVE 2 SL sce . soe SLL wr SL m1 ___ we we I ee ee ° ce ee m m ours ma —_— i ee i on ore rs a on, 7 a ore — — we we, Aaa se wane

HIGH-CURRENT INTERFACE DRIVERS Sey LINEAR MOTOR DRIVERS POWER OPERATIONAL AMPLIFIERS are useful in driving voice-coil motors, linear servo motors, and ac and de motors in a linear mode where motor speed or position is a direct function of a linear input signal. : The operational amplifiers listed here are standard ‘building block” circuits providing almost unlimited application. The high-gain, high-impedance opera- tional amplifier configuration allows many specialized input, output, and feed- back arrangements. All devices feature high output voltage swings, high input common mode range, high PSRR and CMRR. The unity-gain stable versions need no exter- nal compensation. Internal thermal shutdown circuitry protects these devices against output overloads. The dual amplifiers include programmable output current-sensing capability. Cont, Peak Engineering Part Number | Type lor les Features Package Bulletin ULN-3751Z Single | 28V | =25A | +358 | Unity-Gain Stable S-Lead SIP 2718.1 Internal Compensation ULN-37530 40v Prog. Current Sense, Tateadse | 2711810 ULN-37538 External Compensation 16-Pin DIP ULN-3755W 40V Bootstrapped Output, 12-Lead SIP 2718.11 ULN-37558 =10A | 35a | Unity-Gain Stable, 16-Pin DIP Prog. Current Sense POSITION SERVO FROM uP CONTROL Cee EC ecec Sree AD558 Re R4 D-TO-A 3 LSS SS TS | ote = R6 POSITION-SENSING “@: +5V0 POTENTIOMETER > <i On | 19 1 419 .001 t =I 008 o~ i | —9 R7 x e001 i] = On | o1 T T MECHANICAL DRIVE/ LINKAGE. R4=R5=R6=R7 R1, R2 DEFINE D-C GAIN R3, C1 SELECTED FOR LOOP COMP, og. Nata 4—130

HIGH-CURRENT INTERFACE DRIVERS ee TWO-PHASE, 60 Hz OSCILLATOR/MOTOR DRIVER 502 509 25K 12.4K + o- |12. O 12 é 033 8.2K 82k oF ak oT ro" i == ae? ] = 0.33 = Dwg. No, A=12,651 THREE-PHASE, 400 Hz OSCILLATOR/MOTOR DRIVER 502 508 615K Lee NC | =0° exe] 714] Sot a bree, -4 hoe WK 0.022 8.2K 01 + 7

0.008 T — T = 7° a

= L 82k 0.022 Dag. No, A-12,650 4-181

HIGH-CURRENT INTERFACE DRIVERS SS ULN-2074B AND ULN-2075B HIGH-CURRENT DARLINGTON SWITCHES THE ULN-2074B AND ULN-2075B high-current Darlington switches contain four isolated drivers. With appropriate input- level shifting, these devices can be used in emitter-follower (cur- rent-sourcing) applications. The X-drive circuit shown below operates in the full-step mode with two phases oN in each position. X-drive is energy efficient and has better positional accuracy and hysteresis characteristics than conventional drive circuits. RECOMMENDED MAX. OPERATING CONDITIONS Motor Supply Voltage, Ves ULN-2074B . fetes BBV Output Current, lus ULN-2074B fee eee eee eee L258 Input Voltage, Vy ULN-2074B sees . 30V ULN-2075B eee teeters SOV X-DRIVE MOTOR CONTROL saav | INPUT WAVEFORMS. ~~ eS? fee ) ete — ar ’ a: ‘ a4 | : x 20 hs <4 co ce) 5 * A Ee 7 Pom “STI “sy 1 ENABLE = Ig) Ao cs et —FR a UDN-3eTIM 4—132

HIGH-CURRENT INTERFACE DRIVERS ey UDN-2941B QUAD HIGH-CURRENT SOURCE DRIVER THE UDN-2941B high-current source driver has four independent emitter- follower drivers, associated input-level shifting, and output transient- suppression diodes. Special circuit design techniques result in reduced output- saturation voltages, and improved output-switching speeds. These two characteristics allow the UDN-2941B driver to operate high-current induc- tive loads at maximum efficiency. ‘Where increased package power dissipation ratings are required, the modified bat-wing ‘‘B”” package with a copper lead frame allows the attachment of an inexpensive heat sink. The heat sink is at ground potential and needs no insulation. RECOMMENDED MAX. OPERATING CONDITIONS MotorSupplyVoltage,Vop oo... ocecvveeceeeeeeeeeeses 12Wt030V Continuous Load Current, leur UUN-206BB eee eee vets eee eee ee eee ee LOSA UIN-2089B eect erect ee eee DBA Input Voltage, Vig... eee cece eee ees veces LV 4 FULL-BRIDGE MOTOR DRIVER (One of Two Windings Shown) +28 +5V ro) fe) INA O ULN-29688 UDN-29418 4 ULN-20698 EE EET eel Gl Lalla“ bal? hl hah Cero Vo. | ' ABA Pel | Lots PCP PPP) Er ene P E 4 INBO ovo, be, Biss 4—133

HIGH-CURRENT INTERFACE DRIVERS Dena nl UDN-2952B AND UDN-2952W FULL-BRIDGE MOTOR DRIVERS Tr UDN-2952B AND UDN-2952W power drivers provide bi- directional control of d-c motors operating with peak start-up ' currents as high as 3.5 A. These integrated circuits include extensive circuit protection. Both drivers have adjustable short-circuit pro- ‘tection, a thermal shutdown network that disables the motor driver if package power dissipation ratings are exceeded, and internal diode transient suppression. RECOMMENDED MAX. OPERATING CONDITIONS Continuous Output Current, lpyp- 6. e ee ee eee eee erence eee BQOA FULL-BRIDGE DC MOTOR DRIVE © Vpp=36V ea 33} © Vop=5V - nS | mt | (ACTIVE Low) “ Dwg.No. A-11,986 4—134

HIGH-CURRENT INTERFACE DRIVERS ey BIPOLAR STEPPER-MOTOR DRIVE UON-2952w UoN-2952W | ces | | so | ronan reine im +8y vf Sey Bh j ovrpur a oureur &. = 5 UCN-42024 2 +8v > }-—-"3 pte eb i Pot ae fa Sh gig sre input j a ee +5V STEP INPUT +8v INPUT & +8v INPUT B + ee | -J a L — —" - —___ a Dag. AL 982 NOTES: 1. This is not a bipolar, pulse-width modulated application. 2. Resistor Re sets the maximum allowable output current for protection against crossover currents and short circuits. Ry = 0.6/\\,yur 4—135

HIGH-CURRENT INTERFACE DRIVERS A UDN-2935Z AND UDN-2950Z HIGH-CURRENT BIPOLAR HALF-BRIDGE MOTOR DRIVERS T= UDN-2935Z_ AND UDN-2950Z ICs The UDN-2935Z and UDN-2950Z may be are monolithic half-bridge motor drivers in used in pairs (full-bridge) to drive d-c stepper power tab TO-220 style packages. The circuits motors or brushless d-c motors. combine sink and source drivers with diode Either power driver may also be used in step- vd 2 voltae 2 regulator for single- supply opera. per motor bipolar bridge circuits as, for exam- " : . ple, with the Sprague UCN-4202A or UCN- ton. They are Gesigned for servo-motor drive 4204B stepper motor translator/drivers. applications using pulse-width modulation. The PWM drive mode is characterized by RECOMMENDED MAX. OPERATING CONDITIONS Jows the output to switch currents of 2 amperes. Continuous Output Current, lour veces B2OA Output d-c current accuracies of better than Peak Output Current, loe . 1. 3.5 10% at 100 kHz can be obtained. Input Voltage, Vy... eee tere SOV SINGLE-WINDING DC OR FULL-BRIDGE DC SERVO-MOTOR DRIVE STEPPER-MOTOR DRIVE UDN-2950Z UDN-2935Z UDN-2950Z ca rom, AL cid cia | +30V 0 | | | Ih piRection o + +28V0 (R§) O+14V LI a) DIRECTION O SPEED Owg.No. Ae12,114 (wm) ° Dag.No. Ae12,115 4—136

HIGH-CURRENT INTERFACE DRIVERS cs 3-PHASE BRUSHLESS DC MOTOR CONTROL (Using Sprague Hall Effect Sensors) uoN28502 UONZ0802 _vOKZ9s02 604 +5Y +28V 73 75 Usnrg030T Ff ty bl nt i Ae Te ee Sc

1 DBD:

a EE 4—137

HIGH-CURRENT INTERFACE DRIVERS A UDN-2933B AND UDN-2934B 3-CHANNEL HALF-BRIDGE MOTOR DRIVERS THE UDN-2933B AND UDN-2934B inte- transient suppression, and tri-state outputs al- grated circuits are specifically designed for lowing them to be used in diverse applications. three-phase, bipolar brushless d-c motor appli- cations. Saturated drivers provide for low out- put-voltage drops at maximum rated current. RECOMMENDED MAX. OPERATING CONDITIONS The UDN-2933B is for use with TTL and $V Output Current, laure 60.0... eee e eee eee £800 mA CMOS. The UDN-2934B is intended for use _Logic Supply Voltage Range, Veo ENABLE function, independent inputs, internal UDN-2934B. o.oo eee ee eee LOW 13.5¥ 3-PHASE BRUSHLESS DC MOTOR DRIVE —rerinpits tor Electrical 1 2 3 4 § 6 Current Degrees Low High High Low High Low AB 0 Low High High = Low Low High ~CA 60 High Low High Low Low High BC 120 High Low High High Low Low -AB 180 Hign High Low High Low Low cA 240 High = High Low Low High Low —BC 300 Vee +24 a CA t | t | | 1 2 | | | | | I a | \\ca ---- i [| I T i 1 4 5 | I 1 i ! Dog. No. Ae22,518 4—138

HIGH-CURRENT INTERFACE DRIVERS el SWITCHING INDUCTIVE LOADS WITH POWER INTERFACE ICs Integrated circuits that carry both logic and leakage current, which is specified in the data bipolar power devices — whether for driving print sheet. Operating any load above the voltage that hammers, servos, steppers, relays, or brushless may produce the maximum leakage current is thus de motors — are going a long way toward con- unsafe. Even with resistive loads, the user may solidating industrial-control electronics. Though encounter occasional trouble if the load line is these power interface ICs greatly simplify the steep. Trouble occurs because the line may cross system designer's task, they must be im- the point equal to the minimum collector-emitter plemented carefully when they operate an induo- sustaining voltage. tive load. ‘The second fundamental specification, Vegi.) To do so, the engineer must fully understand is the greatest voltage that the chip can sustain how the device’s fundamental specifications relate under worst-case conditions. This limit is deter- to that inductive load, ensuring that the chip's mined by the minimum collector-emitter voltage breakdown limits are never exceeded. For exam- ple, the designer must be able to distinguish be- tween the vaguely similar but quite different 600- output-voltage specifications and know how to Vertu = 35¥ clamp transients since they cannot be prevented. The limitations and idiosyncrasies of ever-present Esco] »\\noverve ross parasitic elements also need to be well understood 5 \\ if the device is to operate flawlessly. Fe \\ The biggest roadblocks to successful circuit g aN Ver = 60 design are two frequently misunderstood speci- § 2007) RESISTIVE LOAD. H fications. The first is the power interface chip's NJ | maximum output voltage, Vcex. In most cases, ’ this parameter approximates Vapcao), the eT U minimum collector-base breakdown voltage with fo 20 0 A080 80 the emitter lead open. The actual designation SUPPLY VOLTAGE) would be Vercex: Which denotes that there is a DHS. NO, A808 standard resistance in the emitter lead. It should not be exceeded at any time, especially if the load is inductive. 1. The limits of power interface chips are more likely to The maximum collector-base breakdown value lyse afl gahoil A alin tO for a given IC is confirmed by applying a voltage collector-emitter potential may be above the supply to the device’s output to measure its maximum voltage. Thus designs must ensure the dc operating voltage stays below the device's minimum sustaining Reprinted by permission from the March 14, 1985 issue of Elec- voltage, Vesjeuy for a given quiescent load current. in tronic Design, Copyright © 1985 by Hayden Publishing Co., Inc., no case should its maximum output vottage, Very be Hasbrouck Heights, NJ. exceeded. 4139

HIGH-CURRENT INTERFACE DRIVERS et for a specified output current. It can also be is difficult to determine. Some industrial timing cir- measured with a coil dump test, in which the IC’s cuits may be both low-speed and predictable; un- output is switched off and its output voltage fortunately, random switching is the rule rather measured. Generally, the first test is done at 5% ‘than the exception. to 10% of the nominal output current for a given application. The coil test is often run at a high out- vs Ve put current and for a specified inductance. Either of these conditions will satisfactorily confirm a device’s minimum output-sustaining voltage. Switching inductive loads with interface ICs, then, demands careful attention to both the device's load line and the guaranteed output- sustaining voltage. With inductive loads, reactive voltages often greatly exceed the source voltages when the chip is switched off (Fig. 1). The source voltage is clamped off to a safe value with flyback + ac diodes that are effectively shunted across the in- (@ ® ductive load and are often internal to the device. Without such protection, or that offered by resistor- DWi6. NO. 413,007 capacitor snubbing networks, the high voltage that 2. Arranging a Zener diode network in series to clamp results from switching the coil will likely damage a power interface chip's output allows its fiyback tn or destroy the device. Unfortunately, internal pro- devin to he fumed off perad When poorly e tection alone is often insufficient, and external Feguiated supply voltages power a circult that drives : clamping circuitry must be added. muttiple devices whose voltage transients exceed the Of great concern to the designer is that insuffi- oe ’s capability, a parallel configuration is preferred cient output protection may result in gradual — and thus hard to detect — secondary breakdown. Zener diodes, on the other hand, do not suffer Particularly hardy power interface chips may seem from that limitation. The voltage rating for a series to stand up well to occasional transients in excess arrangement (Fig. 2a) is determined by: of 100 V for a load supply voltage of 12 V; that Ve = Vogisuy — Vaueexr — Ve is, until they suddenly fail. where V, is the diode’s forward voltage drop. When fast switching is a must, it is generally Thus for an IC with a sustaining voltage of 35 V, only achieved with a circuit that allows the out- a 15 V supply, and a diode drop of 2 V, the max- put voltage to rise fast and exceed the supply imum Zener value is 18 V. For designs that use voltage. For such approaches, other schemes. many power ICs for multiple loads, it is often prac- must be used. Typically, both external Zener tical to work with multiple Zener diodes with lower diodes and resistors should be employed. To- power and maximum current ratings. That avoids gether, they furnish inexpensive protection. Zener the cost of power devices and sidesteps their need diodes, however, are often used alone. for heat sinks. Zener diodes can be placed in parallel across DROPPING THE RESISTOR the output as well (Fig. 2b). In this case, the Zener The reason for this apparent omission is obvious voltage must be slightly below the minimum sus- once it is realized that the flyback voltage is not taining voltage. Automotive systems, for one, only a function of current and resistance but also typically employ internal 30 V to 35 V clamps in of the number of outputs switching off at any time. their interface chips because such operations as Only well-defined or simultaneous switching se- “jump starting’ two or three 12 V batteries quences are suitable for resistors; without either, precludes the series approach. A setup exhibiting the magnitude of the voltage transient produced an unregulated supply voltage, which varies con- 4—140

HIGH-CURRENT INTERFACE DRIVERS el siderably, may also necessitate the parallel clamp- The problem is exacerbated by the IC’s junc- ing approach. tion isolation, which produces a parasitic transistor Beyond staying within the chip's maximum across the isolation diodes (the transistor’s base voltage rating, the designer's second major con- lead is connected at their junction). Frequently, cern is avoiding problems created by inherent current injected into the device’s output is suffi- parasitic elements. In the early days of the TTL cient to create formidable substrate currents, thus device and its gold-doped low-resistivity silicon, turning all lateral transistors on. parasitic problems were virtually non-existent. As a result, the device’s leakage current may (Adding gold to improve circuit speed effectively increase, and the chip may be inadvertently ac- killed parasitic elements.) Linear bipolar ICs and tivated. In extreme cases, positive feedback a wider range of power loads make parasitic con- causes the IC to destroy itself. Circuits employ- cerns much more of an issue. The vast majority ing small low-current stepper motors are not of today's chips are junction-isolated ICs and they generally a problem, since the substrate current all demonstrate such unwanted by-products in- is seldom sufficient to turn on the transistor. In herent in their fabrication processes. high-current applications, however, putting a The most common parasites pertaining to in- discrete diode across the output device's collector- ductive loads are the vertical PNP and lateral NPN ground junction will cure the problem. transistors that are created by a device's protec- A parasitic diode exists at the input circuit to tion circuitry. The internal flyback diode of a power most power interface chips. In many instances, interface chip, for instance, becomes a low-gain it may hinder circuit operation when a negative transistor (Fig. 3). voltage is applied to the input, since substrate cur- Most circuits are not affected by this parasitic rents may be created. Connecting a discrete back- transistor, unless the switching frequency is above biased diode directly between input and ground the audio range. Curiously enough, many of the diverts current away from the substrate. Provisions problems are related to power dissipation. The should be made, though, for limiting the current parasitic transistor often draws considerable if the input state is to be pulled to voltages well power, thus raising the chip’s temperature, even below ground. when the transistor’s gain is below unity. MINIMIZING THE PROBLEM Where practical, lowering the supply voltage “ Lie niel | and decreasing the pulse repetition rate will it fe] minimize the trouble. When high switching rates py te and maximum source voltages are necessary, the WoW PVRS best technique is to place a discrete diode across Al @ A the devices’ output stage, between collector and i Pi a the supply line (or to ground if Zener clamping is used). A discrete diode, with its lower forward- voltage drop, effectively shunts the flyback diode and will conduct most of the current during DW, NO. A-19,008 clamping. Less troublesome, but still of concern, are the 3. The interface IC's flyback diode almost always lateral parasitics that may cause circuit anomalies creates a parasitic transistor (T) at the device's output. and malfunctions. In many stepper motors par- ee en eres [nuts ofthe oe the ticularly, the transformer action of the motor wind- Moreover, parasitic diodes at the inputs also are com- ings produces undesirable substrate currents In- mon. Adding external protection diodes at both the in- to the IC. In effect, a negative voltage is applied aenatone cach as false Slogan Eurhen f mey well at the device’s output, and current is injected in- prevent the device from being destroyed by the positive to its substrate. feedback currents that are occasionally generated. 4—l41

HIGH-CURRENT INTERFACE DRIVERS a TURNING IT OVER bipolar, or bridge arrangement, allows the motor . to turn either clockwise or counterclockwise. Employing power interface ICs to drive motors demands adherence to four basic design rules. HALF-BRIDGE OPERATION First, if the device is without internal protection, Alternatively, the half-bridge motor driver run diodes must be added to clamp both positive and by a pair of chips also makes possible bipolar negative overshoots caused by inductive loads. operation (Fig. 4b). Further, speed is controlled Second, if the device is protected with internal by a pulse-width-modulated waveform. Clamping clamps, external diodes could be added. That not diodes on either side of the motor take care of the only serves as insurance but eliminates the effects problems caused when the motor changes direc- of parasitic elements, which occasionally trigger tion. And with minimal modification, the driving or even destroy the chip. Third, in balanced drive circuitry accommodates ac motors as well. More arrangements, complementary input signals specifically, no clamping diode is required be- should be appropriately skewed. Doing so avoids tween pin 4 of each device and ground. The crossover currents that may cause excessive designer need only build circuitry to control the heating and reduce available output current. Final- speed of the motor; no circuitry for defining its ly, when it is unclear if the interface chip furnishes direction is required. As before, pins 2 and 5 of suitable drive to the motor — or if it is difficult to each device accept complementary driving damp the effects of parasitics at high outputs — signals. discrete bipolar transistors and appropriate clamp- Where intermediate, or discrete, bipolar tran- ing may be the solution. The transistors driven by sistors drive a de motor, it is always best to in- the chip, in turn power the motor. stall any clamping or commutating diodes close Consider a de motor circuit driven by a 1.5 A to the motor itself. Otherwise, inductive under- quad Darlington device that uses four discrete shoots or overshoots may find their way through diodes for protection and commutation (Fig. 4a). the transistors, triggering or damaging them or the The configuration, which employs a so-called power interface chip. UDN-28458 UDN-29502 UDN-29802 . wt <7 <a IN ed OO dt SPEEDO ) @ OW, Wo. 18,008 4, Following simple clamping and driving rules ensures trouble-free operation. Four diodes protect and properly commutate @ chip that drives a two-way de motor (a). Alternatively, two diodes protect a pulse-width modulated de motor circuit from damage (b). In both cases, input signals should be appropriately skewed. When transistors are used as intermediate drivers, the clamping circuitry should be placed as closely to the motor as possible, 4—142

HIGH-CURRENT INTERFACE DRIVERS AN INTEGRATED 3-PHASE BRUSHLESS DC MOTOR DRIVER Three-phase brushless de motors are especially use- sensors detect rotor position, which must be de- ful because they have no brushes to make noise, coded to drive the coils in the proper sequence. Hall dust, or wear out, The brushes of a conventional effect sensors produce low level differential analog motor have been replaced by position sensors, usu- outputs. Today’s Hall effect ICs amplify this signal ally Hall effect or optical devices. These sensors 86 make it easier to use. These Hall effect ICs pro- detect the rotor position with respect to the stator duce either large signal ac linear waveforms, or open windings. This information is used to drive the wind- collector digital signals. The UDN-2936W is com- ings in a sequence synchronized with the rotor posi- patible with both types of Hall effect IC (pull-up re- tion, called commutation. To use a three-phase sistors are needed for open collector digital Hall brushless motor usually requires custom ICs to per- effect ICs). form the commutation, and discretes for drivers. Then, to control the motor current, and with it speed — — and torque, requires pulse width modulation cir- LINEAR sx x SN] cuitry. All this adds up to many components and an SehSor QS LL expensive solution. Neurs SS 5 Now, due to progress in integrated power technol- | 4 ogy, all of the functions needed to drive three phase Hu brushless motors can be performed by one chip. The DIGITAL UDN-2936W incorporates Hall effect sensor decod- pate ing logic, power outputs capable of driving 2 A con- INPUTS iy, tinuous at 50V, PWM current limiting, direction control, dynamic braking, and integrated protection features. This device can be used to provide a sim- Abed Le ro ple, inexpensive, and reliable solution to the prob- Sie: I... a lem of driving brushless de motors. Wf Overall Chip Structure The UDN-2936W is made up of five sections, MoroR x namely the commutation logic, output drivers, cur- current ke AA RAR AAA rent limiting, direction and braking, and thermal shutdown. All logic and power functions utilize only Dwg. Mo, Aei4, 1485 bipolar processing, which allows for high power Figure 1 with an efficient use of die area. Position of the Hall effect sensors determines the Motor Commutation decoding sequence to produce the correct driving In a three-phase motor, winding current must be waveforms for each motor. The decoding sequence synchronized to rotor position to run the motor effi- programmed into this device is based on Hall effect ciently, i.e., with unidirectional torque. Hall effect cells 60 electrical degrees apart. This 60 degree se- Copyright © 1986, intertec Communications, Inc. Reprinted with permission. 4103

HIGH-CURRENT INTERFACE DRIVERS ee] quence is one of the most common used in the indus- Viee10 is the limiting threshold on Vjeqse- The default try. The truth table and timing waveforms found in limiting can be programmed by: Figure 1 illustrate how the Hall cell inputs, driving _ 25V output waveforms, and motor currents states are in- Tim = Rene terrelated. Motors with other commutation se- Default hysteresis is set at 7.5%, For a Vy; <2.5 quences can typically be accommodated by V, the limiting threshold is the following: inverting one of the position inputs. Yim = Yat Chopping Current Control 10" Raerse ‘The current limit technique chops the source driv- In this case, hysteresis is created by drawing 200 ers to control the load current level. The maximum, uA from the resistor divider when the sources are current and percentage ripple, or hysteresis, can be chopped, lowering the limiting threshold a certain programmed by the user or left to internal default percentage. The sources turn back on when the values. Source chopping produces a continuous sense voltage decays to the new lower threshold. sense voltage (see Figure 2), so this voltage is an Hysteresis is given by this expression: accurate representation of load current, even during _ 100*200 wA * R2) recirculation. Also, chopping only the sources pro- Shys = — ly duces a fast current charge-up and a slower current et * decay. This occurs because of the different voltages eo i a across the coil in both states, and results in a con- = troflable current waveform. The chopping method functions as follows: When the current reaches lim, ae the source is disabled and the current recirculates / through a sink driver and clamp diode. The motor current decays a fixed percentage, the source is en- ; ag, No, Ants abled again, and the cycle repeats. The internal Figure 3A sense voltage comparator has a limited bandwidth ten——a}tep ton} that essentially filters out noise on the sense pin to aE prevent erroneous chopping. . Dag, No. £4140

98 Figure 3B

| The hysteresis current source, V,.. voltage divider, SOURCE ha and current limiting equations can be found in Figure 4. The tables in Figure 5 aid in selecting values for SINK RiandR2. Coe croeecoonnnng Vee ay IM Vseuse Veet ° Th vi Hur H Reese o) i Ri ? inys 200pA wg, Ne, 16147 we, No, A450 Figure 2 Figure 4 The limiting current level and hysteresis are deter- The internal and external current limit settings can mined by the user or left to internal defaults. Figure be used together to start a motor with a high regu- 3 illustrates these values in a typical output current lated current, and run it at a lower regulated current. waveform. A voltage divider on the Vr pin sets the To do this, Vie must be tied above 2.5 V when the used. Whether V,,; is set internally or externally, start-up (see Figure 6). 414g

HIGH-CURRENT INTERFACE DRIVERS ey ve yg 23 iS a7 et & is o 33 55222 88s ody TUTTI sy 30023 p, é pels Hw. Xe | gee HALL DEVICE! a - : Ong, No. A488 Figure 8 The device is packaged in a 12 pin power SIP that limiting for the Vr resistor divider. Choosing Ryne has a large copper tab for excellent heat dissipation. = 0.1 ohm results in internal default limiting current The design of the tab, and the fact that it is at ground, of 2.5.A, and 7.5% ripple. This internal limiting is make the package easy to use with a heat sink. The active when QI is off. R1 and R2 form a resistor maximum allowable power dissipation in 25°C am- divider, when QI is on, to apply 1 V to the V,.rinput, bient air without a heat sink is 5.2 W. With minimal producing 1 A of regulated running current and 5% heat sinking, dissipation greater than 10 W can be ripple. Typically, QI would be off during start-up, accomplished. See Figure 7 for more information on giving 2.5 A of regulated start-up current, and then power ratings. turned on to provide 1A of running current. The Applicat values of R1, R2, and Veen. can be calculated using pplication the circuit and equations of Figure 5, or the tables of The application shown in Figure 8 is a simple one Figure 6. ‘a igure >, or the tables o! illustrating the use of the UDN-2936W in an open gure 6. ; ; loop situation with bi-level current limiting. The ___The motor speed is controlled by the current lim- motor uses digital open collector Hall cells such as iting. For a given load, speed is proportional to the Sprague UGN-3013T, so pull-up resistors are torque, and torque is proportional to motor current. required, Three 1k@ resistors pull up the Hall IC Subsequently, the motor speed can be controlled outputs to a 5V supply, the same one needed to through Vier. power the Hall effect ICs themselves. If the motor is Conclusion equipped with linear Hall effect ICs, such as the Smart power integrated circuits have come a long Sprague UGN-3503U, then there is no need for pull- way in the past few years in solving numerous motor up resistors on the inputs. These Hall effect sensors driving problems. The UDN-2936W is one example have a quiescent output voltage of 2.5 V, and emitter of how integrated monolithic devices can replace a follower outputs, The UDN-2936W has a regulated drive circuit of many components with one reliable internal. 2.5 V reference designed to make the inputs component. Also evident is the fact that bipolar tran- compatible with those linear Hall effect sensors. The sistors continue to provide economic solutions in the 5V supply is also used as a reference in the current high current application.

HIGH-CURRENT INTERFACE DRIVERS ee POWER OP AMP APPLICATIONS ‘Sprague monolithic power operational amplifiers to sense load currents without need ot the usual meet many high-current design challenges. The level-shifting or sense circuitry. Series ULN-3750 high-gain, high-current operational The operational amplifiers in this family of ICs amplifiers are used in power-driver applications such provide peak push-pull output currents as high as as servo-positioning systems (e.g., voice-coil motors +3.5A, making them suitable for applications in for disk drives), de motors, single-phase and mul- which both current sourcing and current sinking are tiphase motor-drive circuits, linear regulators, and needed. As illustrated in the examples that follow, in many other applications that, in the past, have some of the op amps allow a very high output swing. required power buffers driven by conventional They also provide overload and thermal protection operational amplifiers. under a variety of fault conditions. Attention to thermal design in IC layout has Linear motor drivers will inherently produce lower minimized temperature-induced degradation of electrical noise levels than their fast-switching digital parameters while maximizing output-power capa- counterparts. Linear position servos usually achieve bility. Single power op amp drivers are furnished in substantially higher resolution and are capable of power-tab TO-220 packages (ULN-3751Z). Dual faster response than digitally contro!led stepper units are supplied in 12-pin single in-line packages motors. Series ULN-3750 offers increased output- (ULN-3753W and ULN-3755W) and in low-cost voltage swing and high output-current drive, high standard DIPs with heat-sink tabs (Series ULN- gain as well as unity-gain stability and the capability 37508). SERIES ULN-3750 POWER OP AMPS Peak — | Short-Circuit| Thermal) Boost Functional Type |Current Output) Protection | Protect | Voltage) Compensation| Supply Span| Package ULN-37512 [Single 3.5A Yes | — Internal | 6V to 30V | 5-Pin TO-220 | Power-Tab SIP ULN-3753W 3.5A Yes Yes - External | 6V to 40V 12-Pin Power-Tab SIP ad ad DIP ULN-3755W 3.58 Yes Yes Yes Internal BV to 40V 12-Pin Power-Tab SIP DIP Some of the material appearing in this application note, is taken from an article that appeared in the August 22, 1985 issue of EDN magazine 4—147

HIGH-CURRENT INTERFACE DRIVERS Ce] BRUTE FORCE AND SMALL SIGNALS Both classical small-signal op amps and brute- schematic provide compensation with adequate force boosters must possess two attributes: they phase-gain margins to allow operation for closed- must have true differential (inverting and noninvert- loop gains as low as 1. Note the graph of the ampli- ing) inputs. Second, to minimize errors and drifts in fier's gain and phase characteristics as functions of closed-loop configurations, they must have high frequency (noninverting test circuit, Av = 1000). It open-loop gain. Frosting-on-the-cake includes low exhibits a smooth, 6 dB per octave rolloff to fre- offset voltage and drift, unity-gain stability, high out- quencies as high as 1 MHz, and an approximate 20° put swing, large common-mode input range, high phase margin at unity gain. common-mode rejection, short-circuit protection, and a thermal-shutdown feature. ade Inthe amplifier's output stage, the output transis- Sprague Series ULN-3750 offers all these fea- tors are completely protected from inductive kickback tures, and more. Consider the input section. The voltages by clamping diodes built into the chip. The circuit is a classic op amp input stage found, for clamp diodes are capable of handling currents equal example, in many operational amplifiers with little to the rated capacity of the output sink/source tran- power-handling capacity. The use of PNP input sistors. The output transistors are connected in a transistors allows the application of input voltages quasi-complementary configuration. The lower sink ranging from about 0.5 V below ground to approxi- transistor can provide output voltages as low as. mately three base-emitter drops below the positive ground plus one saturation drop. The current-sense supply voltage. The ability to use ground-level input terminals can be used to impart a transconductance: voltages is an important consideration. It allows the characteristic to the amplifier, or simply to provide a op amp to be easily operated from a single supply, separate power output ground and minimize output- where the input source is often referenced to ground. to-input feedback through a common ground The two capacitors shown in the input-circuit resistance. INPUT STAGE GAIN AND PHASE CHARACTERISTICS +Ye a T i — aT TTe, 60; << 90D ait K Ber 8 os Sis Z ye ga re Pra) PES LI P| ote a a a a a ong no. W18 FREQUENCY IN Hz wg, No, Werte 4148

HIGH-CURRENT INTERFACE DRIVERS en OUTPUT STAGE to be bootstrapped in ac applications by its own output or by another ac output. Vecosr “Ys The specifications shown below for the ULN-3755W apply to operation with +6 V sup- ® t+ > plies, at an ambient temperature of + 25°C. Not C4 OUTPUT shown are the amplifier’s absolute maximum [J ae ratings: 40 V supply span, + 3.5 A peak repetitive COMP. current, and 20W allowable package power is dissipation (with 3°C/W heat sink and +25°C INPUT. r ambient). STAGES The Series ULN-3750 currently is comprised of six types. Considering allowable package power stp dissipation ratings, continuous output currents to ~VeORGROUND SENSE +1A are recommended for the 16-pin batwing Pw No. WT DIPs (suffix “‘B”). Applications with ratings to +2.5A require the TO-220 or 12-pin single in-line power tab packages (suffix ““Z” and “W” respec- BOOST TO BOOTSTRAP tively). All 5 types provide thermal shutdown at The boost terminal is a unique feature of the high junction temperatures. All are unity-gain ULN-3755B and ULN-3755W. It increases the Stable. Pin count essentially dictates the features amplifier's available output-voltage swing by 1V available with the various units. For example, the to 2V, depending on output current, by allowing dual amplifiers lacking the boost capability the upper source transistor to saturate (an im- (ULN-3753B/W) offer compensation pins for tailor-" Possibility with the usual emitter-follower lacking ing the operational amplifiers’ frequency the boost feature). To take advantage of the boost characteristics to specific applications. The single capability, use a boost-terminal voltage that is ULN-3751Z provides neither boost nor compen- about 3V higher than the positive load supply sation options, due to the 5-pin limitation, but is voltage. The boost function allows the amplifier unity-gain stable. ULN-3755W DUAL POWER OP AMP TYPICAL ELECTRICAL CHARACTERISTICS Characteristic Typical Value Ouiescent Curent, +i Input Offset Voitage Yon = OV, No Load Input Bias Curent Input Offset Current Von = OV, No Load Slew Rate Vi = 0.2V Step 1.0 Vins Output Swing Veoost = 6 V, lu = 1A 9.5 Yop Vast = 9, lyr = 1A 10.5 ¥pp Power-Supply Rejection Either Supply 80 dB Comman-Mode Rejection [ti‘“‘CSCSC‘sSOY 8508 Ty = + 25°C, Toy S +70°C, +¥y = Voor = +6, —V, = —BV (unless otherwise specified, 4—49

HIGH-CURRENT INTERFACE DRIVERS SA CAREFUL THERMAL DESIGN WRINGS WATTS FROM ICs Power ICs are now capable of delivering tens of Limiting the junction temperature to + 150°C, the watts of power. It is easy to obtain such power from 60°C/W figure allows a worst-case (still air) package an IC when the device is mounted in a metal can with power dissipation of 1.33 W at + 70°C. Unfortunately, low thermal resistance. Moreover, it is easy to provide this power figure is still inadequate for many modern heat sinking for such a package. Metal packages, power applications. however, are expensive. The challenge is to develop inexpensive plastic packaging that also provides a way to keep junction temperatures at a safe level. HIGH-POWER SIPs What's a safe level? At the moment, the prevailing For high-power applications, power ICs use single industry standard for maximum junction temperature in-line packages similar to the TO-220, universally is + 150°C. However, using any temperature as a used for power transistors. The 5-pin ULN-3751Z reference, an |C’s expected lifetime roughly doubles uses such a package. Its maximum junction-to-tab. for every 10°C reduction in junction temperature. thermal resistance is 4.0°C/W. The ULN-3755W dual Note, too, that such circuit parameters as leakage power op amp is housed in a similar, but wider, current suffer significant degradation at high package. Exhibiting 3°C/W maximum junction-to-tab temperatures. thermal resistance, the IC can dissipate as much as. The most widely accepted IC package is the dual 26W ata tab temperature of +70°C. in-line package (DIP). Without special enhance- ments, though, the standard DIP is woefully ineffi- ISOTHERMAL DESIGN CUTS GRADIENTS cient for thermal transfer. The package itself provides Chip temperatures inevitably rise in high-power ajunction-to-ambient thermal resistance as high as. applications. Even with ideal packaging, the thermal 125°C/W. This figure assumes the use of a Kovar resistance of the silicon chip itself will result in a lead frame and, since the lead frame is the main temperature gradient across the chip. In linear cir- carrier of heat from the IC to the outside world, cuits such as these op amps, the worst effects can changing the material to copper reduces the thermal arise from unequal heating on the chip's surface. resistance to about 60°C/W. All Sprague power Itis important to position input transistors as far operational amplifiers have copper lead frames and as possible from the heat-generating output devices. heat sinks. What is less obvious is the need to arrange the high- ee <M ge 0 Dwg, No. W6? ° og Na wes | Hit U 16-PIN BATWING 'B' PACKAGE 5-PIN TO-220 2’ PACKAGE, wg No. W116 12-PIN SINGLE IN-LINE ‘W’ PACKAGE 4—150

HIGH-CURRENT INTERFACE DRIVERS SS ISOTHERMAL DESIGN | (SOOO!) =" eT | OB ae i|eeroveve~c| | a COOSS), =| z — Fea] © il = fi =a == SEE (ars) | Toll ==-= thal if CHANGES IN Vee i 2 | (Oe O i WITH TEMPERATURE = aa sa) | ll +Vs Se a= ea | ell emt \\© fy i — = ’ ©) EELS AE — Ir ~2mV =15mv IT ls th ee 7 ee. “or “fo Oc}=3 lat F sae A es (UE ca] es (lg Leer sub L | SUB, 2 5,2 can] amet =~ Qes es ~~ 4 ' a -3my —-3mV | I |i LOOM sub UB 1 | | eae Gea i I Dg No, ES gain input stages so as to minimize the effects of any base-emitter voltages. It's a different story, however, temperature differences between them. For exam- for Qe: and Qz2. They lie farther away from the power ple, unequal junction temperatures in the amplifiers section, and layout considerations have made it input transistors can cause large offset-voltage and Impossible to keep them at equal temperatures. The offset-current shifts. same problem also exists for Q2o and Qzs. For the As shown in the chip drawing and schematic, purposes of illustration, assume that a dissipation- cross-coupling of the input stages cancels differ- induced temperature rise causes the base-emitter ences in the low-level transistors’ junction temper- voltage of Qes and Qos to drop by 3mvV. Transistor atures. It is also necessary to lay out the stage's Qez is slightly cooler and suffers a Vee decrease of associated resistors to minimize temperature gra- 2mV while the comparable Qo, drop is only 1.5 mV. dients. in this case, all input-stage resistors are Finally, Qeo and Qs exhibit Vee changes of 1 mV and arranged in the same epitaxial tub (and in the same 0.5my, respectively. As a result of thermal cross- direction) to ensure that all resistors are equally coupling, the Vee reductions from either input can affected by the unavoidable heating. be matched at 2.5mV. The base-emitter voltage variations as a function of temperature thus cancel ACASE STUDY out. Without this cross-coupling, the total change in Note the isothermal lines shown in the chip draw- base-emitter voltage would be 3 mv for the ieft input ing. Qes and Qze are at equal temperatures; these stage and 2 mV for the right input stage. two current-mirror transistors must have the same 4—151

HIGH-CURRENT INTERFACE DRIVERS LE CURRENT-SENSE TRANSCONDUCTANCE The op amps’ current-sense terminals can be Ve ULN-3755W used to derive a transconductance function. This . poo PRU IER OP AMP function is commonly used in motor control appli- i {| i cations such as voice-coil servo or microstepping Vnsr© { Dan a positioning systems found in many computer disk | , drives. The drawing at right shows the ULN-3755W Vy out | “eR dual amplifier connected as a transconductance oy L i me amplifier. In this example, amplifier B is used as a mai 4 slave to amplifier A. Feedback from the pair of cur- rent-sensing resistors, Rs, in the emitters of the Re: iad < > output’s current-sinking transistors is applied to the Rs summing network and scaled to the inverting input if | of amplifier A, where it is compared to the input 7Vs OR GROUND Veer voltage. Dg. No. We The voltage developed across the sensing resis- TRANSCONDUCTANCE tors is directly proportional to the output current. AMPLIFIER Using this voltage as a feedback source defines the gain of the circuit as output current in amperes as a function of the input voltage in volts. The gain thus 14 — lp = IL. The external network sums and assumes the dimensions of a transconductance amplifies (scales) the voltages developed across the function (output current divided by input voltage), current-sensing resistors. The resulting feedback expressed in siemens (formerly mhos). voltage (Vr) is a scaled, level-shifted version of the Conventional monolithic power op amps can be load current. It is possible, in certain applications, made to operate in similar configurations where the to combine this network with the input-feedback current-sensing resistor(s) are inserted in the ground network and eliminate the small-signal operational (or negative supply) retum. However, that configu- amplifier. ration is not recommended, since both the amplifier's The negative feedback forces the amplifier to signal and bias currents now flow through the output adjust the output current to attain a value such that current sensing resistor(s), causing the high-gain the feedback voltage equals the applied input volt- signal ground to float. Operating in this mode can age. The transfer function of the transconductance cause problems with stability and common-mode amptifier is approximately: rejection, as well as reducing the input common- l(Vin - Veer) = Ra/(ReRs) mode range. The dual power op amps in the Series Resistors Ra, Re, and Rs define the transconduc- ULN-3750, however, provide open-emitter outputs tance gain. To avoid limiting the transconductance that can be used to sense current without degra- amplier’s output compliance (swing capability), low- dation of the input characteristics of the high-gain value current-sensing resistors (Rs) should be used. stages. . The product of peak output current and sensing The graphs below illustrate the bidirectional nature resistance should be kept to as low a value as of olltput load current (and the same current divided possible. between the two output sink returns). k ke b Ve omg. No. wei20 4—152

HIGH-CURRENT INTERFACE DRIVERS SE Os four FOR Vp S0.8V Vaer — u 19 12 2 6 eae 6 OA7R lave FOR Ve 20V AX 01 lour = Vaee/ Rss H D, ° De Rex 10K Vo Q, 1K} O 47K ark = = so wo. No, Wee BIDIRECTIONAL CURRENT CONTROLLER . 4 There are many applications requiring constant ing inputs. Vp represents the digital direction-control current sources that can be controlled both in mag- voltage. When Vo is low, Q2 is OFF, allowing Dz to nitude and direction. Examples of this requirement conduct, driving pin 11 high. This causes the output are found in some brushless de motor drives as well of amplifier A to be driven low. Q;, meanwhile, is ON, as in numerous industrial process control systems. clamping the anode of D, to ground (or to the sat- Both open-loop and closed-loop feedback systems uration voltage of Q;). This results in D, being held are used depending on the specific requirements to OFF and allowing active feedback to pin 2 of amplifier be met. In any case, there exists a voltage directly B, Amplifier B will then source current into the load Proportional to the desired output current and a with amplifier A acting as a current sink. By raising control signal or switch whose state determines Vp to a high level, the output of amplifier B will go direction. low, with amplifier A acting as the controlled current The circuit above is a bidirectional transconduc- source. Resistor values are non-critical except to tance amplifier. A voltage, proportional to the desired ensure that the inverting input of the switched current, is applied to both non-inverting inputs of a amplifier is held above the programming voltage ULN-3755W, which is connected in a bridge (Vaer) applied to its non-inverting input. As shown, configuration. Current feedback is obtained from control voltage-Vp is TTL compatible. current-sense resistors (Rsa and Rss). The voltage developed across the current-sense resistor is If Vp is the output of a pulse generator, this appli- directly proportional to the load current. This sense cation will produce a time-dependent current rever- voltage is applied to the inverting inputs of the sal. This meets the requirements found, for example, amplifiers, as shown, to provide negative feedback. in a typical industrial process control application The output will adjust until the feedback voltage is where a current is passed through a pair of elec- equal to the programmed input voltage. This can be trodes immersed in a conducting fluid. Alternatively, expanded to a switched selector network or the out- Q and its drive can be replaced by a latching Hall put of a servo-control loop. Effect switch, such as the Sprague UGN-3075U, for The direction of the load current is controlled by use in brushless de motor applications where current apositive bias voltage applied to either of the invert- is controlled by Rs. 4—153

HIGH-CURRENT INTERFACE DRIVERS DIGITALLY CONTROLLED POSITION SERVO In a position-control application, a microprocessor A circuit that uses far fewer components to is often used to control a servomotor's shaft angle accomplish the same position-control function is or to control position, as in a computer disk drive. constructed around the ULN-3755W integrated cir- Below is a typical discrete semiconductor circuit cuit. In addition to the original functions, the circuit implementation of that concept. The basic config- now includes thermal and short-circuit protection, as uration is a classic one, using two low-power well as component matching and thermal tracking operational amplifiers, many discrete pas- inherent to monolithic construction. The ULN-3755W sive components, and four PNP and NPN power dual power operational amplifier has its two inde- transistors connected in a push-pull, H-bridge pendent outputs connected in a push-pull, H-bridge configuration. configuration. An 8-bit D/A converter yields a res- The circuit consists of small-signal input opera- olution of 256 shaft positions in discrete steps of 1.41°. tional amplifiers and power output stages. The circuit Ahigher resolution converter would, of course, pro- derives its input from the D/A converter, whose output vide finer control. Because of its push-pull arrange- is determined by a code from the controlling micro- ment, the circuit provides bidirectional servo control. processor and related digital-control circuitry. The overall resolution of the system is a function The analog equivalent of this servo-contro! circuit of the position-sensing element, whether a digitally might use a multi-turn potentiometer to produce a encoded disk or an analog potentiometer, and the voltage proportional to the servomotor's position. In digital control circuitry, including the microprocessor any event, the sensed position signal normally and the A/D converter. The ULN-3755W dual oper- undergoes processing and comparison with the ational amplifier combines the small-signal summing desired position, through a digitally-based micro- amplifiers, predrivers, and the output H-bridge. The. processor system (or its analog equivalent) that IC's outputs also include clamping diodes with produces an error signal to control the servo ampli- current-handling capacity equal to that of the output fier’s output. drivers, DISCRETE CIRCUIT IMPLEMENTATION OVs FROM POSITION SENSE rT] ! < a’ al & F || CONTROL qu a | D A conten |] PS ; Ma i rS TT) He pT LT wg. Ne. 22 4-154

HIGH-CURRENT INTERFACE DRIVERS ee] DIGITALLY CONTROLLED POSITION SERVO — INTEGRATED CIRCUIT IMPLEMENTATION 9Vs 9 Voces Li] roncrea— p-e FROM POSITION SENSE H i t © iS o) I | JOVER-CURREN A D/A @ > i 1 i H } SUB sus | = i { * ¥ wg. No. 128 The current-sense pins (4 and 9) provide access to +2.5A and peak output currents as high as to the emitters of the H-bridge current sinks, thereby +3.5A. providing convenient output-current sensing to The user must be ai that igh the voltage ground (or to the negative rail), while allowing sep- ‘or current limits shown are well within the IC’s arate low-current signal ground returns. This feature current mis Shown are well within ine 5 pi capabilities, the resultant power dissipation must helps to prevent undesirable feedback to the input onan . , be kept within the constraints of the overall (chip + stage, a common problem with conventional , ee package + heat sink) thermal rating. This rating is approaches to output-current sense. oe . , r principally dependent on the package chosen and Ifa voltage higher than the supply is applied to the the amount of heat sinking provided by the user. ULN-3755W boost pins, the positive output swing 9p ‘A : is limited only by the saturation resistance of the The boost feature provides important additional output transistors (typically less than 0.5Q). For output voltage swing at the amplifier's full rated cur- example, with a 12V supply, the circuit typically rent. However, the IC’s boost input requires only a supplies a 10.5 Vpp output swing at 1 A output current. low, unregulated current of 25mA, maximum. This figure is atleast 1 V higher than can be expected Thanks to this modest current requirement, the boost from ICs lacking the boost capability. Note that the voltage can be obtained from such compact sources externally supplied boost voltage should be at least as inexpensive, modular dc to de converters. Or, in 3V higher than the load supply voltage. This criterion ahead-positioning application in a disk drive, for Satisfied, the boost voltage can be any value within example, a simple overwinding in the spindle motor the IC's 40 V absolute-maximum rating. The circuit (or a voltage doubler using the motor's driven shown will deliver continuous output currents of up phases) can easily generate such a voltage. 4—155

HIGH-CURRENT INTERFACE DRIVERS ee Vs o a2 $ or] 4 H TH ULN.s758W VOLTAGE-DOUBLER | > r-"-1 on BOOST SUPPLY | ' | ULN-27556

1 I MOTOR ' 1

i> i | i i \\ I ! ' c | 1 1 t 1 HEAD ty-_J I UON-28338 = UDN-29432 (3) Dg. No, Wee SIMPLE VOLTAGE DOUBLERS FOR OP AMP BOOST An example of a simple-to-implement voltage- motor phase is needed to generate the boost, the doubler boost supply is shown above. This circuit three-phase connection is recommended to prevent affects the doubling by connecting a series diode- unbalancing the spindle. capacitor network between the main supply and each of the spindle motor’s driven phases. A three- Below is a similar circuit using a ULN-3755W to diode bridge then charges the voltage-doubling provide linear drive to a delta-connected spindle capacitor to nearly twice the main supply voltage. motor. The use of linear drive instead of pulse-width- Note that connecting the capacitor to the main supply modulation results in much lower noise with only a. (instead of to ground) effectively reduces rms ripple slight reduction in efficiency. Because fast PWM in the main supply by injecting its charge current into transitions in the circuit above resuit in motor losses, the supply mains concurrently with the spindle’s the efficiency compromise of the linear configuration opposing drive currents. Although, in theory, only one is not as significant as might be expected. Vs Zz ¢ | be [Pr] Veoosr TAO ae uins7ssw — VOLTAGE-DOUBLER 1 nocd BOOST SUPPLY | > { Sovon: H | VLNSTSS8 WITH LINEAR DRIVE i i c ' ' 1 i t i | > { |

1 T | 1

[inerssw ' £ on 1 HEAD ULN-97558 “4 MOTOR - wget 4—156

HIGH-CURRENT INTERFACE DRIVERS a ‘OUTPUT SELECT

009000000 Ovs

ve Vour= Wu (1+2) J 1 5 POSITIVE-OUTPUT D/A CONVERTER v, PROGRAMMABLE REGULATOR 1K 001 4 four we O 2 + i) 7 | 10 uF O-Vs ¥. = = Dg. No, Wa HIGH-CURRENT REGULATORS The high current-output capability of the opera- providing programmability. An 8-bit D/A, for example, tional amplifiers in Series ULN-3750 makes them provides for 256 steps of output resolution. suitable for use in linear voltage regulators. The For higher output currents (but without the sink amplifiers’ high open-loop gain and low offset voltage capability) the addition of an external power transistor ensure high load regulation and accuracy. Consider, (below) provides outputs as high as the NPN power for example, the positive-output, programmable transistor’s safe operating area allows. This circuit regulator above. The circuit provides output currents is shown using a voltage reference such as the pop- as high as +3.5A peak. Unlike most monolithic ular three-terminal TL431. The voltage Vz is deter- regulators, the ULN-3751Z is equally effective as a mined by the ratio of resistors Rs and Ra, while Rs sink or a source. Therefore, the circuit maintains provides bias current. The circuit can, of course, be regulation for active loads that present reversing load programmed by substituting the D/A reference currents. Note that the circuit easily handles tran- above. The ampiifier's output voltage is a function sitions from high to low output voltages, thanks to of the ratios of R; and Re. The PNP transistor pro- the crowbar effect of the outputs sinking capability. vides short-circuit (Isc) current limiting according to The input reference is the output of a D/A converter, the expression shown. Vs O Vee Poo= SX) POSITIVE OUTPUT REGULATOR CD WITH SHORT-CIRCUIT LIMITING v L | - 2N6486 * un ) - 37558 i Ped ate poet 4 5K TAB, el eo Vs = Re R, Re 4—157

HIGH-CURRENT INTERFACE DRIVERS ee] Re STe) fh 10 I ” a 6 A) 2N6491 B24 vere eval HIGH-CURRENT ot nl) NEGATIVE OUTPUT ns REGULATOR ia ™ ve wg. No. W128 HIGH-CURRENT REGULATORS (Continued) To configure a high-current, dual-output supply, the amplifier's output provides local compensation the mirror-image circuit shown at top can be used. for the output stage. ‘Simply connect this stage's input to the D/A converter Asimple split supply can also be developed using or voltage reference output. The combination of this a single ULN-3751Z power op amp to generate an circuit and the positive output regulator on the pre- artificial ground, as shown below. By taking advan- vious page provides an accurately tracking pair of tage of the device's four-quadrant sink/source drive positive and negative supplies from a common ref- capability, the outputs will ratio (rather than track) erence, whether a programmable D/A converter or over a wide range of supply voltages and unequal the simple resistor-programmed TL431. Both circuits load currents. Tota/ load current is unrestricted, use the ULN-3755B with external high-current pass provided the difference in load currents is less than transistors. The external devices are unnecessary the maxirhum rated current of the power op amp. In if output-current loading is less than 2.5A. addition, the allowable package power dissipation The previously described boost capability can be rating must be greater than the product of the used to good advantage in these regulator circuits. amplifier’s sourcing current (Ia < Is) and the source Applying a low-current boost voltage at least 3V driver voltage (Va) or the sinking current (Ia > ls) and higher than the load supply voltage results in a reg- the sink driver voltage (Vg). This circuit is also very ulator with less than 1V input-output differential, useful in tracking supplies to enhance common- (dependent on output current) yielding high efficiency mode supply rejection. from the main supply. The 0.1 9/0.1 .F network at Oy,=+ Save | Ye RR Ra Vs 4 8 ARTIFICIAL GROUND / — aa SPLIT SUPPLY a oF Re i wg, No. W128 4158

HIGH-CURRENT INTERFACE DRIVERS ay DC MOTOR SPEED CONTROL ev wv z 7 10k te 4 10, 12 ( 1 = 2 4 1 a. 1 PS a4 -8V 1 4 1 5 tT ii. laa }-ev = / = 0-6 oe / 10K Onur r, x @) L MOTOR IS GLOBE 1004565 (12 VDC) T i wg. No. W120 ICs CONTROL MOTOR SPEED | 4| Power op amps can be used to provide accurate The motor speed, in rpm, is: speed control for de motors. The drawing above S = Vser(Ri + Re)/0.0027 Re shows a closed-loop system for controlling the speed of a 12 V de motor. The circuit provides bidirectional The RC feedback network prevents oscillation speed control. The amplifiers’ push-pull configu- by compensating for the inherent dynamic mechan- ration ensures a full rail-to-rail voltage swing (minus. ical lag of the motor. Select the ReCr time constant ‘the output stages’ saturation drops) across the motor to match the particular motor's characteristics. By in either direction. consulting with individual motor data sheets, the Rr The circuit uses a mechanically-coupled ta- and Cr values can be chosen to match the motor chometer to provide speed-stabilizing feedback to response or dynamic time constant. This should yield the first amplifier section. The motor’s speed and a good starting point for stabilizing the system. direction of rotation is set by adjusting the 10k. Optimal response is achieved by varying the com- potentiometer at the amplifier’s noninverting input. pensating capacitor. 4—159

HIGH-CURRENT INTERFACE DRIVERS A 50 50, SINGLE-PHASE AC MOTOR DRIVER Our, 9 1 + Vs 82K oyFL = 0.33 pF ane, Ry T ~ Cy T Re == ug, No, Wt N-PHASE MOTOR DRIVE Its high amplification factor and its built-in power- op amp is configured as a Wein-bridge power oscil- output stage make the integrated power operational lator. The RC, and ReC2 feedback networks deter- amplifier a convenient driver for single-phase or mine the oscillation frequency according to the multiphase ac motors. The high gain allows one op expression: amp to be configured as an oscillator to generate fo = 1/(2nVRiReCiC2) the required ac signal. The power-output stage, of By varying either Ry or Re, the oscillator frequency course, supplies the high-current drive to the motor. can be adjusted over a narrow range. Consider, for example, the three motor-drive cir- In the single-phase and two-phase examples, the cuits shown here. The circuit above is a single-phase oscillation frequency is 60 Hz. In the three-phase driver that uses the ULN-3751Z single power op example, the frequency is 400 Hz. The Type 47 amp. The other circuits use the ULN-3755W dual incandescent light bulb in the oscillator circuits serve amplifier to drive two-phase and three-phase to stabilize the amplifiers output amplitude. The bulb: motors. Note that in all three circuits, the controlling owes its stabilization qualities to its intrinsic positive TWO-PHASE AC MOTOR DRIVER 50 50 25K Ry t <0 0° S Be Ow ae ; Ste bd os ’ + Ou our oek omeax T | 0238 pF: ae Thea = 4 4 oe Re 82k ~ = 033uF wg. No, W192 4—160

. HIGH-CURRENT INTERFACE DRIVERS Ce THREE-PHASE AC MOTOR DRIVER 50 50, 615K Ry

9 OVs

yw | Re [3] o=0 o=r20| 1d Me @)sa7 Weel Tr +2 Cc b-Vs 1 a: I 008 uF og, 0.02uF Ve 82K - Our 00s uF aaq BRK One T Cp T Re + = “ = 82K 0.022 uF wg. No, We temperature coefficient. If the amplifier's output level 120° of phase shift. The motor shown is a three- attempts to increase, the corresponding increase in phase delta-connected motor with one input lamp current causes a temperature rise in the fila- grounded and the remaining inputs driven from the ment. The heating, in turn, results in an increase in 0° and 120° phase-shifted amplifier outputs. The filament resistance, producing increased negative result is a balanced three-phase a-c drive. feedback and a reduction in amplifier gain. A PTC In both the two-phase and three-phase circuits, (positive temperature coefficient) resistor could be the Re/R, ratio sets the second amplifiers gain to used instead of the lamp. To set the output amplitude, compensate for signal attenuation occurring in the adjust the 50 potentiometer in the feedback phase shifters. Again, pins 3 and 10 can be returned network. to a boost supply to obtain additional output-swing Tb drive multiphase motors, its a relatively simple capability. matter to add another stage to the single-phase cir- The three circuits can all be driven from an external cuit. In the 60 Hz, two-phase drive, the 8.2k0/0.33 nF source, such as a pulse or square wave output of a networks provide both the 60 Hz oscillator frequency digital source, setting the gain of the left-hand and the 90° phase shift needed by the right-hand amplifier to a level less than that required for oscil- amplifier. The 8.2k/0.005 wF networks in the three- lation. The RC feedback networks then function as phase drive set the 400 Hz oscillator frequency, while active filters, causing the outputs to be sinusoidal the 8.2k0/0.022 .F networks provide the required UNIVERSAL BUILDING BLOCKS Power operational amplifiers provide a funda- voltage swing, while an output-current-sensing mental set of universal building blocks incorporating scheme prevents unwanted interaction between the the merged equivalent of small-signal operational outputs and inputs. Many applications that previously amplifiers, pre-drivers, output amplifiers and various required individual low-level and high-level com- protective features such as output clamp diodes, ponents can now be implemented with a single inte- thermal shutdown, and output-current limiting. An grated circuit and few external components. output-boost capability can provide for high output- 4—l61