LTBPB

LT1996 LINER

Document overview

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Technical content

RESISTOR MATCHING (%) PERCENTAGE OF UNITS (%) 0.04

1996 TA01b

–0.02 0 0.02 –0.04 LT1996A G = 81 TYPICAL APPLICATIO U

FEATURES

■ Pin Configurable as a Difference Amplifier, Inverting and Noninverting Amplifier ■ Difference Amplifier Gain Range 9 to 117 CMRR >80dB ■ Noninverting Amplifier Gain Range 0.008 to 118 ■ Inverting Amplifier Gain Range –0.08 to –117 ■ Gain Error: <0.05% ■ Gain Drift: < 3ppm/°C ■ Wide Supply Range: Single 2.7V to Split ±18V ■ Micropower Operation: 100µA Supply ■ Input Offset Voltage: 50µV (Max) ■ Gain Bandwidth Product: 560kHz ■ Rail-to-Rail Output ■ Space Saving 10-Lead MSOP and DFN Packages Precision, 100µA Gain Selectable Amplifier The LT 1996 combines a precision operational amplifier with eight precision resistors to form a one-chip solution for accurately amplifying voltages. Gains from –117 to 118 with a gain accuracy of 0.05% can be achieved without any external components. The device is particularly well suited for use as a difference amplifier, where the excellent resistor matching results in a common mode rejection ratio of greater than 80dB. The amplifier features a 50 µV maximum input offset voltage and a gain bandwidth product of 560kHz. The device operates from any supply voltage from 2.7V to 36V and draws only 100µA supply current on a 5V supply. The output swings to within 40mV of either supply rail. The internal resistors have excellent matching character- istics; variation is 0.05% over temperature with a guaran- teed matching temperature coefficent of less than 3ppm/°C. The resistors are also extremely stable over voltage, exhibiting a nonlinearity of less than 10ppm. The LT1996 is fully specified at 5V and ±15V supplies and from –40 °C to 85 °C. The device is available in space saving 10-lead MSOP and DFN packages. For an amplifier with selectable gains from –13 to 14, see the LT1991 data sheet. DESCRIPTIO U APPLICATIO SU Rail-to-Rail Gain = 9 Difference Amplifier Distribution of Resistor Matching 15V –15V ∆VIN VM(IN) VP(IN) VOUT = VREF + 9 • ∆VIN SWING 40mV TO EITHER RAIL INPUT RANGE ±60V RIN = 100kΩ LT1996

1996 TA01

, LTC and LT are registered trademarks of Linear Technology Corporation. All other trademarks are the property of their respective owners. Patents Pending. ■ Handheld Instrumentation ■ Medical Instrumentation ■ Strain Gauge Amplifiers ■ Differential to Single-Ended Conversion

SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS ∆G Gain Error V S = ±15V, VOUT = ±10V; RL = 10k G = 81; LT1996AMS ● ±0.02 ±0.05 % G = 27; LT1996AMS ● ±0.03 ±0.06 % G = 9; LT1996AMS ● ±0.03 ±0.07 % G = 81; LT1996ADD ● ±0.02 ±0.05 % G = 27; LT1996ADD ● ±0.02 ±0.07 % G = 9; LT1996ADD ● ±0.03 ±0.08 % GNL Gain Nonlinearity V S = ±15V; VOUT = ±10V; RL = 10k; G = 9 ● 1 10 ppm ∆G/∆T Gain Drift vs Temperature (Note 6) V S = ±15V; VOUT = ±10V; RL = 10k ● 0.3 3 ppm/ °C CMRR Common Mode Rejection Ratio, V S = ±15V; G = 9; VCM = ±15.3V Referred to Inputs (RTI) LT1996AMS ● 80 100 dB LT1996ADD ● 80 100 dB LT1996 ● 70 100 dB VS = ±15V; G = 27; VCM = –14.5V to 14.3V LT1996AMS ● 95 105 dB LT1996ADD ● 90 105 dB LT1996 ● 75 105 dB PACKAGE/ORDER I FOR ATIOUU W Input Current Operating Temperature Range (Note 4) ...–40°C to 85°C Specified Temperature Range (Note 5) ....–40°C to 85°C ORDER PART NUMBER MS PART MARKING*TJMAX = 150°C, θJA = 230°C/W LTBPB LT1996CMS LT1996IMS LT1996ACMS LT1996AIMS ABSOLUTE AXI U RATI GSW WW U (Note 1) The ● denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25°C. Difference amplifier configuration, VS = 5V, 0V or ±15V; VCM = VREF = half supply, unless otherwise noted. *Temperature and electrical grades are identified by a label on the shipping container. Consult LTC Marketing for parts specified with wider operating temperature ranges. P27 P81 V EE REF M27 M81 V CC OUT TOP VIEW MS PACKAGE 10-LEAD PLASTIC MSOP Maximum Junction Temperature Storage Temperature Range ORDER PART NUMBER DD PART MARKING* TJMAX = 125°C, θJA = 160°C/W UNDERSIDE METAL CONNECTED TO VEE (PCB CONNECTION OPTIONAL) LBPC LT1996CDD LT1996IDD LT1996ACDD LT1996AIDD TOP VIEW DD PACKAGE 10-LEAD (3mm × 3mm) PLASTIC DFN 1 M9 M27 M81 V CC OUT P27 P81 V EE REF

ELECTRICAL CHARACTERISTICS

SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS CMRR Common Mode Rejection Ratio (RTI) V S = ±15V; G = 81; VCM = –14.1V to 13.9V LT1996AMS ● 105 120 dB LT1996ADD ● 100 120 dB LT1996 ● 85 120 dB VCM Input Voltage Range (Note 7) P9/M9 Inputs VS = ±15V; VREF = 0V ● –15.5 15.3 V VS = 5V, 0V; VREF = 2.5V ● 0.84 3.94 V VS = 3V, 0V; VREF = 1.25V ● 0.98 1.86 V P9/M9 Inputs, P81/M81 Connected to REF VS = ±15V; VREF = 0V ● –60 60 V VS = 5V, 0V; VREF = 2.5V ● –12.6 15.6 V VS = 3V, 0V; VREF = 1.25V ● –1.25 6.8 V P27/M27 Inputs V S = ±15V; VREF = 0V ● –14.5 14.3 V VS = 5V, 0V; VREF = 2.5V ● 0.95 3.84 V VS = 3V, 0V; VREF = 1.25V ● 1 1.82 V P81/M81 Inputs VS = ±15V; VREF = 0V ● –14.1 13.9 V VS = 5V, 0V; VREF = 2.5V ● 0.99 3.81 V VS = 3V, 0V; VREF = 1.25V ● 1 1.8 V VOS Op Amp Offset Voltage (Note 8) LT1996AMS, V S = 5V, 0V 15 50 µV

• 135 µV LT1996AMS, VS = ±15V 15 80 µV
• 160 µV LT1996MS 25 100 µV
• 200 µV LT1996DD 25 150 µV
• 250 µV ∆VOS/∆T Op Amp Offset Voltage Drift (Note 6) ● 0.3 1 µV/°C IB Op Amp Input Bias Current 2.5 5 nA
• 7.5 nA IOS Op Amp Input Offset Current LT1996A 50 500 pA
• 750 pA LT1996 50 1000 pA
• 1500 pA Op Amp Input Noise Voltage 0.01Hz to 1Hz 0.35 µVP-P 0.01Hz to 1Hz 0.07 µVRMS 0.1Hz to 10Hz 0.25 µVP-P 0.1Hz to 10Hz 0.05 µVRMS en Input Noise Voltage Density G = 9; f = 1kHz 46 nV/ √Hz (Includes Resistor Noise) G = 117; f = 1kHz 18 nV/ √Hz RIN Input Impedance (Note 10) P9 (M9 = Ground) ● 350 500 650 k Ω P27 (M27 = Ground) ● 326.9 467 607.1 k Ω P81 (M81 = Ground) ● 319.2 456 592.8 k Ω M9 (P9 = Ground) ● 35 50 65 k Ω M27 (P27 = Ground) ● 11.69 16.7 21.71 k Ω M81 (P81 = Ground) ● 3.85 5.5 7.15 k Ω The ● denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25°C. Difference amplifier configuration, VS = 5V, 0V or ±15V; VCM = VREF = half supply, unless otherwise noted.

SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS ∆R Resistor Matching (Note 9) G = 81; LT1996AMS ● ±0.02 ±0.05 % G = 27; LT1996AMS ● ±0.03 ±0.06 % G = 9; LT1996AMS ● ±0.03 ±0.07 % G = 81; LT1996ADD ● ±0.02 ±0.05 % G = 27; LT1996ADD ● ±0.02 ±0.07 % G = 9; LT1996ADD ● ±0.03 ±0.08 % ∆R/∆T Resistor Temperature Coefficient (Note 6) Resistor Matching ● 0.3 3 ppm/ °C Absolute Value ● –30 ppm/ °C PSRR Power Supply Rejection Ratio V S = ±1.35V to ±18V (Note 8) ● 105 135 dB Minimum Supply Voltage ● 2.4 2.7 V VOUT Output Voltage Swing (to Either Rail) No Load VS = 5V, 0V 40 55 mV VS = 5V, 0V ● 65 mV VS = ±15V ● 110 mV 1mA Load VS = 5V, 0V 150 225 mV VS = 5V, 0V ● 275 mV VS = ±15V ● 300 mV ISC Output Short-Circuit Current (Sourcing) Drive Output Positive; 8 12 mA Short Output to Ground ● 4m A Output Short-Circuit Current (Sinking) Drive Output Negative; 8 21 mA Short Output to VS or Midsupply ● 4m A BW –3dB Bandwidth G = 9 38 kHz G = 27 17 kHz G = 81 7 kHz GBWP Op Amp Gain Bandwidth Product f = 10kHz 560 kHz tr, tf Rise Time, Fall Time G = 9; 0.1V Step; 10% to 90% 8 µs G = 81; 0.1V Step; 10% to 90% 40 µs tS Settling Time to 0.01% G = 9; V S = 5V, 0V; 2V Step 85 µs G = 9; VS = 5V, 0V; –2V Step 85 µs G = 9; VS = ±15V; 10V Step 110 µs G = 9; VS = ±15V; –10V Step 110 µs SR Slew Rate V S = 5V, 0V; VOUT = 1V to 4V ● 0.06 0.12 V/ µs VS = ±15V; VOUT = ±10V ● 0.08 0.12 V/ µs IS Supply Current V S = 5V, 0V 100 110 µA

• 150 µA VS = ±15V 130 160 µA
• 210 µA Note 1: Absolute Maximum Ratings are those beyond which the life of the device may be impaired. Note 2: The P27/M27 and P81/M81 inputs are protected by ESD diodes to the supply rails. If one of these four inputs goes outside the rails, the input current should be limited to less than 10mA. The P9/M9 inputs can withstand ±60V if P81/M81 are grounded and VS = ±15V (see Applications Information section about “High Voltage CM Difference Amplifiers”). Note 3: A heat sink may be required to keep the junction temperature below absolute maximum ratings. The ● denotes the specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25°C. Difference amplifier configuration, VS = 5V, 0V or ±15V; VCM = VREF = half supply, unless otherwise noted.

Supply Current vs Supply Voltage Output Voltage Swing vs Temperature Output Voltage Swing vs Load Current (Output Low) Output Voltage Swing vs Load Current (Output High) Output Short-Circuit Current vs Temperature Input Offset Voltage vs Difference Gain TYPICAL PERFOR A CE CHARACTERISTICSUW (Difference Amplifier Configuration) Note 4: Both the LT1996C and LT1996I are guaranteed functional over the –40°C to 85°C temperature range. Note 5: The LT1996C is guaranteed to meet the specified performance from 0°C to 70°C and is designed, characterized and expected to meet specified performance from –40°C to 85°C but is not tested or QA sampled at these temperatures. The LT1996I is guaranteed to meet specified performance from –40°C to 85°C. Note 6: This parameter is not 100% tested. Note 7: Input voltage range is guaranteed by the CMRR test at VS = ±15V. For the other voltages, this parameter is guaranteed by design and through correlation with the ±15V test. See the Applications Information section to determine the valid input voltage range under various operating conditions. Note 8: Offset voltage, offset voltage drift and PSRR are defined as referred to the internal op amp. You can calculate output offset as follows. In the case of balanced source resistance, V OS, OUT = VOS • Noise Gain + IOS • 450k + IB • 450k • (1 – RP/RN) where RP and RN are the total resistance at the op amp positive and negative terminal respectively. Note 9: Resistors connected to the minus inputs. Resistor matching is not tested directly, but is guaranteed by the gain error test. Note 10: Input impedance is tested by a combination of direct measurements and correlation to the CMRR and gain error tests. SUPPLY VOLTAGE (±V) SUPPLY CURRENT (µA) 200 175 150 125 100

1996 G01

TA = 85°C TA = –40°C TA = 25°C LOAD CURRENT (mA) OUTPUT VOLTAGE (mV) 1400 1200 1000 800 600 400 200 V EE

1996 G03

VS = 5V, 0V TA = 85°C TA = –40°C TA = 25°C LOAD CURRENT (mA) VCC –100 –200 –300 –400 –500 –600 –700 –800 –900 –1000 OUTPUT VOLTAGE SWING (mV)

1996 G04

VS = 5V, 0V TA = 85°C TA = –40°C TA = 25°C TEMPERATURE (°C) –50 OUTPUT SHORT-CIRCUIT CURRENT (mA) 0 50 75

1996 G05

–25 25 100 125 VS = 5V, 0V SINKING SOURCING GAIN (V/V) INPUT OFFSET VOLTAGE (µV) 150 100 –50 –100 –150 10881 90 99 11745

1996 G06

VS = 5V, 0V REPRESENTATIVE PARTS TEMPERATURE (°C) –50 OUTPUT VOLTAGE SWING (mV) 100

1996 G02

V EE –25 25 75 125 VS = 5V, 0V NO LOAD OUTPUT HIGH (RIGHT AXIS) OUTPUT LOW (LEFT AXIS) V CC –20 –40 –60

TYPICAL PERFOR A CE CHARACTERISTICSUW (Difference Amplifier Configuration) Output Impedance vs Frequency CMRR vs Temperature Gain Error vs Temperature Bandwidth vs Gain CMRR vs Frequency PSRR vs Frequency Output Offset Voltage vs Difference Gain Gain Error vs Load Current Slew Rate vs Temperature GAIN (V/V) OUTPUT OFFSET VOLTAGE (mV) 10.0 7.5 5.0 2.5 –2.5 –5.0 –7.5 –10.0 10881 90 99 11745

1996 G07

VS = 5V, 0V REPRESENTATIVE PARTS LOAD CURRENT (mA) GAIN ERROR (%) 3 5

1996 G08

0.04 0.03 0.02 0.01 –0.01 –0.02 –0.03 –0.04 GAIN = 81 VS = ±15V VOUT = ±10V TA = 25°C REPRESENTATIVE UNITS TEMPERATURE (°C) –50 SLEW RATE (V/µs) 0.30 0.25 0.20 0.15 0.10 0.05 25 75

1996 G09

–25 0 50 100 125 GAIN = 9 VS = ±15V VOUT = ±10V SR– (FALLING EDGE) SR+ (RISING EDGE) GAIN (V/V) –3dB BANDWIDTH (kHz) 27 45 63 81

1996 G10

VS = 5V, 0V TA = 25°C FREQUENCY (Hz) CMRR (dB) 130 120 110 100 10 1k 10k 1M

1996 G11

VS = 5V, 0V TA = 25°C GAIN = 9 GAIN = 27 GAIN = 81 PSRR (dB) 120 110 100 VS = 5V, 0V TA = 25°C GAIN = 9 GAIN = 27 FREQUENCY (Hz) 10 1k 10k

1996 G12

GAIN = 81 FREQUENCY (Hz) OUTPUT IMPEDANCE (Ω) 1 100 1k 100k 10k

1996 G13

0.1 0.01 VS = 5V, 0V TA = 25°C GAIN = 9 GAIN = 27 GAIN = 81 TEMPERATURE (°C) –50 CMRR (dB) 120 100 25 75

1996 G14

–25 0 50 100 125 GAIN = 9 VS = ±15V REPRESENTATIVE UNITS TEMPERATURE (°C) –50 GAIN ERROR (%) 0.030 0.025 0.020 0.015 0.010 0.005 25 75

1996 G15

–25 0 50 100 125 GAIN = 9 VS = ±15V REPRESENTATIVE UNITS

P9 (Pin 1): Noninverting Gain-of-9 input. Connects a 50k internal resistor to the op amp’s noninverting input. P27 (Pin 2): Noninverting Gain-of-27 input. Connects a (50k/3) internal resistor to the op amp’s noninverting input. P81 (Pin 3): Noninverting Gain-of-81 input. Connects a (50k/9) internal resistor to the op amp’s noninverting input. VEE (Pin 4): Negative Power Supply. Can be either ground (in single supply applications), or a negative voltage (in split supply applications). REF (Pin 5): Reference Input. Sets the output level when difference between inputs is zero. Connects a 450k internal resistor to the op amp’s noninverting input. OUT (Pin 6): Output. V OUT = VREF + 9 • (VP1 – VM1) + 27 • (VP3 – VM3) + 81 • (VP9 – VM9). VCC (Pin 7): Positive Power Supply. Can be anything from 2.7V to 36V above the VEE voltage. M81 (Pin 8): Inverting Gain-of-81 input. Connects a (50k/9) internal resistor to the op amp’s inverting input. M27 (Pin 9): Inverting Gain-of-27 input. Connects a (50k/3) internal resistor to the op amp’s inverting input. M9 (Pin 10): Inverting Gain-of-9 input. Connects a 50k internal resistor to the op amp’s inverting input. (Difference Amplifier Configuration) Gain and Phase vs FrequencyGain vs Frequency Small Signal Transient Response, Gain = 9 Small Signal Transient Response, Gain = 27 0.01Hz to 1Hz Voltage Noise TYPICAL PERFOR A CE CHARACTERISTICSUW (Difference Amplifier Configuration) FREQUENCY (kHz) GAIN (dB)

1996 G16

VS = 5V, 0V TA = 25°C 0.5 10 100 5001 GAIN = 9 GAIN = 27 GAIN = 81 FREQUENCY (kHz) GAIN (dB) PHASE (deg) 10 100 400

1996 G17

0.1 VS = 5V, 0V TA = 25°C GAIN = 9 PHASE (RIGHT AXIS)GAIN (LEFT AXIS) –20 –40 –60 –80 –100 –120 –140 –160 –180 –200 –10 VS = ±15V TA = 25°C MEASURED IN G =117 REFERRED TO OP AMP INPUTS 0 1 02 03 04 05 06 07 08 09 0 1 0 0 TIME (s) OP AMP VOLTAGE NOISE (100nV/DIV)

1996 G21

10µs/DIV

1996 G18

20µs/DIV

1996 G19

50µs/DIV

1996 G20

Small Signal Transient Response, Gain = 81

The LT1996 may be the last op amp you ever have to stock. Because it provides you with several precision matched resistors, you can easily configure it into several different classical gain circuits without adding external compo- nents. The several pages of simple circuits in this data sheet demonstrate just how easy the LT1996 is to use. It can be configured into difference amplifiers, as well as into inverting and noninverting single ended amplifiers. The fact that the resistors and op amp are provided together in such a small package will often save you board space and reduce complexity for easy probing. The Op Amp The op amp internal to the LT1996 is a precision device with 15µV typical offset voltage and 3nA input bias cur- rent. The input offset current is extremely low, so match- ing the source resistance seen by the op amp inputs will provide for the best output accuracy. The op amp inputs are not rail-to-rail, but extend to within 1.2V of V CC and 1V of VEE. For many configurations though, the chip inputs will function rail-to-rail because of effective attenuation to the +input. The output is truly rail-to-rail, getting to within 40mV of the supply rails. The gain bandwidth product of the op amp is about 560kHz. In noise gains of 2 or more, it is stable into capacitive loads up to 500pF. In noise gains below 2, it is stable into capacitive loads up to 100pF. The Resistors The resistors internal to the LT1996 are very well matched SiChrome based elements protected with barrier metal. Although their absolute tolerance is fairly poor ( ±30%), their matching is to within 0.05%. This allows the chip to achieve a CMRR of 80dB, and gain errors within 0.05%. The resistor values are (450k/9), (450k/27), (450k/81) and 450k, connected to each of the inputs. The resistors have power limitations of 1watt for the 450k and (450k/81) resistors, 0.3watt for the (450k/27) resistors and 0.5watt for the (450k/9) resistors; however, in practice, power dissipation will be limited well below these values by the BLOCK DIAGRA W LT1996 1996 BD 9 8 2 3 4 5 7 610 M9 M27 M81 P9 P27 P81 VCC VEE OUT REF 450k/81 450k/27 450k/27 450k/9 450k/9 450k 4pF 450k 450k/81 4pF OUT APPLICATIO S I FOR ATIOWU UU

maximum voltage allowed on the input and REF pins. The 50k resistors connected to the M9 and P9 inputs are isolated from the substrate, and can therefore be taken beyond the supply voltages. The naming of the pins “P9,” “P27,” “P81,” etc., is based on their admittances relative to the feedback and REF admittances. Because it has 9 times the admittance, the voltage applied to the P9 input has 9 times the effect of the voltage applied to the REF input. Bandwidth The bandwidth of the LT1996 will depend on the gain you select (or more accurately the noise gain resulting from the gain you select). In the lowest configurable gain of 1, the –3dB bandwidth is limited to 450kHz, with peaking of about 2dB at 280kHz. In the highest configurable gains, bandwidth is limited to 5kHz. Input Noise The LT1996 input noise is comprised of the Johnson noise of the internal resistors ( √4kTR), and the input voltage noise of the op amp. Paralleling all four resistors to the +input gives a 3.8kΩ resistance, for 8nV/√Hz of voltage noise. The equivalent network on the –input gives another 8nV/√Hz, and the op amp 14nV/ √Hz. Taking their RMS sum gives a total 18nV/ √Hz input referred noise floor. Output noise depends on configuration and noise gain. Input Resistance The LT1996 input resistances vary with configuration, but once configured are apparent on inspection. Note that resistors connected to the op amp’s –input are looking into a virtual ground, so they simply parallel. Any feedback resistance around the op amp does not contribute to input resistance. Resistors connected to the op amp’s +input are looking into a high impedance, so they add as parallel or series depending on how they are connected, and whether or not some of them are grounded. The op amp +input itself presents a very high G Ω impedance. In the classical noninverting op amp configuration, the LT1996 presents the high input impedance of the op amp, as is usual for the noninverting case. Common Mode Input Voltage Range The LT1996 valid common mode input range is limited by three factors: 1. Maximum allowed voltage on the pins 2. The input voltage range of the internal op amp 3. Valid output voltage The maximum voltage allowed on the P27, M27, P81 and M81 inputs includes the positive and negative supply plus a diode drop. These pins should not be driven more than a diode drop outside of the supply rails. This is because they are connected through diodes to internal manufactur- ing post-package trim circuitry, and through a substrate diode to V EE. If more than 10mA is allowed to flow through these pins, there is a risk that the LT1996 will be detrimmed or damaged. The P9 and M9 inputs do not have clamp diodes or substrate diodes or trim circuitry and can be taken well outside the supply rails. The maximum allowed voltage on the P9 and M9 pins is ±60V. The input voltage range of the internal op amp extends to within 1.2V of V CC and 1V of VEE. The voltage at which the op amp inputs common mode is determined by the voltage at the op amp’s +input, and this is determined by the voltages on pins P9, P27, P81 and REF. (See “Calcu- lating Input Voltage Range” section.) This is true provided that the op amp is functioning and feedback is maintaining the inputs at the same voltage, which brings us to the third requirement. For valid circuit function, the op amp output must not be clipped. The output will clip if the input signals are attempt- ing to force it to within 40mV of its supply voltages. This usually happens due to too large a signal level, but it can also occur with zero input differential and must therefore be included as an example of a common mode problem. APPLICATIO S I FOR ATIOWU UU

Figure 3. Calculating Additional Voltage Range of Figure 1. Difference Amplifier Cannot Produce 0V on a Single dictated by how the P inputs and REF pin are connected. Figure 2. Calculating CM Input Voltage Range

1996 F01

1996 F02

1996 F03

shown on the bottom configured in a precision gain of 9.1. Table 1. Many of these are also represented in Figure 5 in noise gain are identical, for optimal precision. Table 1. Configuring the M Pins for Simple Noninverting Gains.

1 Output Output Output

1.08 Output Output Grounded

1.11 Output Float Grounded

1.30 Output Grounded Output

1.32 Float Output Grounded

1.33 Output Grounded Float

1.44 Output Grounded Grounded

3.19 Grounded Output Output

3.7 Float Grounded Output

3.89 Grounded Output Float

4.21 Grounded Output Grounded

9.1 Grounded Float Output

10 Float Float Grounded

11.8 Grounded Grounded Output

28 Float Grounded Float

37 Float Grounded Grounded

82 Grounded Float Float

91 Grounded Float Grounded

109 Grounded Grounded Float

118 Grounded Grounded Grounded

violated, the maximum voltage allowed on the pin. Figure 4. The LT1996 as a Classical Noninverting Op Amp

1996 F04

CLASSICAL NONINVERTING OP AMP CONFIGURATION. IMPLEMENTED WITH LT1991. RF = 45k, RG = 5.6k, GAIN = 9.1. THE AVAILABLE RESISTORS TO ARRIVE AT DESIRED RF AND RG. WE PROVIDE YOU WITH <0.1% RESISTORS.

Figure 5. Some Implementations of Classical Noninverting

1996 F05

Figure 6. LT1996 Provides for Easy Attenuation to the Op Amp’s Figure 7. Over 600 Unique Gain Settings Achievable with the Table 2 as a design reference. attenuations in Tables 1 and 2, and seeking the best match. about 50% as seen in Figure 7. Table 2. Configuring the P Pins for Various Attenuations. Those

0.0085 Grounded Grounded Grounded Driven

0.0092 Grounded Grounded Float Driven

0.0110 Grounded Float Grounded Driven

0.0122 Grounded Float Float Driven

0.0270 Float Grounded Grounded Driven

0.0357 Float Grounded Float Driven

0.0763 Grounded Grounded Driven Grounded

0.0769 Grounded Grounded Driven Float

0.0847 Grounded Grounded Driven Driven

0.0989 Grounded Float Driven Grounded

0.1 Grounded Float Driven Float

0.110 Grounded Float Driven Driven

0.229 Grounded Driven Grounded Grounded

0.231 Grounded Driven Grounded Float

0.237 Grounded Driven Grounded Driven

0.243 Float Grounded Driven Grounded

0.248 Grounded Driven Float Grounded

0.25 Float Grounded Driven Float

0.25 Grounded Driven Float Float

0.257 Grounded Driven Float Driven

0.270 Float Grounded Driven Driven

0.305 Grounded Driven Driven Grounded

0.308 Grounded Driven Driven Float

0.314 Grounded Driven Driven Driven

0.686 Driven Grounded Grounded Grounded

0.692 Driven Grounded Grounded Float

0.695 Driven Grounded Grounded Driven

0.730 Float Driven Grounded Grounded

0.743 Driven Grounded Float Grounded

0.75 Float Driven Grounded Float

0.752 Driven Grounded Float Driven

0.757 Float Driven Grounded Driven

0.763 Driven Grounded Driven Grounded

0.769 Driven Grounded Driven Float

0.771 Driven Grounded Driven Driven

0.890 Driven Float Grounded Grounded

0.9 Float Float Driven Grounded

0.901 Driven Float Grounded Driven

0.915 Driven Driven Grounded Grounded

0.923 Driven Driven Grounded Float

0.924 Driven Driven Grounded Driven

0.964 Float Driven Float Grounded

0.973 Float Driven Driven Grounded

0.988 Driven Float Float Grounded

0.989 Driven Float Driven Grounded

0.991 Driven Driven Float Grounded

0.992 Driven Driven Driven Grounded

1996 F06

1996 F07

Table 3. Configuring the M Pins for Simple Inverting Gains

1996 F08

CLASSICAL INVERTING OP AMP CONFIGURATION. THE AVAILABLE RESISTORS TO ARRIVE AT DESIRED RF AND RG. WE PROVIDE YOU WITH <0.1% RESISTORS. Figure 8. The LT1996 as a Classical Inverting Op Amp. Note the

1996 F09

Figure 9. It Is Simple to Get Precision Inverting Gains with the LT1996.

Figure 10. Difference Amplifier Using the LT1996. Gain Is Set shows the difference gains and how they are achieved. Table 4. Connections Giving Difference Gains for the LT1996

0.083 P9 M9 M27, M81 P27, P81

0.110 P9 M9 M81 P81

0.297 P27 M27 M9, M81 P9, P81

0.321 P9 M9 M27 P27

0.329 P27 M27 M81 P81

0.439 P9, P27 M9, M27 M81 P81

2.189 P81 M81 M9, M27 P9, P27

2.700 P27 M27 M9 P9

2.893 P81 M81 M27 P27

3.214 P9, P81 M9, M81 M27 P27

8.1 P81 M81 M9 P9

9 P9 M9

10.8 P27, P81 M27, M81 M9 P9

27 P27 M27

36 P9, P27 M9, M27

81 P81 M81

90 P9, P81 M9, M81

108 P27, P81 M27, M81

117 P9, P27, P81 M9, M27, M81

1996 F10

Figure 11. Many Difference Gains Are Achievable Just by Strapping the Pins

1996 F11

integer gains are achievable, as shown in Table 5 below. Table 5. Connections Using Cross-Coupling. Note That Equations

18 P27, M9 M27, P9 27 – 9 39 14 46 16

45 P81, M27, M9 M81, P27, P9 81 – 27 – 9 117 5 12 6

54 P81, M27 M81, P27 81 – 27 108 5 16 6

63 P81, P9, M27 M81, M9, P27 81 + 9 – 27 117 5 16 5

72 P81, M9 M81, P9 81 – 9 90 6 45 6

99 P81, P27, M9 M81, M27, P9 81 + 27 – 9 117 5 45 4

Figure 12. Another Method of Selecting Difference Gain Is “Cross-Coupling.” Figure 13. Integer Gain Difference

1996 F13

DASHED CONNECTIONS REDUCE THE GAIN FROM 3 T0 2. + VOLTAGE. CONNECTING P27 AND M9 GIVES 27 – 9 = 18. – ARE SYMMETRIC: M27 AND P9.

This class of difference amplifier remains to be discussed. upper and lower common mode extremes respectively. Figure 14. Extending CM Input Range

1996 F14

RESISTORS RT CONNECTED TO VTERM. Table 6. HighV CM Connections Giving Difference Gains

9 P9 M9 10 10/9 • V LIM - VREF/9

9 P9 M9 P27, M27 37 37/9 • V LIM – VREF/9 – 3 • VTERM

9 P9 M9 P81, M81 91 91/9 • V LIM – VREF/9 – 9 • VTERM

9 P9 M9 P27||P81 118 118/9 • V LIM – VREF/9 – 12 • VTERM

1996 F15

Figure 15. Common Mode Ranges for Various LT1996 Difference Amp Configurations on VS = 3V, 0V, with Gain = 9

1996 F16

Figure 16. Common Mode Ranges for Various LT1996 Difference Amp Configurations on VS = 5V, 0V, with Gain = 9

Figure 17. Common Mode Ranges for Various LT1996 Difference Amp Configurations on VS = ±5V, with Gain = 9

1996 F17

Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However, no responsibility is assumed for its use. Linear Technology Corporation makes no represen- tation that the interconnection of its circuits as described herein will not infringe on existing patent rights. PACKAGE DESCRIPTIO U MSOP (MS) 0603 0.53 ± 0.152 (.021 ± .006) SEATING PLANE 0.18 (.007) 1.10 (.043) MAX 0.17 – 0.27 (.007 – .011) TYP 0.127 ± 0.076 (.005 ± .003) 0.86 (.034) REF 0.50 (.0197) BSC 12 3 45 4.90 ± 0.152 (.193 ± .006) 0.497 ± 0.076 (.0196 ± .003) REF8910 7 6 3.00 ± 0.102 (.118 ± .004) (NOTE 3) 3.00 ± 0.102 (.118 ± .004) (NOTE 4) NOTE: 1. DIMENSIONS IN MILLIMETER/(INCH) 2. DRAWING NOT TO SCALE 3. DIMENSION DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS. MOLD FLASH, PROTRUSIONS OR GATE BURRS SHALL NOT EXCEED 0.152mm (.006") PER SIDE 4. DIMENSION DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS. INTERLEAD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.152mm (.006") PER SIDE 5. LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.102mm (.004") MAX 0.254 (.010) 0° – 6° TYP DETAIL “A” DETAIL “A” GAUGE PLANE 5.23 (.206) MIN 3.20 – 3.45 (.126 – .136) 0.889 ± 0.127 (.035 ± .005) RECOMMENDED SOLDER PAD LAYOUT 0.305 ± 0.038 (.0120 ± .0015) TYP 0.50 (.0197) BSC 10-Lead Plastic DFN (3mm × 3mm) (Reference LTC DWG # 05-08-1699) 3.00 ±0.10 (4 SIDES) NOTE: 1. DRAWING TO BE MADE A JEDEC PACKAGE OUTLINE M0-229 VARIATION OF (WEED-2). CHECK THE LTC WEBSITE DATA SHEET FOR CURRENT STATUS OF VARIATION ASSIGNMENT 2. DRAWING NOT TO SCALE 3. ALL DIMENSIONS ARE IN MILLIMETERS 4. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED 0.15mm ON ANY SIDE 5. EXPOSED PAD SHALL BE SOLDER PLATED 6. SHADED AREA IS ONLY A REFERENCE FOR PIN 1 LOCATION ON THE TOP AND BOTTOM OF PACKAGE 0.38 ± 0.10 BOTTOM VIEW—EXPOSED PAD 1.65 ± 0.10 (2 SIDES) 0.75 ±0.05 R = 0.115 TYP 2.38 ±0.10 (2 SIDES) 106 PIN 1 TOP MARK (SEE NOTE 6)

0.200 REF

0.00 – 0.05 (DD10) DFN 1103 0.25 ± 0.05 2.38 ±0.05 (2 SIDES) RECOMMENDED SOLDER PAD PITCH AND DIMENSIONS 1.65 ±0.05 (2 SIDES)2.15 ±0.05 0.50 BSC 0.675 ±0.05 3.50 ±0.05 PACKAGE OUTLINE 0.25 ± 0.05

0.50 BSC

PART NUMBER DESCRIPTION COMMENTS LT1990 High Voltage Difference Amplifier ±250V Input Common Mode, Micropower, Pin Selectable Gain = 1, 10 LT1991 Precision, 100 µA Gain Selectable Amplifier Gain Resistors of 450k, 150k, 50k LT1995 30MHz, 1000V/ µs Gain Selectable Amplifier High Speed, Pin Selectable Gain = –7 to 8 LT6010/LT6011/LT6012 Single/Dual/Quad Precision Op Amp Similar Performance as LT1996 Diff Amp, 135 µA, 14nV√Hz, Rail-to-Rail Out LT6013/LT6014 Single/Dual Precision Op Amp Lower Noise A V ≥ 5 Version of LT1991, 145µA, 8nV/√Hz, Rail-to-Rail Out LTC6910-X Programmable Gain Amplifiers 3 Gain Configurations, Rail-to-Rail Input and Output Linear Technology Corporation 1630 McCarthy Blvd., Milpitas, CA 95035-7417 (408) 432-1900 ● FAX: (408) 434-0507 ● www.linear.com © LINEAR TECHNOLOGY CORPORATION 2005 LT/TP 0205 1K • PRINTED IN USA RELATED PARTS TYPICAL APPLICATIO U VM VP VOUT LT1996

1996 TA02

Micropower AV = 90 Instrumentation Amplifier VIN– VIN+ VIN VS+ VS– VS+ VS– M81 M27 P27 P81 LT1996 M81 M27 P27 P81 VOUTLT1996 GAIN = 117 BW = 4Hz TO 5kHz 10k 9(VIN+ – VIN–) 10kΩILOAD = 0.1µF

1996 TA03

VIN– VIN+ VOUT– VOUT+ VOCM VS+ VS– M81 M27 P27 P81 LT1996 10k 10k USE VOCM TO SET THE DESIRED OUTPUT COMMON MODE LEVEL LT6010 Bidirectional Controlled Current Source AC Coupled Amplifier Differential Input/Output G = 9 Amplifier