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82P33810

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Synchronization Management Unit for IEEE 1588 and Synchronous Ethernet September 4, 2017

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82P33810 RENESAS

Document overview

Manufacturer or author: IDT
PDF pages: 72

Technical content

Datasheet sections

1 PIN ASSIGNMENT
2 PIN DESCRIPTION
2.1 RECOMMENDATIONS FOR UNUSED INPUT AND OUTPUT PINS
2.1.1 Inputs
2.1.2 Outputs
2.2 RESET OPERATION
2.3 MS/SL PIN USAGE
3 FUNCTIONAL DESCRIPTION
3.1 IEEE 1588 AND SYNCHRONOUS ETHERNET (SYNCE) SYSTEM ARCHITECTURES
3.1.1 IEEE1588 and SyncE Single Blade Architecture
3.1.2 Distributed Architecture for T-BC and T-TSC, IEEE 1588 in the Timing Card
3.1.3 T-BC and T-TSC - IEEE 1588 in the Line Card
3.1.4 Distributed Architecture for Telecom Slave clock
3.1.4.1 Telecom Slave Clock - IEEE 1588 in the Timing Card
3.1.4.2 Telecom Slave Clock - IEEE 1588 in the Line Card
3.2 SYNCHRONOUS ETHERNET, SONET AND SDH ARCHITECTURE
3.3 HARDWARE FUNCTIONAL DESCRIPTION
3.3.1 System clock
3.3.2 Modes of operation
3.3.2.1 DCO control modes
3.3.2.2 Disciplined DCO
3.3.2.3 Combo Mode
3.3.2.4 DPLL1 and DPLL2 Operating Mode
3.3.2.5 DPLL3 Operating Mode
3.3.3 Input Clocks and frame sync
3.3.3.1 Input Clock Pre-divider
3.3.3.2 Input Clock Quality Monitoring
3.3.3.3 Input Clock Selection
3.3.4 DPLL Locking Process
3.3.4.1 Fast Loss
3.3.4.2 Fine Phase Loss
3.3.4.3 Hard Limit Exceeding
3.3.4.4 Locking Status
3.3.4.5 Phase Lock Alarm
3.3.5 APLL1 and APLL2
3.3.6 Output Clocks & Frame Sync Signals
3.3.6.1 Output Clocks
3.3.6.2 Frame Sync Signals
3.3.7 Input and output Phase control
3.3.7.1 DPLL1 and DPLL2 Phase offset control
3.3.7.2 Input Phase control
3.3.7.3 Output Phase control
3.3.8 Time of Day counter
4 POWER SUPPLY FILTERING TECHNIQUES

Synchronization Management Unit (SMU) provides tools to manage physical layer and packet based synchronous clocks for IEEE 1588 / PTP Telecom Profile applications
Supports independent IEEE 1588 and Synchronous Ethernet (SyncE) timing paths
Combo mode provides SyncE physi cal layer frequency support for IEEE 1588 Telecom Boundary Clocks (T-BC) and Telecom Time Slave Clocks (T-TSC) per G.8273.2
Digital PLL 1 (DPLL1) and DPLL 2 can be configured as Digitally Con- trolled Oscillators (DCOs) for PTP clock synthesis
DCO frequency resolution is [(77760 / 1638400) * 2^-48] or ~1.686305041e-10 ppm
DPLL1 and DPLL2 generate G.8262 compliant SyncE clocks
Two independent Time of Day (ToD) counters/time accumulators, one associated with each of DPLL1 and DPLL2, can be used to track dif- ferences between the two time dom ains and to time-stamp external events
DPLL3 performs rate conversions to frequency synchronization inter- faces or for other general purpose timing applications
APLL1 and APLL2 generate clocks with jitter < 1 ps RMS (12 kHz to

20 MHz) for: 1000BASE-T and 1000BASE-X

Fractional-N input dividers suppor t a wide range of reference frequen- cies
Locks to 1 Pulse Per Second (PPS) references
It can be configured from an external EEPROM after reset

FEATURES

Composite clock inputs (IN1 and IN 2) accept 64 kHz synchronization interface signals per ITU-T G.703
Differential reference inputs (IN3 to IN8) accept clock frequencies between 1 PPS and 650 MHz
Single ended inputs (IN9 to IN14) accept reference clock frequencies between 1 PPS and 162.5 MHz
Loss of Signal (LOS) pins (LOS0 to LOS3) can be assigned to any clock reference input
Reference monitors qualify/dis qualify references depending on activ- ity, frequency and LOS pins
Automatic reference selection state machines select the active refer- ence for each DPLL based on the refer ence monitors, priority tables, revertive and non-revertive settings and other programmable settings
Fractional-N input dividers enable t he DPLLs to lock to a wide range of reference clock frequencies including: 10/100/1000 Ethernet, 10G Ethernet, OTN, SONET/SDH, PDH, TDM, GSM, CPRI and GNSS fre- quencies
Any reference input (IN3 to IN14) can be designated as external sync pulse inputs (1 PPS, 2 kHz, 4 kHz or 8 kHz) associated with a select- able reference clock input
FRSYNC_8K_1PPS and MFRSYNC_2K_1PPS output sync pulses that are aligned with the selected ex ternal input sync pulse input and frequency locked to the associated reference clock input
DPLL1 and DPLL2 can be configured with bandwidths between 0.09 mHz and 567 Hz
DPLL1 and DPLL2 lock to input references with frequencies between

1 PPS and 650 MHz

DPLL3 locks to input references with frequencies between 8 kHz and

650 MHz

DPLL1 and DPLL2 comply with ITU-T G.8262 for Synchronous Ether- net Equipment Clock (EEC), and G.813 for Synchronous Equipment Clock (SEC); and Telcordia GR-253-CORE for Stratum 3 and SONET Minimum Clock (SMC)
DPLL1 and DPLL2 generate clocks with PDH, TDM, GSM, CPRI/ OBSAI, 10/100/1000 Ethernet and GNSS frequencies; these clocks are directly available on OUT1 and OUT8
DPLL1 and DPLL2 can be configured as DCOs to synthesize IEEE 1588 clocks
DPLL3 generates N x 8 kHz clocks up to 100 MHz that are output on OUT10 and OUT11
APLL1 and APLL2 can be connected to DPLL1 or DPLL2
APLL1 and APLL2 generate 10/100/1000 Ethernet, 10G Ethernet, or SONET/SDH frequencies
Any of eight common TCXO/OCXO frequencies can be used for the System Clock: 10 MHz, 12.8 MHz, 13 MHz, 19.44 MHz, 20 MHz, 24.576 MHz, 25 MHz or 30.72 MHz
The I2C slave, SPI or the UART interface can be used by a host pro- cessor to access the control and status registers
The I2C master interface can autom atically load a device configura- tion from an external EEPROM after reset
DPLL1 or DPLL3 can be connected to an internal composite clock generator that outputs its 64 kHz synchronization signal on OUT8
Differential outputs OUT3 to OU T6 output clocks with frequencies between 1 PPS and 650 MHz
Single ended outputs OUT1, OUT2, OUT7 and OUT8 output clocks with frequencies between 1 PPS and 125 MHz
Single ended outputs OUT10 and OUT 11 output clocks N*8kHz multi- ples up to 100 MHz
DPLL1 and DPLL2 support independent programmable delays for each of IN3 to IN14; the delay for each input is programmable in steps of 0.61 ns with a range of ~±78 ns
The input to output phase delay of DPLL1 and DPLL2 is programma- ble in steps of 0.0745 ps with a total range of ±20 μs
The clock phase of each of the out put dividers for OUT1 (from APLL1) to OUT8 is individually programmable in steps of ~200 ps with a total range of +/-180°
1149.1 JTAG Boundary Scan
144-pin CABGA green package 82P33810 Datasheet Synchronization Management Unit for IEEE 1588 and Synchronous Ethernet

APPLICATIONS

Access routers, edge routers, core routers
Carrier Ethernet switches
Multiservice access platforms
PON OLT
LTE eNodeB
IEEE 1588 / PTP Telecom Profile clock synthesizer
ITU-T G.8273.2 Telecom Boundary Clock (T-BC) and Telecom Time Slave Clock (T-TSC)
ITU-T G.8264 Synchronous Equi pment Timing Source (SETS)
ITU-T G.8263 Packet-based Equipment Clock (PEC)
ITU-T G.8262 Synchronous Ethernet Equipment Clock (EEC)
ITU-T G.813 Synchronous Equipment Clock (SEC)
Telcordia GR-253-CORE Stratu m 3 Clock (S3) and SONET Mini- mum Clock (SMC)

DESCRIPTION

The 82P33810 Synchronization Management Unit (SMU) provides tool s to manage timing references, cl ock sources and timing paths f or IEEE 1588 / Precision Time Protocol (PTP) and Synchronous Ethernet (SyncE) based clocks . The device supports up to three independent timing paths that control: PTP clock synthesis; SyncE clock generation; and general purpose frequency translation. The device supports physical layer timing with Digital PLLs (DPLLs) and it supports packet based timing with Digitally Controlled O scillators (DCOs). Input-to- input, input-t o-output and output-to- output phase skew can all be precisely managed. The device outputs low-jitter clocks that can directly synchronize Ethernet int erfaces; as well as SONET/SDH and PDH interfaces and IEEE 1588 Time Stamp Units (TSUs). The 82P33810 accepts six differential reference inputs and six si ngle ended reference inputs that can operate at common GNSS, E thernet, SONET/SDH and PDH frequencies that range in frequency from 1 Pulse Per Second (PPS) to 650 MHz. The device also provides two Alternate Mark Inversion (AMI) inputs for Composite Clock (CC) signals bearing 64 kHz, 8 kHz and 0.4 kHz synchronization information. The references are continu- ally monitored for loss of signal and for frequency offset per user programmed threshol ds. All of the references are available to all three DPLLs. The active reference for each DPLL is determined by forced selecti on or by automatic selection bas ed on user programmed priorities and locking allow- ances and based on the reference monitors and LOS inputs. The 82P33810 can accept a clock reference and an associated phase locked sync signal as a pair. DPLL1 or DPLL2 can lock to the clock refer- ence and align the frame sync and multi-frame sync outputs with the paired sync input. The device allows any of the differential or single ended refer- ence inputs to be configured as sync inputs that can be associat ed with any of the other diffe rential or single ended reference inputs. The input sync signals can have a frequency of 1 PPS, 2 kHz, 4 kHz or 8 kHz. Th is feature enables DPLL1 or DPLL2 to phase align its frame sync and multi-frame sync outputs with a sync input without the need use a low bandwidth setting to lock directly to the sync input. DPLL1 and DPLL2 support four primary operating modes: Free-Run, Locked, Holdover and DCO. In Free-Run mode the DPLLs synthesize clocks based on the system clock alone. In Locked mode the DPLLs filter reference clock jitter with the selected bandwidth. In Locked mode, the long-term output frequency accuracy is the same as the long term frequency accu racy of the selected input reference. In Holdover mode, th e DPLL uses fre- quency data acquired while in Locked mode to generate accurate freque ncies when input references are not available. In DCO mode the DPLL con- trol loop is opened and the DCO can be controlled by a PTP clock recovery servo running on an external processor to synthesize PTP clocks. The 82P33810 requires a system clock for its re ference monitors and other digital circuitry. The fr equency accuracy of the syst em clock deter- mines the frequency accuracy of the DPLLs in Free-Run mode. The frequency stability of the system clock determines the frequenc y stability of the DPLLs in Free-Run mode and in Holdover mode; and it affects the wander generation of the DPLLs in Locked and DCO modes. When used with a suitable system clock, DPLL1 and DPLL2 meet the frequency accuracy, pull-in, hold-in, pull-out, noise generation, noise toler- ance, transient response, and holdover performance requirements of the following applications: ITU-T G.8262/G.813 EEC/SEC options 1 and 2, ITU- T G.8263, ITU-T G.8273.2, Telcordia GR-1244 Stratum 3 (S3), Telcordia GR-253-CORE Stratum 3 (S3) and SONET Minimum Clock (SMC). DPLL1 and DPLL2 can be configured with a range of selectable filt ering bandwidths from 0.09 mHz to 567 Hz. The 17 mHz bandwidth can be used to lock the DPLL directly to a 1 PPS reference. The 69 mHz and the 92 mHz bandwidths can be used for G.8273.2. The 92 mHz bandwidth can for G.8262/G.813 Option 1 applications. Bandwidths above 10 Hz can be used in jitter attenuation and rate conversion applications. DPLL1 and DPLL2 are each connected to Time of Da y (ToD) counters or time accumulators; these ToD counters/time accumulators can be used to track differences between the two time domains and to time-stamp external events by using reference inputs as triggers. DPLL3 supports three primary operation modes: Free-Run, Locked and Holdover. DPLL3 is a wideband (BW > 25Hz) frequency translator that can be used, for example, to convert a recovered line clock to a 1.544 MHz or 2.048 MHz synchronization interface clock. In Telecom Boundary Clock (T-BC) and Telecom Time Slave Clock (T-TSC) applications per ITU-T G.8275.2, DPLL1 and DPLL2 are both used; one DPLL is configured as a DCO to synthesize PTP clocks and the other DPLL is configured as an EEC/SEC to generate physical la yer clocks. Combo mode provides physical layer frequency support from the EEC/SEC to the PTP clock.

clocks for the T0 reference point and DPLL3 can be used to output clocks for the T4 reference point. output clocks generated by APLL1 and APLL2 are suitable for serial GbE and lower rate interfaces. nected to either DPLL1 or DPLL3. DPLLs, APLL1 and APLL2, the I2C master interface can automatically load a configuration from an external EEPROM after reset. Figure 1. Functional Block Diagram

1 PIN ASSIGNMENT

Figure 2. Pin Assignment (Top View)

1 VDDDO VSSDO VSSA DPLL3_LOCK IN14 IN13 Frsync_8K_1PP

2 PIN DESCRIPTION

Table 1: Pin Description Pin No. Name I/O Type Description Global Control Signal E1 OSCI I CMOS OSCI: Crystal Oscillator System Clock A clock provided by a crystal oscillator is input on this pin. It is the system clock for the device. The oscillator frequency is selected via pins XO_FREQ0 ~ XO_FREQ2 K8 MS/SL I pull-up CMOS MS/SL: Master / Slave Selection This pin, together with the MS_SL_CTRL bit, controls whether the device is configured as the Master or as the Slave. The signal level on this pin is reflected by the MASTER_SLAVE bit. MS_SL = 0: Slave MS_SL = 1: Master (default with internal pull-up) A11 SONET/SDH/ LOS3 I pull-down CMOS SONET/SDH: SONET / SDH Frequency Selection During reset, this pin determines the default value of the IN_SONET_SDH bit (b2, 09H): High: The default value of the IN_SONET_SDH bit is ‘1’ (SONET); Low: The default value of the IN_SONET_SDH bit is ‘0’ (SDH). After reset, this pin takes on the operation of LOS3 LOS3- This pin is used to disqualify input clocks. See input clocks section for more details. K6 RSTB I pull-up CMOS RSTB: Reset Refer to section 2.2 reset operation for detail. XO_FREQ0/ LOS0 XO_FREQ1/ LOS1 XO_FREQ2/ LOS2 I pull-down CMOS XO_FREQ0 ~ XO_FREQ2: These pins set the oscillator frequency. XO_FREQ[2:0] Oscillator Frequency (MHz) 000 10.000 001 12.800 010 13.000 011 19.440 100 20.000 101 24.576 110 25.000 111 30.720 LOS0 ~ LOS2 - These pins are used to disqualify input clocks. See input clocks section for more details. After reset, this pin takes on the operation of LOS0-LOS2 Input Clock and Frame Synchronization Input Signal K10 IN1 I AMI IN1: Input Clock 1 A 64 kHz + 8 kHz or 64 kHz + 8 kHz + 0.4 kHz composite clock is input on this pin. AMI input has internal 1k ohm to 1.5V termination. K9 IN2 I AMI IN2: Input Clock 2 A 64 kHz + 8 kHz or 64 kHz + 8 kHz + 0.4 kHz composite clock is input on this pin. AMI input has internal 1k ohm to 1.5V termination. M12 M11 IN3_POS IN3_NEG I PECL/LVDS IN3_POS / IN3_NEG: Positive / Negative Input Clock 3 A reference clock is input on this pin.This pin can also be used as a sync input, and in this case a 2 kHz, 4 kHz, 8 kHz, or 1PPS signal can be input on this pin. L12 L11 IN4_POS IN4_NEG I PECL/LVDS IN4_POS / IN4_NEG: Positive / Negative Input Clock 4 A reference clock is input on this pin.This pin can also be used as a sync input, and in this case a 2 kHz, 4 kHz, 8 kHz, or 1PPS signal can be input on this pin. K12 K11 IN5_POS IN5_NEG I PECL/LVDS IN5_POS / IN5_NEG: Positive / Negative Input Clock 5 A reference clock is input on this pin.This pin can also be used as a sync input, and in this case a 2 kHz, 4 kHz, 8 kHz, or 1PPS signal can be input on this pin. J12 J11 IN6_POS IN6_NEG I PECL/LVDS IN6_POS / IN6_NEG: Positive / Negative Input Clock 6 A reference clock is input on this pin.This pin can also be used as a sync input, and in this case a 2 kHz, 4 kHz, 8 kHz, or 1PPS signal can be input on this pin. G12 G11 IN7_POS IN7_NEG I PECL/LVDS IN7_POS / IN7_NEG: Positive / Negative Input Clock 7 A reference clock is input on this pin.This pin can also be used as a sync input, and in this case a 2 kHz, 4 kHz, 8 kHz, or 1PPS signal can be input on this pin.

8©2017 Integrated Device Technology, Inc. 82P33810 Datasheet September 4, 2017 F12 F11 IN8_POS IN8_NEG I PECL/LVDS IN8_POS / IN8_NEG: Positive / Negative Input Clock 8 A reference clock is input on this pin.This pin can also be used as a sync input, and in this case a 2 kHz, 4 kHz, 8 kHz, or 1PPS signal can be input on this pin. J10 IN9 I pull-down CMOS IN9: Input Clock 9 A reference clock is input on this pin.This pin can also be used as a sync input, and in this case a 2 kHz, 4 kHz, 8 kHz, or 1PPS signal can be input on this pin. H10 IN10 I pull-down CMOS IN10: Input Clock 10 A reference clock is input on this pin.This pin can also be used as a sync input, and in this case a 2 kHz, 4 kHz, 8 kHz, or 1PPS signal can be input on this pin. G10 IN11 I pull-down CMOS IN11: Input Clock 11 A reference clock is input on this pin.This pin can also be used as a sync input, and in this case a 2 kHz, 4 kHz, 8 kHz, or 1PPS signal can be input on this pin. F10 IN12 I pull-down CMOS IN12: Input Clock 12 A reference clock is input on this pin.This pin can also be used as a sync input, and in this case a 2 kHz, 4 kHz, 8 kHz, or 1PPS signal can be input on this pin. E11 IN13 I pull-down CMOS IN13: Input Clock 13 A reference clock is input on this pin.This pin can also be used as a sync input, and in this case a 2 kHz, 4 kHz, 8 kHz, or 1PPS signal can be input on this pin. E10 IN14 I pull-down CMOS IN14: Input Clock 14 A reference clock is input on this pin.This pin can also be used as a sync input, and in this case a 2 kHz, 4 kHz, 8 kHz, or 1PPS signal can be input on this pin. Output Frame Synchronization Signal E12 FRSYNC _8K_1PPS OC M O S FRSYNC_8K_1PPS: 8 kHz Frame Sync Output An 8 kHz signal or a 1PPS sync signal is output on this pin. C12 MFRSYNC _2K_1PPS OC M O S MFRSYNC_2K_1PPS: 2 kHz Multiframe Sync Output A 2 kHz signal or a 1PPS sync signal is output on this pin. Output Clock OUT1 OUT2 OC M O S OUT1 ~ OUT2: Output Clock 1 ~ 2 OUT3_POS OUT3_NEG O PECL/LVDS OUT3_POS / OUT3_NEG: Positive / Negative Output Clock 3 This output is set to LVDS by default.The LVDS output has internal 100 ohm termination. OUT4_POS OUT4_NEG O PECL/LVDS OUT4_POS / OUT4_NEG: Positive / Negative Output Clock 4 This output is set to LVDS by default.The LVDS output has internal 100 ohm termination. OUT5_POS OUT5_NEG O PECL/LVDS OUT5_POS / OUT5_NEG: Positive / Negative Output Clock 5 This output is set to LVDS by default.The LVDS output has internal 100 ohm termination. OUT6_POS OUT6_NEG O PECL/LVDS OUT6_POS / OUT6_NEG: Positive / Negative Output Clock 6 This output is set to LVDS by default.The LVDS output has internal 100 ohm termination. C10 OUT7 OUT8 OC M O S OUT7 ~ OUT8: Output Clock 7 ~ 8 M10 OUT9_POS OUT9_NEG OA M I OUT9_POS / OUT9_NEG: Positive / Negative Output Composite Clock A 64 kHz + 8 kHz or 64 kHz + 8 kHz + 0.4 kHz composite clock is differentially output on this pair of pins. D12 D11 OUT10 OUT11 OC M O S OUT10 ~ OUT11: Output Clock 10 ~ 11 Miscellaneous C9, A9, D8 CAP1, CAP2, CAP3 CAP1, CAP2 and CAP3: Analog Power Filter Capacitor connection 1 to 3. These capacitors are be part of the power filtering. Lock Signal E9 DPLL3_LOCK OC M O S DPLL3_LOCK This pin goes high when DPLL3 is locked Table 1: Pin Description (Continued) Pin No. Name I/O Type Description

9©2017 Integrated Device Technology, Inc. 82P33810 Datasheet September 4, 2017 G9 DPLL2_LOCK OC M O S DPLL2_LOCK This pin goes high when DPLL2 is locked H9 DPLL1_LOCK OC M O S DPLL1_LOCK This pin goes high when DPLL1 is locked Microprocessor Interface J9 INT_REQ O Tri-state CMOS INT_REQ: Interrupt Request This pin is used as an interrupt request. B11 C11 MPU_MODE1/ I2CM_SCL MPU_MODE0/ I2CM_SDA I/O pull-up CMOS/ Open Drain MPU_MODE[1:0]: Microprocessor Interface Mode Selection During reset, these pins determine the default value of the MPU_SEL_CNFG[1:0] bits as fol- lows: 00: I2C mode 01: SPI mode 10: UART mode 11: I2C master (EEPROM) mode I2CM_SCL: Serial Clock Line In I2C master mode, the serial clock is output on this pin. I2CM_SDA: Serial Data Input for I2C Master Mode In I2C master mode, this pin is used as the for the serial data. D9 SDI/I2C_AD2/ UART_RX I pull-down CMOS SDI: Serial Data Input In Serial mode, this pin is used as the serial data input. Address and data on this pin are seri- ally clocked into the device on the rising edge of SCLK. I2C_AD2: Device Address Bit 2 In I2C mode, I2C_AD[2:0] pins are the address bus of the microprocessor interface. UART_RX In UART mode, this pin is used as the receive data (UART Receive) E5 CLKE/I2C_AD1 I pull-down CMOS CLKE: SCLK Active Edge Selection In Serial mode, this pin is an input, it selects the active edge of SCLK to update the SDO: High - The falling edge; Low - The rising edge. I2C_AD1: Device Address Bit 1 In I2C mode, I2C_AD[2:0] pins are the address bus of the microprocessor interface. C8 CS/I2C_AD0 I pull-up CMOS CS: Chip Selection In Serial modes, this pin is an input.A transition from high to low must occur on this pin for each read or write operation and this pin should remain low until the operation is over. I2C_AD0: Device Address Bit 0 In I2C mode, I2C_AD[2:0] pins are the address bus of the microprocessor interface. D10 SCLK/I2C_SCL I CMOS SCLK: Shift Clock In Serial mode, a shift clock is input on this pin. Data on SDI is sampled by the device on the rising edge of SCLK. Data on SDO is updated on the active edge of SCLK. The active edge is determined by the CLKE. I2C_SCL: Serial Clock Line In I2C mode, the serial clock is input on this pin. Table 1: Pin Description (Continued) Pin No. Name I/O Type Description

10©2017 Integrated Device Technology, Inc. 82P33810 Datasheet September 4, 2017 C5 SDO/I2C_SDA/ UART_TX I/O CMOS/ Open Drain SDO: Serial Data Output In Serial mode, this pin is used as the serial data output. Data on this pin is serially clocked out of the device on the active edge of SCLK. I2C_SDA: Serial Data Input/Output In I2C mode, this pin is used as the input/output for the serial data. UART_TX: In UART mode, this pin is used as the transmit data (UART Transmit) JTAG (per IEEE 1149.1) F1 TMS I pull-up CMOS TMS: JTAG Test Mode Select The signal on this pin controls the JTAG test performance and is sampled on the rising edge of TCK. K3 TRSTB I pull-up CMOS TRSTB: JTAG Test Reset (Active Low) A low signal on this pin resets the JTAG test port. This pin should be connected to ground when JTAG is not used. G1 TCK I pull-down CMOS TCK: JTAG Test Clock The clock for the JTAG test is input on this pin. TDI and TMS are sampled on the rising edge of TCK and TDO is updated on the falling edge of TCK. If TCK is idle at a low level, all stored-state devices contained in the test logic will indefinitely retain their state. L3 TDI I pull-up CMOS TDI: JTAG Test Data Input The test data are input on this pin. They are clocked into the device on the rising edge of TCK. L5 TDO O tri-state CMOS TDO: JTAG Test Data Output The test data are output on this pin. They are clocked out of the device on the falling edge of TCK. TDO pin outputs a high impedance signal except during the process of data scanning. Power & Ground C1, C6, C7, D2, F2, F9, G2, H2, K1, K2 VDDA Power - VDDA: Analog Core Power - +3.3V DC nominal A5, A7, B2, B3, L4, M4 VDDAO Power VDDAO: Analog Output Power - +3.3V DC nominal E4, E6, L7, M8 VDDDO Power VDDDO: Digital Output Power - +3.3V DC nominal D5,F7 VDDD Power VDDD: Digital Core Power - +3.3V DC nominal L10, H12 VDDD_1_8 Power VDDD_1_8: Digital Core Power - +1.8V DC nominal B9, C2, D1, D6, D7, E2, E8, F3, F8, H3, L1, L2 VSSA Ground - VSSA: Ground B1, B4, B5, B7, K4, M3 VSSAO Ground VSSAO: Ground E7, F4, K7, M7 VSSDO Ground VSSDO: Ground D4, F6, H11, L9 VSSD Ground VSSD: Ground D3 VSSCOM Ground - VSSCOM: Ground C3, F5, G4, G5, G6, G8, H4, H5, H6, H7, H8, J3, J4, J5, J6, J7, J8 VSS Ground - VSS: Ground Other A1, A2, A3, A4, A10, A12, B10, B12, E3, G3, G7, L6 IC - - IC: Internal Connection Internal Use. This pin must be left open for normal operation. Table 1: Pin Description (Continued) Pin No. Name I/O Type Description

2.1 RECOMMENDATIONS FOR UNUSED INPUT

2.1.1 INPUTS

All control pins have internal pul l-ups or pull-downs; additional resis- tance is not required but can be added for additional protection. A 1k Ω resistor can be used. Single-Ended Clock Inputs For protection, unused single-ended clock inputs should be tied to ground. Differential Clock Inputs For applications not requiring the use of a differential input, both *_POS and *_NEG can be left floating. Though not required, but for additional protection, a 1kΩ resistor can be tied from _POS to ground.

2.1.2 OUTPUTS

For applications not requiring the use of a status pin, we recommend bringing out to a test point for debugging purposes. Single-Ended Clock Outputs All unused single-ended clock outputs can be left floating, or can be brought out to a test point for debugging purposes. Differential Clock Outputs All unused differential outputs can be left floating. We recommend that there is no trace attached. Both sides of the differential output pair should either be left floating or terminated.

2.2 RESET OPERATION

The device must be reset properly in order to ensure operations con- form with specification. To properly reset the device, the RSTB pin must be held at a low value for at least 50 usec. The dev ice should be brought out of reset only at the time when power suppl ies are stabilized and the system clock is available on OSCi pin. The RSTB can be held low until this time, or pulsed low for at least 50us after this time. The bootstrap pins (XO_FREQ[2:0], MPU_MODE[1:0], I2C_AD[2:0], MS/SL, SONET/SDH) need to be held at desired states for at least 2ms after de-assertion of RSTB pin to allow correct sampling. See Figure 3 for detail. If loading from an EEPROM, the maximum time from RSTB de- assert to have stable clocks is 100ms. Note that if there is a bad EEPROM read sequence and the EEPROM loading is repeated once or twice (three times halts the device), then this time can be 2 or 3 times longer respectively. If not loadi ng from EEPROM the maximum time from RSTB de-assert to have stable clocks is 10ms. An on-board reset circuit or a commercially available voltage supervi- sory can be used to generate the reset signal. It is also feasible to use a standalone power-up RC reset circuit. When using a power-up RC reset circuit, careful consideration must be taken into account to fine tune the circuit properly based on each power supply's specification to ensure the

2.3 MS/SL PIN USAGE

for SETS and SMU Devices on Timing Redundancy Designs.

3 FUNCTIONAL DESCRIPTION

3.1 IEEE 1588 AND SYN CHRONOUS ETHERNET

(SYNCE) SYSTEM ARCHITECTURES ITU-T is working on key recommendations for the use of IEEE 1588 for Telecom. There are several recommendations that have been pub- lished for frequency applications, they are:

ITU-T Recommendation G.8261, Timing and synchronization aspects in packet networks.
ITU-T Recommendation G.8262, Ti ming characteristics of Syn- chronous Ethernet Equipment slave clock (EEC).
ITU-T Recommendation G.8264, Di stribution of timing through packet networks
Recommendation ITU-T G.8261.1, Pa cket Delay Variation Network Limits applicable to Packet Bas ed Methods (Frequency Synchroni- zation).
Recommendation ITU-T G.8263, Ti ming Characteristics of Packet based Equipment Clocks (PEC) and Packet based Service Clocks (PSC)
ITU-T Recommendation G.8265), Architecture and requirements for packet based frequency delivery
ITU-T Recommendation G.8265.1, Prec ision time protocol telecom profile for frequency sync
ITU-T Recommendation G.8260, De finitions and terminology for synchronization in packet networks For the phase and time applications ITU-T has consented the follow- ing recommendations:
ITU-T Recommendation G.8271, Time and phase synchronization aspects of packet networks
ITU-T Recommendation G.8272, Timi ng characteristics of Primary reference time clock
ITU-T Recommendation G.8271.1, Network Limits for Time Syn- chronization in Packet Networks
ITU-T Recommendation G.8273, Framework of phase and time clocks
ITU-T Recommendation G.8273.2, Timing characteristics of tele- com boundary clocks and telecom time slave clocks
ITU-T Recommendation G.8275, Architecture and requirements for packet-based time and phase delivery
ITU-T Recommendation G.8275.1, Prec ision time protocol telecom profile for phase/time synchroniza tion with full timing support from the network Another important ITU-T Recommendation that is used in synchroni- zation networks is ITU-T Reco mmendation G.781, Synchronization Layer Functions. 82P33810 has a very flexible architecture to allow systems to sup- port the current requirements defined by ITU-T. In addition to supporting the published ITU-T Recommendations, the device has the flexibility to support future ITU-T phase/time recommendations.

3.1.1 IEEE1588 AND SYNCE SINGLE BLADE ARCHITEC-

Figure 4 shows the single blade architecture, note that only the blocks relevant to synchronization have been drawn. In this application all the synchronization functions are centralized in one card, for example in a pizza box type of system. In, the timestamps are done at the Ether- net PHY, but there are solutions that deploys a host processor that inte- grates the time stamp unit. The host processor terminates the transport layer protocol and the IEEE 1588 protocol. The timestamps are pro- cessed (servo or clock recovery algorithm) by the host processor. Based on the clock recovery algorithm the host processor will control the 82P33810 internal DCO to generate cloc ks that are locked to an IEEE 1588 master in the network. In the case of a slave node that has the frequency locked to synchro- nous Ethernet (SyncE), the 82P33810 has a combo mode that allows the frequency to be used from SyncE and the phase be controlled by IEEE 1588 (see section 3.3.2.3 Combo Mode on page 24 for more details on combo mode).

3.1.2 DISTRIBUTED ARCHITECTURE FOR T-BC AND T-

to allow very fine control of the phase of the clocks inside the equipment. page 40 for details on the phase adjustment control modes. filter PDV must be implemented in this case.

1588 Time

1588 DCO

1588 DPLL1

3.1.3 T-BC AND T-TSC - IEEE 1588 IN THE LINE CARD

Figure 6 shows a distributed architectu re that can represent a T-BC or a T-TSC implementation where t he IEEE 1588 is handled in the line cards. In this architecture IEEE 1588 protocol is terminated in the line cards. The local host processor will run the clock recovery algorithm (servo) and run the alternate Best Master Clock Algorithm (BMCA) according to ITU-T G.8275.1. The alternate BMCA determines which Telecom Grand Master (T-GM) to be used as the source of time. In, one of the packet data port will be a slave port and the others will be master ports of the T-BC. The 82P33810 disciplined DCO mode is very important for this archi- tecture as it allows the use of a simple crystal (e.g. 20ppm) at the line card, as the SyncE clock coming from the timing card will be used at the line card to implement the T-BC wi th SyncE assistance. Also in this architecture it is very important to control the IEEE 1588 clocks inde- pendently of the SyncE clocks. It is also important to be able to suppress phase transients on the SyncE clocks to not affect the IEEE 1588 clocks. See 3.3.2.2 Disciplined DCO on page 23 for mode details on the disci- plined DCO mode. To be able to meet the ITU-T G.8273.2 tight requirements described in the previous architecture, it is very important to control the delays between the clocks from the line card that is behaving as the slave port of the T-BC with line cards that are behaving as master ports. 82P33810 has individual phase adjustments to allow very fine control of the phase of the clocks inside the equipment. See 3.3.2.3 Combo Mode on page 24 for mode details on the phase adjustment control. The architecture depicted in Figure 6 can also be used for a phase and time application using G.8275. 2 and frequency application using G.8265.1 (see Figure 7). The key difference in this case is that the T-BC, T-TSC or a packet slave clock will experience Packet Delay Variation (PDV) due to the network that does not support IEEE 1588. An algorithm to filter PDV must be implemented in this case.

3.1.4 DISTRIBUTED ARCHITECTURE FOR TELECOM

3.1.4.1 Telecom Slave Clock - IEEE 1588 in the Timing Card

clock implementation where the IEEE 1588 is handled in the timing card. In this architecture IEEE 1588 protocol is terminated in the timing card. Mode on page 24 for mode details on the combo mode. Figure 7. Telecom slave clock functional model

GM1, Priority1
GM2, Priority2 Instantiation QL processing PTSF processing Request Announce Req. sync/ del resp. GM selection QL from Protocol instances PTSF signals from Protocol Instances PTSF_Unusable from PDV analysis ENABLE_REQUESTING_ UNICAST_ANNOUNCE to protocol Frequency/time correction (runtime) from PDV mitigationCorrection for clock ENABLE_REQUESTING_ SYNC_DEL_RESP to protocol Freq/time correction PDV analysis PDV analysis processing Telecom slave PTSF-lossSync, PTSF-lossAnnounce PTSF_Unusable

3.1.4.2 Telecom Slave Clock - IEEE 1588 in the Line Card

clock implementation where the IEEE 1588 is handled in the line cards. In this architecture IEEE 1588 protocol is terminated at the line cards. be used as a source of frequency and/or time.

3.3.2.2 Disciplined DCO on page 23 for mode details on the disciplined

3.2 SYNCHRONOUS ET HERNET, SONET AND

ITU-T Recommendation G.8262, Ti ming characteristics of Syn- chronous Ethernet Equipment slave clock (EEC)
ITU-T Recommendation G.8264, Di stribution of timing through packet networks
ITU-T Recommendation G.812, Ti ming requirements of slave clocks suitable for use as node clocks in synchronization networks.
ITU-T Recommendation G.813, Timing characteristics of SDH equipment slave clocks (SEC).
GR-253-CORE - Telcordia Technol ogies Generic Requirements - Issue 5, October 2009
GR-1244-CORE - Telcordia Technol ogies Generic Requirements - Issue 4, October 2009
ATIS-0900101.2006 - T1.101 - Synchronization Interface Standard Figure 8 shows a single blade architecture that it is usually used in simple equipment. Figure 9 shows an active/redundant ar chitecture, as described before it is usually used in Telecom equipment that are designed to have a redundant timing card in case of primary timing card failure. The redundant timing card mimics the output of the active timing card, so in case of failure the system will still provide proper synchronization. Single Blade CDR SyncE/ SONET /SDH PHY SyncE-RxCK SyncE-TxCK Ethernet TCXO BITS/SSU SyncE (T0) A P L L LOS

Figure 8. SyncE/SONET/SDH single blade application

3.3 HARDWARE FUNCTI ONAL DESCRIPTION

3.3.1 SYSTEM CLOCK

A crystal oscillator should be used as an input on the OSCI pin. This clock is provided for the device as a system clock. The system clock is used as a reference clock for all the internal circuits. The active edge of the system clock can be selected by the OSC_EDGE bit in xo_freq_cnfg register. Eight common oscillator frequencies can be used for the stable Sys- tem Clock. The oscillator frequency can be set by pins or by xo_fre- q_cnfg register as shown in Table 2. An offset from the nominal frequency may be compensated by set- ting the NOMINAL_FREQ_VALUE[23:0] bits. The calibration range is within ±741 ppm. The crystal oscillator should be c hosen accordingly to meet different applications and standard requirements. (See AN-807 Recommended Crystal Oscillators for NetSynchro WAN PLL).

3.3.2 MODES OF OPERATION

3.3.2.1 DCO control modes

Figure 10 and Figure 11 show a high level diagram of the DCO con- trol architecture, it shows the DCO in DPLL2 being controlled, but both DPLL1 and DPLL2 have the same capabili ties, they are identical. The DCO is a phase accumulator running at an internal clock. The DCO is controlled by a digital word that can represent phase offset or frequency offset. In the case of an IEEE 1588 application, the external processor will run the clock recovery servo algorithm and it will generate a phase offset word or a frequency offset word to control the DCO. The DCO control modes can be set by registers DPLL1_operating_- mode_cnfg and DPLL2_operating_mode_cnfg for DPLL1 and DPLL2 respectively. Figure 10 shows the DCO being controlled by writing a frequency off- set word into the DCO, then by changing temporarily the DCO’s fre- quency, the phase of the clock (or 1PPS) being generated by the DCO will also change. The output phase change is the product of the fre- quency change times the duration for which the frequency change is applied for. Because the DCO's frequency word has a very fine resolu- tion, the output phase can be adjusted in very fine steps. In this case the clock recovery servo algorithm controls the bandwidth and phase slope limiting. The frequency offset word can be written into DPLL1_hold- over_freq_cnfg[39:0] bits of frequency configuration registers for DPLL1, and into DPLL2_holdover_freq_cnfg[39:0] bits of frequency configura- tion registers for DPLL2. This valu e is 2’s complement signed number. Total range is +/-92 ppm, and the DCO programming resolution is [(77760 / 1638400) * 2^-48] or ~1.686305041e-10 ppm. The DCO reso- lution is affected by the offset applied into the DCO, so when writing into the DCO, the programming resolu tion is [(77760/1638400) * 2^-48] * (1 + offset-in-ppm / 1e6). Controlling the DCO’s frequency for smaller fine resolution phase changes is a good method, but for bigger phase changes it is better to use the snap-alignment method. T he snap phase alignment is fast but only provides coarse adjustment. The 82P33810 allows for both the fine phase adjustment by controlling the frequency of the DCO and the coarse phase adjustment by snap-ali gn the output clock (or 1PPS), for details, see section 3.3.7.3 Output Phase control on page 40. Figure 11 shows the DCO being controll ed by writing a phase offset word into the DCO, then the clock recovery servo algorithm directly con- trols the DPLL phase, which in turn controls DCO phase with hardware This method allows a better control of the bandwidth of the clock as the bandwidth is controlled in hardware, so it makes it easier to meet and 0.1Hz). The phase offset wo rd can be written into DPLL1_ phase_offset_cnfg[28:0] of phase c onfiguration registers for DPLL1, and into DPLL2_ phase_offset_cnfg[28:0] of phase configuration regis- ters for DPLL2. The update rate needs to be at least 60 times of the loop filter bandwidth, as an example, for 0.1Hz, the update should be >6Hz. This value is 2's complement number, phase programming resolution is 0.0745ps and the total range is +/-20us This mode is enabled by writ- ing the ph_offset_en in those registers. Table 2: Oscillator Frequencies xo_freq[2:0] pins xo_freq_cnfg[2:0] bits Oscillator Frequency (MHz) 000 10.000 001 12.800 010 13.000 011 19.440 100 20.000 101 24.576 110 25.000 111 30.720

3.3.2.2 Disciplined DCO

the disciplined DCO is the same as the SyncE (SONET/SDH) reference. oscillator can be used in the line cards instead of a TCXO or an OCXO. Figure 12. Disciplined DCO mode

3.3.2.3 Combo Mode

1 PPS pulse and the IEEE 1588 slave’s 1 PPS pulse and then align the

SyncE clock and the IEEE 1588 timing are traceable to the same PRTC. based on SSM clock quality level. Figure 13. Combo mode using frequency control

3.3.2.4 DPLL1 and DPLL2 Operating Mode

MODE[4:0] bits respectively. the internal state machine is shown in Table 16. sponding mask bit is set to “1”, the mask bit is set to “0” by default.

00000 Automatic

00001 Forced - Free-Run

00010 Forced - Holdover

00011 Reserved

00100 Forced - Locked

00101 Forced - Pre-Locked2

00110 Forced - Pre-Locked

00111 Forced - Lost-Phase

01010 DCO write frequency

An input clock is selected.
The DPLL selected input clock is disqualified AND No qualified input clock is available.
The DPLL selected input clock is switched to another one.
The DPLL selected input clock is locked (the DPLL_LOCK bit is ‘1’).
The DPLL selected input clock is disqualified AND No qualified input clock is available.
The DPLL selected input clock is unlocked (the DPLL_LOCK bit is ‘0’).
The DPLL selected input clock is locked again (the DPLL_LOCK bit is ‘1’).
The DPLL selected input clock is switched to another one.
The DPLL selected input clock is locked (the DPLL_LOCK bit is ‘1’).
The DPLL selected input clock is disqualified AND No qualified input clock is available.
The DPLL selected input clock is switched to another one.
The DPLL selected input clock is disqualified AND No qualified input clock is available.
An input clock is selected.
The DPLL selected input clock is switched to another one.

3.3.2.4.1 Free-Run Mode

In Free-Run mode, the DPLL1/2 output refers to the system clock and is not affected by any input clock. The accuracy of the DPLL1/2 out- put is equal to that of the system clock.

3.3.2.4.2 Pre-Locked Mode

In Pre-Locked mode, the DPLL1/2 output attempts to track the selected input clock. The Pre-Locked mode is a secondary, temporary mode.

3.3.2.4.3 Locked Mode

In Locked mode, the DPLL1/2 is locked to the input clock. The phase and frequency offset of the DPLL1/2 out put track those of the DPLL1/2 selected input clock. For a closed loop, different bandwidths and damping factors can be used depending on DPLL locking stages: starting, acquisition and locked. In the first two seconds when the DPLL1/2 attempts to lock to the selected input clock, the starting bandwidth and damping factor are used. They are set by the DPLL1/2_START_BW[4:0] bits and the DPLL1/2_START_DAMPING[2:0] bits respectively. During the acquisition, the acquisition bandwidth and damping factor are used. They are set by the DPLL1/2_ACQ_BW[4:0] bits and the DPLL1/2_ACQ_DAMPING[2:0] bits respectively. When the DPLL1/2 is locked, the locked bandwidth and damping fac- tor are used. They are set by the DPLL1/2_LOCKED_BW[4:0] bits and the DPLL1/2_LOCKED_DAMPING[2:0] bits respectively. The corresponding bandwidth and damping factor are used when the DPLL1/2 operates in different locki ng stages: starting, acquisition and locked, as controlled by the device automatically. The locked bandwidth is selectable can be set as shown in Table 4.

3.3.2.4.4 Pre-Locked2 Mode

In Pre-Locked2 mode, the DPLL1/2 output attempts to track the selected input clock. The Pre-Locked2 mode is a secondary, temporary mode.

3.3.2.4.5 Lost-Phase Mode

In Lost-Phase mode, the DPLL1/2 output attempts to track the selected input clock. The Lost-Phase mode is a secondary, temporary mode. Table 4: DPLL1/2 Locked Bandwidth DPLL1/2_LOCKED_BW[4:0] BW Application 00000 0.090 mHz 00001 0.27 mHz 00010 0.90 mHz stratum 3E, BW<1mHz 00011 2.9 mHz G.812 Type I, BW< 3mHz 00100 4.3 mHz 00101 8.7 mHz 00110 17 mHz 00111 35 mHz 01000 69 mHz 01001 92 mHz GR-253 stratum 3, SMC and EEC- option, 2, BW < 0.1Hz 01010 277 mHz 01011 554 mHz 01100 1.1 Hz EEC-option 1, 1< BW <10 GR-1244 stratum 3, BW<3Hz 01101 2.2 Hz EEC-option 1, 1< BW <10 GR-1244 stratum 3, BW<3Hz 01110 4.4 Hz EEC-option 1, 1< BW <10 01111 8.9 Hz EEC-option 1, 1< BW <10 10000 18 Hz 10001 35 Hz 10010 71 Hz 10011 142 Hz 10100 283 Hz 10101 567 Hz 10110-11111 Reserved

3.3.2.4.6 Holdover Mode

In Holdover mode, the DPLL1/2 resorts to the stored frequency data acquired in Locked mode to control its output. The DPLL1/2 output is not phase locked to any input clock. The frequency offset acquiring method is selected by the holdover bit, auto_avg bit, the hist_mode [1:0] bits, and the avg_mode[1:0] bits in DPLL1/2_holdover_mode_cnfg registers as shown in Table 5: The default value for holdover mode is set to current averaged value with holdover filter BW of ~1.5mHz. In this mode the initial frequency off- set is better than 1.1e-5ppm assuming that there is no in-band jitter/wan- der at the input just before enteri ng holdover state. The default mode is used for Telcordia GR-1244, Telcordia GR-253, ITU-T G.8262 and ITU-T G.813 to meet holdover requirements. In Manual Mode, the frequency offset is set by the DPLL1/2_hold- over_freq_cnfg[39:0] bits. The accuracy is1.686305041e-10 ppm, how- ever the resolution is affected by the frequency offset applied, so when writing the frequency offset, t he programming resolution is [(77760/ 1638400) * 2^-48] * (1 + offset-in-ppm / 1e6). The offset value, which is ac quired by the modes shown in Table 5, can be read from the holdover_freq_c nfg[39:0] bits by setting the read_avg bit to “1”. If read_avg bit is set to “0” then the value in hold- over_freq_cnfg[39:0] bits is the val ue written into it. The value is 2’s complement signed number, and the total range is +/- 92 ppm. The holdover frequency resolution is calculated as follows: Holdover Frequency resolution: HO_freq_res = (77760/1638400) * 2^-48 The Holdover value read from register bits holdover_freq_cnfg[[39:0] must be converted to decimal: HO_value_dec = holdover_freq_cnfg[39:0] value in decimal The frequency offset in ppm is calculated as follows: Holdover Frequency Offset (ppm) = (HO_freq_res * HO_value_dec)/ (1-((HO_freq_res * HO_value_dec)/1e6))

3.3.2.4.7 Hitless Reference Switching

Bit hitless_switch_en in DPLL1/2_mon_sw_pbo_cnfg register can be used to set hitless reference switch ing. When a Hitless Switching (HS) event is triggered, the phase offset of the selected input clock with respect to the DPLL1/2 output is measured. The device then automati- cally accounts for the measured phase offset and compensates for the appropriate phase offset into the DPLL output so that the phase tran- sients on the DPLL1/2 output are minimized. The input frequencies should be set to frequencies equal to 8kHz or higher. If hitless_switch_en is set to “1”, a HS event is triggered if any one of the following conditions occurs:

DPLL1/2 selected input clock switches to a different reference
DPLL1/2 exits from Holdover mode or Free-Run mode Table 5: Frequency Offset Control in Holdover Mode man_hold over auto_avg hist_mode [1:0] avg_mode[1 :0] Frequency Offset Acquiring Method 0 don’t-care don’t-care Averaged 0 0 Current averaged value with holdover filter BW of ~0.18mHz 0 1 Current averaged value with holdover filter BW of ~1.5mHz 1 0 Current averaged value with holdover filter BW of ~12mHz 1 1 Current averaged value with holdover filter BW of ~0.15Hz 0 0 Averaged value 1 second before with holdover filter BW of ~0.18mHz 0 1 Averaged value 1 second before with holdover filter BW of ~1.5mHz 1 0 Averaged value 1 second before with holdover filter BW of ~12mHz 1 1 Averaged value 1 second before with holdover filter BW of ~0.15Hz 0 0 Averaged value 8 seconds before with holdover filter BW of ~0.18mHz 0 1 Averaged value 8 seconds before with holdover filter BW of ~1.5mHz 1 0 Averaged value 8 seconds before with holdover filter BW of ~12mHz 1 1 Averaged value 8 seconds before with holdover filter BW of ~0.15Hz 0 0 Averaged value 64 seconds before with holdover filter BW of ~0.18mHz 0 1 Averaged value 64 seconds before with holdover filter BW of ~1.5mHz 1 0 Averaged value 64 seconds before with holdover filter BW of ~12mHz 1 1 Averaged value 64 seconds before with holdover filter BW of ~0.15Hz 1 don’t-care Manual - values is set by DPLL1/2_holdover_freq_cnfg register

3.3.2.4.8 Phase Slope Limit

3.3.2.4.9 Frequency Offset Limit

hard limit (refer to 3.3.4.3 Hard Limit Exceeding on page 36).

3.3.2.5 DPLL3 Operating Mode

write “0” to bit DPLL3_dpll_pdn in pdn_conf register to enable it. Figure 16. DPLL3 Automatic Operating Mode

An input clock is selected.
An input clock is selected.
No input clock is selected.

3.3.2.5.1 Free-Run Mode

equal to that of the system clock.

3.3.2.5.2 Locked Mode

DPLL3 is a wide BW DPLL, with loop bandwidth higher than 25Hz.

3.3.2.5.3 Holdover Mode

value to meet different standards according to this table.

000 Automatic

001 Forced - Free-Run

010 Forced - Holdover

100 Forced - Locked

31©2017 Integrated Device Technology, Inc. 82P33810 Datasheet September 4, 2017 manually set to go into holdover, the initial frequency accuracy is 4.4X10-8 ppm. DPLL3_auto_avg = 1: averaged frequency value is used as holdover frequency. The holdover average bandwid th is about 1.5mHz. In this mode the initial frequency offset is 1.1e-5ppm assuming that there is no in-band jitter/wander at the input just before entering holdover state.

3.3.2.5.4 Frequency Offset Limit

The DPLL3 output is limited to be within the DPLL hard limit (refer to 3.3.4.3 Hard Limit Exceeding on page 36).

3.3.3 INPUT CLOCKS AND FRAME SYNC

The 82P33810 has 14 input clocks that can also be used for frame sync pulses. The 82P33810 supports Telecom and Ethernet frequencies from 1PPS up to 650 MHz. IN1 and IN2 support the AMI input signal only. The input clock is a 64 kHz + 8 kHz or 64 kHz + 8 kHz + 0.4 kHz composite clock. The 400hz_- sel bit should be set to match the input frequency. Any input violation that does not meet the standard composite clock structure will trigger an AMI violation. The AMI violation is indicated by the AMI1_VIOL/ AMI2_VIOLbit, which will trigger an in terrupt on INT_REQ pin if there is an AMI violation and the respective in terrupt mask bit is set. By default the interrupt mask bit is not set. Any of the input clocks can be used as a frame pulse or sync signal. The SYNC_sel[3:0] bits in INn_los_sync_cnfg (14 < n < 1) registers sets which pin is used as frame pulse or sync signal. IN3 to IN14 can be used for 2 kHz, 4 kHz or 8 kHz frame pulses or 1PPS sync signal.The input frequency should match the setting in the sync_freq[1:0] bits in DPLL1/2_input_mode_cnfg register.

3.3.3.1 Input Clock Pre-divider

Each input clock is assigned an inte rnal Pre-divider. The Pre-divider can be used to divide the clock frequency down to a convenient fre- quency, such as 8 kHz for the internal DPLL1 and DPLL2. Note that T1 and E1 references can exhibit substantial jitter with frequencies above 4 kHz. These references should be applied to DPLL1 or DPLL2 without being divided down to 8 kHz. For IN1 and IN2, the DPLL required frequency is fixed to 8 kHz (i.e., the corresponding IN_FREQ[3:0] bits are ‘0000’). The 8 kHz clock is extracted from the composite cloc k and the Pre-divider is bypassed automatically. For IN3 ~ IN14, the DPLL required frequency is set by the corre- sponding IN_FREQ[3:0] bits. Table 8: IN_FREQ[3:0] DPLL Frequency IN_FREQ[3:0] Bits DPLL Frequency 0000 8 kHz 0001 1.544 MHz / 2.048 MHz (depends on SONET/ SDH bit) 0010 6.48 MHz 0011–1000 Reserved 1001 2 kHz 1010 4 kHz 1011 1 PPS 1100 6.25 MHz 1101–1111 Reserved

32©2017 Integrated Device Technology, Inc. Each Pre-divider consists of an FEC divider and a DivN divider,. block diagram of the pre-dividers for an input clock. FREQ[3:0] bits should be set to match the input frequency. also associated with another reference input used as SYNC.

Write the lower eight bits of the division factor to the
Write the higher eight bits of the division factor to the

Figure 17. Pre-divider for an input clock

3.3.3.2 Input Clock Quality Monitoring

LOS (loss of signal) (only for IN1 and IN2)
Activity
Frequency LOS monitoring is only conducted on IN1 and IN2. Activity and fre- quency monitoring are conducted on all the input clocks. The qualified clocks are available for selection for all 3 DPLLs.

3.3.3.2.1 Loss of Signal (LOS) Monitoring

when the amplitude rises higher than +1 Vp-p.

3.3.3.2.2 Activity Monitoring

Each input clock is assigned an internal leaky bucket accumulator. with respect to the system clock within a 128 ms period. There are four configurations (0 - 3) for a leaky bucket accumulator. INn_NO_ACTIVITY_ALARM bit (14  n  1). Figure 18. Input Clock Activity Monitoring

3.3.3.2.3 Frequency Monitoring

the output of DPLL1, as determined by the FREQ_MON_CLK bit. Accepting Threshold and Soft Alarm Rejecting Threshold. (14  n  1) in the same way as hard alarm.

Read the value in the IN_FREQ_VALUE[7:0] bits and calculate

Figure 19. Hysteresis Frequency Monitoring

3.3.3.3 Input Clock Selection

0000 Automatic selection

1111 Reserved

3.3.3.3.1 Forced Selection

clock selection if Forced selection is used.

3.3.3.3.2 Automatic Selection

monitoring (refer to 3.3.3.2 Input Clock Quality Monitoring on page 33 ). Figure 20. Qualified Input Clocks for Automatic Selection the input clock to be valid; otherwise, it is invalid.

No LOS (the AMI1_LOS / AMI2_LOS bit is ‘0’);
No no-activity alarm (the INn_NO_ACTIVITY_ALARM bit is ‘0’);
No frequency hard alarm (the INn_FREQ_HARD_ALARM bit is ‘0’);
No phase lock alarm, i.e., the INn_PH_LOCK_ALARM bit is ‘0’;
If the ULTR_FAST_SW bit is ‘1’, the DPLL selected input clock misses less than (<) 2 consecutive clock cycles; if the ULTR_- FAST_SW bit is ‘0’, this condition is ignored;
LOS[3:0] are not set to disqualify the input clock For DPLL3, the following conditions must be satisfied for the input clock to be valid; otherwise, it is invalid.
No LOS (the AMI1_LOS / AMI2_LOS bit is ‘0’);
No no-activity alarm (the INn_NO_ACTIVITY_ALARM bit is ‘0’);
No frequency hard alarm (the INn_FREQ_HARD_ALARM bit is ‘0’);
LOS[3:0] are not set to disqualify the input clock The INn bit (14  n  1) indicates whether or not the clock is valid. When the input clock changes from ‘valid’ to ‘invalid’, or from ‘invalid’ to ‘valid), the INn bit will be set. If the INn bit is ‘1’, an interrupt will be gen- erated. When the DPLL selected input clock has failed, i.e., the selected input clock changes from ‘valid’ to ‘invalid’, the DPLL_MAIN_REF_- FAILED bit will be set. If the DPLL_MAIN_REF_FAILED bit is ‘1’, an interrupt will be generated. For DPLL1 and DPLL2, Revertive and Non-Revertive switchings are supported, as selected by the REVERTIVE_MODE bit. For DPLL3, only Revertive switching is supported. GR-1244 defines Revertive and Non- Revertive Reference switching. In Non-Revertive switching, a switch to an alternate reference is main- tained even after the original refer ence has recovered from the failure that caused the switch. In Revertive switching, the clock switches back to the original reference after that reference recovers from the failure, independent of the condition of the alternate reference. In Non-Revertive switching, input clock switch is minimized. In Revertive switching, the sele cted input clock is switched when another qualified input clock with a higher priority than the current selected input clock is available. Therefore, if REVERTIVE_MODE bit is set to “1”, then the selected input clock is switched if any of the following is satisfied:
the selected input clock is disqualified;
another qualified input clock with a higher priority than the selected input clock is available. Input Clock Validation Pri ori ty INn_SEL_PRIORITY[3:0] '0000' Input configuration IN n_VALID = '0' Yes No No No Yes Yes All qualified input clocks are available for Automatic selection Input Clock Quality Monitoring (LOS, Activity, Frequency) IN n = '1'

36©2017 Integrated Device Technology, Inc. 82P33810 Datasheet September 4, 2017 A qualified input clock with the highest priority is selected by revertive switching. If more than one qualified input clock INn is available, then it is important to set appropriate priori ties to the input clocks, two input clocks must not have the same priority. In Non-Revertive switching, the DPLL1/2 selected input clock is not switched when another qualified input clock with a higher priority than the current selected input clock becom es available. In this case, the selected input clock is switched and a qualified input clock with the high- est priority is selected only when the DPLL1/2 selected input clock is dis- qualified. If more than one qualified input clock INn is available, then it is important to set appropriate prioriti es to the input clocks, two input clocks must not have the same priority.

3.3.3.3.3 Selected / Qualified Input Clocks Indication

The selected input clock is indi cated by the CURRENTLY_SELECT- ED_INPUT[3:0] bits. When the device is configured in Automatic selection and Revertive switching is enabled, the input clock indicated by the CURRENTLY_SE- LECTED_INPUT[3:0] bits is the same as the one indicated by the HIGH- EST_PRIORITY_VALIDATED[3:0] bits.

3.3.3.3.4 Input Clock Loss of Signal

There are 4 LOS input pins (LOS[3:0 ]) that can be used to disqualify the input clock. If they are set high, then the associated input clock is disqualified to be used as an input clock, and therefore the DPLLs will not lock to that particular input clock. The 4 LOS pins can be associated with any input clock by setting bits LOS_EN in INn_LOS_SYNC_CNFG (1< n<14) register. By default, the LOS pins are not associated with any input.

3.3.4 DPLL LOCKING PROCESS

The following events are always monitored for the DPLLs locking process:

Fast Loss;
Fine Phase Loss;
Hard Limit Exceeding. For proper operation, COARSE_PH_LOS_LIMT_EN must be set to

3.3.4.1 Fast Loss

A fast loss is triggered when the selected input clock misses 3 con- secutive clock cycles. It is cleared once an active clock edge is detected. For all DPLL1 and DPLL2 the occurrence of the fast loss will result in the DPLL to unlock if the FAST_LOS_SW bit is ‘1’. For DPLL3, the occurrence of the fast loss will result in the DPLL to unlock regardless of the FAST_LOS_SW bit.

3.3.4.2 Fine Phase Loss

The DPLL compares the selected input clock with the feedback sig- nal. If the phase-compared result exceeds the fine phase limit pro- grammed by the PH_LOS_FINE_LIMT[2:0] bits, a fine phase loss is triggered. It is cleared once the phase-co mpared result is within the fine phase limit. For greatest jitter and wander tolerance, set the PH_LOS_FINE_LIMT[2:0] to the largest value. The occurrence of the fine phase loss will result in DPLL to unlock if the FINE_PH_LOS_LIMT_EN bit is ‘1’.

3.3.4.3 Hard Limit Exceeding

Two limits are available for this monitoring. They are DPLL soft limit and DPLL hard limit. When the frequency of the DPLL output with respect to the system clock exceeds the DPLL soft / hard limit, a DPLL soft / hard alarm will be raised; the alarm is cleared once the frequency is within the corresponding limit. T he occurrence of the DPLL soft alarm does not affect the DPLL locking st atus. The DPLL soft alarm is indi- cated by the corresponding DPLL_SOFT_FREQ_ALARM bit. The occurrence of the DPLL hard alarm will result in the DPLL to unlock if the FREQ_LIMT_PH_LOS bit is ‘1’. The DPLL soft limit is set by the DPLL_FREQ_SOFT_LIMT[6:0] bits and can be calculated as follows: DPLL Soft Limit (ppm) = DPLL_FREQ_SOFT_LIMT[6:0] X 0.724 The DPLL hard limit is set by the DPLL_FREQ_HARD_LIMT[15:0] bits and can be calculated as follows: DPLL Hard Limit (ppm) = DPLL_FREQ_HARD_LIMT[15:0] X 0.0014

3.3.4.4 Locking Status

The DPLL locking status depends on the locking monitoring results. The DPLL is in locked state if none of the following events is triggered during 2 seconds; otherwise, the DPLL is unlocked.

Fast Loss (the FAST_LOS_SW bit is ‘1’);
Fine Phase Loss (the FINE_PH_LOS_LIMT_EN bit is ‘1’);
DPLL Hard Alarm (the FREQ_LIMT_PH_LOS bit is ‘1’). If the FAST_LOS_SW bit, the COARSE_PH_LOS_LIMT_EN bit, the FINE_PH_LOS_LIMT_EN bit or the FR EQ_LIMT_PH_LOS bit is ‘0’, the DPLL locking status will not be affected even if the corresponding event is triggered. If all these bits are ‘0’, the DPLL will be in locked state in 2 seconds. The DPLL locking status is indicated by the corresponding DPLL_LOCK bits and by the DPLL_LOCK pins.

3.3.4.5 Phase Lock Alarm

DPLL1 and DPLL2 have a phase lock alarm that will be raised when the selected input clock can not be locked in DPLL1/2 within a certain period. This period can be calculated as follows: Period (sec.) = TIME_OUT_VALUE[5:0] X MULTI_FACTOR[1:0] The phase lock alarm is indicated by the corresponding INn_PH_LOCK_ALARM bit (14  n  1). The phase lock alarm can be cleared, as selected by the PH_ALARM_TIMEOUT bit:

It is cleared when a ‘1’ is written to the corresponding INn_PH_LOCK_ALARM bit;
It is cleared after the period ( = TIME_OUT_VALUE[5:0] X MUL- TI_FACTOR[1:0] in second ) starting from the time the alarm is raised. The selected input clock with a phas e lock alarm is disqualified for the DPLL1 and DPLL2 to lock. Note that phase lock alarm is not available for DPLL3.

3.3.5 APLL1 AND APLL2

APLL1 and APLL2 are provided for a better jitter and wander perfor- mance of the device output clocks.The bandwidth for APLL1 and APLL2 is internally set to 22 kHz (typical). The input of both APLLs can be derived from one of the DPLL1 or DPLL2 outputs, as selected by the apll1_path_freq_cnfg[2:0] and apll2_path_freq_cnfg[2:0] bits respectively as shown in Table 10. To following steps should be followed to set APLL1/APLL2 output to Ethernet LAN PHY frequencies. To initialize the device, write into the following registers: 1. Write 0x04F4F0 to bits apll1 /apll2_divn_frac_cnfg[20:0] of APLL1/APLL2 fractional feedback di vider configuration register to set the fractional part of feedback divider for APLL1/APLL2 2. Write 0x0051 to bits apll1/apll2_divn_den_cnfg[15:0] of APLL1/ APLL2 divisor denominator configur ation register to set the denominator part of feedback divider for APLL1/APLL2 3. Write 0x0010 to bits apll1 /apll2_divisor_num_cnfg[15:0] of APLL1/APLL2 divisor numerator confi guration register to set the numerator part of feedback divider for APLL1/APLL2 4. Write 0x21 to bits apll1/apll2_divisor_int_cnfg[5:0] of APLL1/ APLL2 divisor integer configuration register to set the integer part of feedback divider for APLL1/APLL2 5. Write 0x13356218 to bits apll1/apll2_fr_ratio_cnfg[28:0] of APLL1/APLL2 feedback divider configur ation register to set the feedback divider for APLL1/APLL2 After the device has been initialized according to the steps above, follow the following steps when setting APLL1/APLL2 path to 644.53125 MHz:

Write 1’b1 to dsm_cnfg_en bit to enable the preset programma- ble feedback divider of APLL1/APLL2 configuration register
Write the corresponding value in the apll1/apll2_path_fre- q_cnfg[2:0] bits according to Table 10. After the device has been initialized according to the steps 1 to 5 above, follow the following steps when setting APLL1/APLL2 path to 625MHz: or 622.08MHz
Write 1’b0 to dsm_cnfg_en bit to disable the preset programma- ble feedback divider of APLL1/APLL2 configuration register
Write the corresponding value in the apll1/apll2_path_fre- q_cnfg[2:0] bits according to Table 10. Table 10: APLL1/2 input selection apll1/apll2_path_freq_cnfg[2:0] APLL1/2 Input Selection 000 622.08 MHz from DPLL1 001 625 MHz from DPLL1 010 644.53125 MHz from DPLL1

011 Reserved

100 622.08 MHz from DPLL2 101 625 MHz from DPLL2 110 644.53125 MHz from DPLL2

3.3.6 OUTPUT CLOCKS & FRAME SYNC SIGNALS

3.3.6.1 Output Clocks

OUT2 ~ OUT4 can be derived from APLL1. OUT5 ~ OUT7 can be derived from APLL2. OUT1 to OUT8 have an output divi der associated with each output. can be programmed by writing into OUTn_DIV2_CNFG[26:0]. Figure 21. OUT1 and OUT8 output dividers Figure 22. OUT2 to OUT7 output dividers

To set the feedback divider, program dpll3_fb_div_cnfg[13:0] bits of DPLL3 feedback divider register
To set the fractional divider, pr ogram dpll3_divn_frac_cnfg[23:0] of DPLL3 fractional divider register
To set the denominator of t he fractional divider, program dpll3_divn_den_cnfg[15:0] bits of DPLL3 fractional divider denominator register
To set the numerator of t he fractional divider, program dpll3_divn_num_cnfg[15:0] bits of DPLL3 fractional divider numerator register
To set the integer divider, program dpll3_int_cnfg[7:0]bits of DPLL3 integer divider register Output DividerOutput Divider APLL1/ APLL2 DPLL1 Output Div1 (OUT1_DIV1_CNFG[4:0] (OUT8_DIV1_CNFG[4:0]) OUT1_MUX_CNFG[3:0] OUT8_MUX_CNFG[3:0] Output Div2 (OUT1_DIV2_CNFG[26:0] (OUT8_DIV2_CNFG[26:0]) DPLL2 OUT1 OUT8 APLL_PATH Output Dividers APLL1 APLL2 DPLL1 Output Div1 (OUTn_DIV1_CNFG[4:0] 2<n<4 (from APLL1) 5<n<7 (from APLL2) Output Div2 (OUTn_DIV2_CNFG[26:0] 2<n<4 (from APLL1) 5<n<7 (from APLL2) DPLL2 APLL_PATH 2<n<4 (from APLL1) 5<n<7 (from APLL2)OUTn Phase 1 Phase 2

39©2017 Integrated Device Technology, Inc. 82P33810 Datasheet September 4, 2017 OUT1 to OUT11 output clocks can be inverted by setting OUTn_IN- VERT bit (0: output not inverted, 1: output inverted) in OUTn_MUX- _CNFG register for (1 < n < 8) for OUT1 ~ OUT8, in OUT9_FREQ_CNFG register fo r OUT9, and in OUT10_CNFG and OUT11_CNFG registers for OUT10 and OUT11 respectively. The output clocks can be squelched by setting OUT- n_SQUELCH[1:0] bits (0x: no squelch, 10: squelch to '0', 11: squelch to '1') in OUTn_MUX_CNFG register for (1 < n < 8), and in OUT10_CNFG and OUT11_CNFG registers for OUT1 to OUT8, and OUT10 and OUT11 respectively. OUT1 to OUT8 output clocks c an be individually powered down by setting OUTn_PDN bit to '1' in OUT n_MUX_CNFG register for (1 < n < OUT9 can be enabled or disabl ed by programming OUT9_PDN and DPLL3_INPUT_FAIL bits in OUT9_FREQ_CNFG register. 82P33810 provides a variety of output frequencies from 1Hz to 650MHz. APLL1 is always enabled and the default frequency for OUT1, OUT2, and OUT3 is respectively 25 MH z, 125 MHz, and 156.25MHz. OUT4 is squelched by default. By default, OUT5 to OUT8 are squelched. Set the proper registers to set desired frequency values for OUT5 to OUT8. OUT9 is powered down by default. DPLL3 is disabled by default, and if it is enabled, then the default fre- quency for OUT10 and OUT11 is respectively 16.384 MHz and 2.048 MHz. APLL1, APLL2, and the DPLLs can be configured from an external EEPROM after reset. It can be used to set specific start up frequency values as needed by the application.

3.3.6.2 Frame Sync Signals

Either an 8 kHz or a 2 kHz frame sync, or a 1PPS sync signal are output on the FRSYNC_8K_1PPS and MFRSYNC_2K_1PPS pins if enabled by the 8K_1PPS_EN and 2K_1PPS EN bits respectively. They are CMOS outputs. The output sync frequencies are independent of the input sync fre- quency. The output FRSYNC_8K_1PPS and MFRSYNC_2K_1PPS fre- quencies are selected through the dpll1/2_fr_mfr_sync_cnfg registers. Any supported clock frequency at t he clock input can be associated with the sync signals. The frame sync output signals are derived from the DPLL1 and DPLL2 output and are aligned with the output clock. They are synchro- nized to the frame sync input signa l. In DCO control modes (section 3.3.2.1), the output FRSYNC_8K_1PPS and MFRSYNC_2K_1PPS must not be used, a 1PPS output sync signal can be generated in any of the output clocks connected to the DCO being used. The frame sync output signals are derived from the DPLL1 and DPLL2 output and are aligned with the output clock. They are synchro- nized to the frame sync input signal. The frame/sync output signals ali gn to the first edge of the associ- ated reference clock that occurs after the edge of the frame/sync input signal. The frequency of the associated reference clock must be lower or equal to the frequencies of the output clocks that requires to be aligned with the frame/sync pulse signal. If the frame sync input signal with respect to the DPLL1/2 selected input clock is above a limit set by the SYNC_MON_LIMT[2:0] bits, an external sync alarm will be raised and the frame/sync input signal is dis- abled to synchronize the frame/sync output signals. The external sync alarm is cleared once the frame/sync input signal with respect to the DPLL selected input clock is within the limit. If it is within the limit, whether frame/sync input signal is enabled to synchronize the frame sync output signal is determined by the AUTO_EXT_SYNC_EN bit and the EXT_SYNC_EN bit. When the frame/sync input signal is enabled to synchronize the frame/sync output signal, it is adjus ted to align itself with the DPLL selected input clock. By default, the falling edge of the fr ame/sync input signal is aligned with the rising edge of the DPLL1/2 selected input clock. The rising edge of frame/sync input signal can be set to be aligned with the rising edge of the DPLL1/2 selected input clock by setting sync_edge bit to “1” in DPLL1/2_sync_edge_cnfg register. The EX_SYNC_ALARM_MON bit i ndicates whether frame/sync input signal is in external sync alar m status. The external sync alarm is indicated by the EX_SYNC_ALARM bit. If the EX_SYNC_ALARM bit is ‘1’, the occurrence of the external sync alarm will trigger an interrupt. The 8 kHz frame pulse, the 2 kHz frame pulse, and the 1PPS sync signal can be inverted by setting the 8K_1PPS_INV and 2K_1PPS_INV bits of Frame Sync and Multiframe Sync Output Configuration Register. The 8 kHz and the 2 kHz frame sync outputs can be 50:50 duty cycle or pulsed, as determined by the 8K_P UL and 2K_PUL bits respectively. When they are pulsed, the pulse width derived from DPLL1 is defined by the period of OUT1, and the pulse wi dth derived from DPLL2 is defined by the period of OUT8. They are pul sed on the position of the falling or rising edge of the standard 50:50 duty cycle, as selected by the 2K_8K_PUL_POSITION bit of Frame Sync and Multiframe Sync Output Configuration Register.

3.3.7 INPUT AND OUTPUT PHASE CONTROL

The device has several features to allow a tight control of the phase on the input and output clocks.

3.3.7.1 DPLL1 and DPLL2 Phase offset control

The phase offset of the DPLL1/2 selected input clock with respect to the DPLL1/2 output can be adjusted. If the device is configured as the active PLL in a redundancy system, then the PH_OFFSET_EN bit deter- mines whether the input-to-output phas e offset is enabled. If the device is configured as the inactive P LL in a redundancy system, then the input-to-output phase offset is al ways enabled. If enabled, the input-to- output phase offset can be adjusted by setting the PH_OFF- SET_CNFG[28:0] bits in DPLL1/2 phas e offset configuration register. The register value is a 2's complement phase offset with a resolution of 0.0745ps and a total range of [20us, - 20us]. The input-to-output phase offset can be calculated as follows: Phase Offset (ps) = PH_OFFSET[28:0] X 0.0745

3.3.7.2 Input Phase control

All the inputs phase can be controll ed individually. They can be pro- grammed with a resolution of 0.61 ns and a range of [77.5 ns,-78.1ns] by setting INn_PHASE_OFFSET_CNFG[7:0] bits (3 < n < 14) in the input phase offset configuration register. T he register value is a 2's comple- ment phase offset, the default is ze ro. The programmed offset is auto- matically applied to the DPLL1 and DPLL2 when a particular input is selected. If the manual DPLL1 and DPLL2 phase offset control is used then the per-input phase offset is not applied.

3.3.7.3 Output Phase control

The output phase can be controlled individually for outputs OUT1 to OUT8. There is the coarse phase control that allows the output phase to be adjusted as low as 1.6ns. There is a fine phase adjustment that allows the output phase to be adjusted as low as 187.27 ps. The total range is +/-180 There are two register s associated with the coarse phase adjust- ment, the OUTn_PH1_CNFG (1 < n < 8) and the OUTn_PH2_CNFG (1 < n < 8) registers. The OUTn_PH1_C NFG register is associated with output divider 1 as shown in Figure 21 and Figure 22, the phase can be adjusted by a step size that is equal to the period of the input of clock of the output Div1, the number set in the OUTn_PH1_CNFG register should not be larger than the number set in OUTn_DIV1_CNFG register. The OUTn_PH2_CNFG register is as sociated with output divider 2 as shown in Figure 21 and Figure 22, the phase can be adjusted by a step size that is equal to the period of the input of clock of the output Div2, the number set in the OUTn_PH2_CNFG r egister should not be larger than the number set in OUTn_DIV2_CNFG register. There is a register that is asso ciated with the fine phase adjustment, the OUTn_FINE_CNFG (1 < n < 8). For the fine phase adjustment, the output clocks must be output from the APLLs, The phase can be adjusted by a step size that is equal to the 1/2 of the period of the VCO. For Ethernet clocks the VCO frequenc y is 2.5GHz, for Ethernet LAN PHY the VCO frequency is 2.578125 GHz, and for SONET/SDH clocks the VCO frequency is 2.48832 GHz. OUT1 can be output from the DPLLs, and in that case the fine phase adjustment is not available, it is only available if the clocks are output from the APLLs. The output phase adjustments are not available for OUT9, OUT10, and OUT11

3.3.8 TIME OF DAY COUNTER

The device has 2 time accumulators that keeps track of the local Time of Day (ToD). The time accu mulators are associated with DPLL1 and DPLL2. The time accumulator runs on the 77.76 MHz clock that is generated by the DCO1/2. By using t he DCO clock, the Time of Day tracks the input clock or packet stream that the DPLL is locked to and is also synchronized to the output clocks and the output 1 PPS signal gen- erated from the same DPLL. In order to synchronize the device Ti me of Day with the Time of Day in the IEEE 1588 server, the devic e has several triggers available. These can be used to select on which trigger the time accumulator can be synchronized to a pre-programmed va lue. An internal timer allows to update and sample the Time of Day at fixed intervals timed on the local oscillator. The time accumulator records the Ti me of Day in PTP format: 48-bit seconds, and 32-bit ns.

4 POWER SUPPLY FILTERING TECHNIQUES

core logic as well as I/O driver circuits. Figure 23. 82P33810 Power Decoupling Scheme

5 MICROPROCESS OR INTERFACE

registers in the device. The microprocessor interface supports I2C.

5.1 I2C SLAVE MODE

5.1.1 I2C DEVICE ADDRESS

address is set by pins I2C_AD2, I2C_AD1, and I2C_AD0.

5.1.2 I2C BUS TIMING

Figure 24 shows the definition of I2C bus timing. Figure 24. Definition of I2C Bus Timing

43©2017 Integrated Device Technology, Inc. 82P33810 Datasheet September 4, 2017 Table 11: Timing Definition for Standard Mode and Fast Mode(1) Symbol Parameter Standard Mode Fast Mode Unit Min Max Min Max SCL Serial clock frequency 0 100 0 400 kHz tHD; STA Hold time (repeated) START condition. After this period, the first clock pulse is generated 4.0 - 0.5 - s tLOW LOW period of the SCL clock 4.7 - 1.3 - s tHIGH HIGH period of the SCL clock 4.0 - 0.6 - s tSU; STA Set-up time for a repeated START condition 4.7 - 0.6 - s tHD; DAT Data hold time: for CBUS compatible masters for I 2C-bus devices 5.0 0(2) 3.45(3) 0(2) 0.9(3) s tSU; DAT Data set-up time 250 - 100(4) -n s tr Rise time of both SDA and SCL signals - 1000 20 + 0.1Cb(5) 300 ns tf Fall time of both SDA and SCL signals - 300 20 + 0.1Cb(5) 300 ns tSU; STO Set-up time for STOP condition 4.0 - 0.6 - s tBUF Bus free time between a STOP and START condition 4.7 - 1.3 - s Cb Capacitive load for each bus line - 400 - 400 pF VnL Noise margin at the LOW level for each connected device (Including hysteresis) 0.1VDD - 0.1VDD - V VnH Noise margin at the HIGH level for each connected device (Including hysteresis) 0.2VDD - 0.2VDD - V tsp Pulse width of spikes which must be suppressed by the input filter 05 005 0 n s Note: 1. All values referred to VIHmin and VILmax levels (see Table 23) 2. A device must Internally provide a hold time of at least 300 ns for the SDA signal (referred to the VIHmin of the SCL signal) to bridge the undefined region of the fall- ing edge of SCL. 3. The maximum tHD; DAT has only to be met if the device does not stretch the LOW period (tLOW) of the SCL signal. 4. A Fast-mode I2C-bus device can be used in a Standard-mode I2C-bus system, but the requirement tSU; DAT ≥ 250 ns must then be met. This will automatically be the case if the device does not stretch the LOW period of the SCL signal. If such a device does stretch the LOW period of the SCL signal, it must output the next data bit to the SDA line trmax + tSU; DAT = 1000 + 250 = 1250 ns (according to the Standard-mode I2C-bus specification) before the SCL line is released. 5. Cb = total capacitance of one bus line in pF. If mixed with Hs-mode device, faster fall-times according to Table 24 allowed. n/a = not applicable

5.1.3 SUPPORTED TRANSACTIONS

The supported types of transactions are shown below. Figure 25. I2C Slave Interface Supported Transactions reads and writes can be performed anywhere within that page. ing should be continuous and not be interrupted by any operation.

5.2 I2C MASTER MODE

EEPROM reading process is completed.

8 kbit (1023 x 8) I2C EEPROM with device address 1010000 (for the base block)
Sequential read (block read) of t he entire memory-map for device, from byte-address 0x000 to 0x39E
7-bit device address mode
Validation of the EEPROM read data via CCITT-8 CRC check against value stored in memory-map address 0x39E
Support for 100kHz and 400kHz operation with speed programma- bility. If bit 7 is set at memory-map address 0x001, the 82P33810 will shift from 100kHz operation to 400kHz operation.
2-byte word-addressing (1-byte word addressing is supported by offsetting the memory-map upwards 1 address in the EEPROM)
Read will abort with an alarm (RD_EEPROM_ERR interrupt status set) if any of the following conditions occur: Slave NACK, CRC fail- ure, Slave Response time-out Table 12: Description of I2C Slave Interface Supported Transactions Operation Description Current Read Reads a burst of data from an internal determined starting address, this starting address is equal to the last address accessed during the last read or write operation, incremented by one. If the address exceeds the address space, it will start from 0 again. Sequential Read Reads a burst of data from a specified address space. The starting address of the space is specified as offset a ddress. Sequential Write Writes a burst of data to a specified address space, the starting address of the space is specified as offset address. Current Read S Dev Addr + R A Data 0 A Data 1 A A Data n A P Sequential Read S Dev Addr + W A Data 0 A Data 1 A A Data n A PSr Dev Addr + R A Sequential Write S Dev Addr + W A Data 0 PA Data 1 A A Data n A from master to slave from slave to master S = start Sr= repeated start A = acknowledge A = not acknowledge P=s t o p Offset Addr A Offset Addr A

No support for Multi-master
No support for Slave clock stretching
No support for I2C Start Byte protocol
No support for EEPROM Chaining
No support for Writing to external I2C devices including the EEPROM used for booting

5.2.1 I2C BOOT-UP INITIALIZATION MODE

EEPROM mode is enabled via setting the MPU_MODE[1:0] pins high (through two separate pull-up resistors).Once the RSTB input has been asserted (low) and then de-asserted (high) and the device internal calibration has been completed, the 82P33810 will perform a short block read at 100 kHz to program the EEPROM read speed (100 kHz or 400 kHz). The 82P33810 will then perform a block read to program all the device configuration registers, and check the CRC of the EEPROM data. During the boot-up EEPROM-reading process, the 82P33810 will not respond to microprocessor serial control port accesses. Once the initialization process is completed, the contents of any of the device configuration registers can be further altered by the microprocessor, if desired. The 82P33810 can work with EEPR OMs supporting 2-byte word- addresses or 1-byte word-addresses by using 2-byte word addressing for both. This works in the us ual manner for EEPROMs supporting 2- byte word addresses, and gives an address-to-address match between EEPROM and memory-map. For EEPROMs supporting only 1-byte word addresses, the second address byte will cause an addition incre- ment of the address counter, and the memory-map will be read at the next highest EEPROM address,.i.e memory-map (CSR) address 0x00 will be read from EEPROM address 0x01, and memory map address 0x39E will be read from EEPROM address 0x39F. If a NACK is received to any of the read cycles performed by the 82P33810 during the initialization process, or if the CRC does not match the one stored in memory-map addres s 0x39E, the boot process will be restarted. This restart can happen up to three times before an abort is declared and the RD_EEPROM_ERR interr upt status bit is set. Also on RD_EEPROM_ERR the MPU_MODE1/ I2CM_SCL and MPU_MODE0/ I2CM_SDA pins are both held low until the interrupt status bit is cleared or the device is reset. The sugges ted method for dealing with RD_EE- PROM_ERR is to externally set the MPU_MODE[1:0] pins to 00 and then reset the 82P33810 so that it will boot into I2C serial port mode. After a successful EEPROM boot, the 82P33810 will stop toggling the MPU_MODE1/ I2CM_SCL and MPU_MODE0/I2CM_SDA pins, returning them to static high values, and the RD_EEPROM_DONE inter- rupt status bit will be set. The I2C serial port will now respond to micro- processor reads and writes to the appropriate I2C device address.

5.2.2 EEPROM MEMORY MAP NOTES

The EEPROM memory-map is the same as the control and status register (CSR) map with the following additions and constraints: 1. For EEPROMs supporting 2-byte word-address, the memory-map addresses are the same as the EPPROM addresses; for EEPROMs supporting 1-byte word-address, the memory-map addresses will by mapped to the next address in the EEPROM, i.e. memory-map address 0x00 will be read from EEPROM address 0x01, and memory-map address 0x39E will be read from EEPROM address 0x39F. 2. Memory-map address 0x001, bit 7 is the EEPROM read speed (0 for 100 kps, 1 for 400 kbps) 3. Memory-map address 0x39E is the CRC-8 of the memory-map from 0x000 to 0x39D (the standard CC ITT CRC-8 with the data width and result width being 8; the polynomial is (0, 1, 2, 8) or “0x07”). NB: all memory-map addresses from 0x000 to 0x39d are included in the sequential calculation of CRC, including those not used in the CSR - it is recommend that data at unused addresses be set to 0x00. 4. Memory-map addresses 0x392 to 0x39D must be set to the default values shown in the CSR documentation. 5. The device address at memo ry-map address 0x00f must match the address set by the board. 6. Each memory-map address that is a multiple of 0x7F must contain the pointer to the next page of the CSR i.e 0x07f 0x01 0x0ff 0x02 0x17f 0x03 0x1ff 0x04 0x27f 0x05 0x2ff 0x06 0x37f 0x07

5.3 SERIAL MODE

In a read operation, the active edge of SCLK is selected by CLKE. clocked out on the falling edge of SCLK. Figure 26. Serial Read Timing Diagram (CLKE Asserted Low) Figure 27. Serial Read Timing Diagram (CLKE Asserted High)

5.4 UART MODE

Figure 29. UART Data Frame the baud_limit_cnfg register is pr ogrammed with the value (N - M). goes idle, so it is recommended that all 4 bytes be written in one burst.

Sample Clock Rate = 16 * 9600 = 153 600 Hz
Sample Clock Rate = 77.76 MHz * 4/2025 = 153 600 Hz
baud_freq_cnfg = 4 = x004
baud_limit_cnfg = 2025 - 4 = 2021 = x07E5 115 200 baud
Sample Clock Rate = 16 * 115 200 = 1 843 200 Hz
Sample Clock Rate = 77.76 MHz * 16/675 = 1 843 200 Hz
baud_freq_cnfg = 16 = x010
baud_limit_cnfg = 675 - 16 = 659 = x293 Reads and writes of the 82P33810 control and status registers are performed through a multi-frame/byte binary protocol, which is more effi- cient than a character-oriented (hyper -terminal) protocol. The UART will auto-increment the internal address to support burst reads and writes for even higher efficiency.

5.4.1 PROTOCOL

optionally acknowledged on completion. The format of the command byte is given in. ter at the top of the register page (address 127 / x3F). leave out the High Address byte. Set to 0 to enable address auto increment. Set to 1 to disable address auto increment. Set to 1 to send ACK byte at command completion.

The output boundary scan cells do not capture data from the core and the device does not support EXTEST instruction; The JTAG interface timing diagram is shown in Figure - 30.

Figure 30. JTAG Interface Timing Diagram

7 THERMAL MANAGEMENT

The device operates over the industry temperature range -40°C ~ +85°C. To ensure the functionality and reliability of the device, the maxi- mum junction temperature T jmax should not exceed 125°C. In some applications, the device will consume more power and a thermal solution should be provided to ensure the junction temperature T j does not exceed the Tjmax.

7.1 JUNCTION TEMPERATURE

Junction temperature Tj is the temperature of package typically at the geographical center of the chip where the device's electrical circuits are. It can be calculated as follows: Equation 1: Tj = TA + P X JA Where: JA = Junction-to-Ambient Thermal Resistance of the Package Tj = Junction Temperature TA = Ambient Temperature P = Device Power Consumption In order to calculate juncti on temperature, an appropriate JA must be used. The JA is shown in Table 17: has the thermal results based on JEDEC standard conditions. It is industry practice and IDT practice to publish these results. If the PCB design differs from t he JEDEC standard conditions, then the thermal results will be different.

7.2 THERMAL RELEASE PATH

In order to maximize both the removal of heat from the package, electrical grounding from the package to the board can be done through thermal vias to effectively conduct fr om the surface of the PCB to the ground plane(s). The vias act as “heat pipes”. The number of vias (i.e. “heat pipes”) are application specific and dependent upon the package power dissipation as well as electric al conductivity requirements. Thus, thermal and electrical analysis and/or testing are recommended to determine the minimum number needed. It is recommended to use as many vias connected to ground as possible. It is also recommended that the via diameter should be 12 to 13mils (0.30 to 0.33mm) with 1oz cop- per via barrel plating. These re commendations are to be used as a guideline only. Table 17: Thermal Data Parameter Symbol CONDITIONS PKG Typ Values (C/W) Notes Thermal Resistance JC Junction to Case BAG144 6.8 JEDEC PCB (8x8 matrix) JB Junction to Base 16.2 JA1 Junction to Air, still air 34.8 JA2 Junction to Air, 1 m/s air flow 28.8 JA3 Junction to Air, 2 m/s air flow 26.7 JA4 Junction to Air, 3 m/s air flow 25.7

8 ELECTRICAL SPECIFICATIONS

8.1 ABSOLUTE MAXIMUM RATING

8.2 RECOMMENDED OPER ATION CONDITIONS

Table 18: Absolute Maximum Rating Symbol Parameter Min Max Unit VDDA, VDDAO, VDDDO,VDDD Supply Voltage VDDA, VDDAO, VDDDO,VDDD -0.5 3.6 V VDDD_1_8 Supply Voltage VDDD_1_8 -0.5 1.98 V VINCMOS Input Voltage (CMOS and Open drain pins) -0.5 5.5 V VINDIFF Input Voltage (Differential and AMI pins) -0.5 VDDD+ 0.5 V VINAN Input Voltage (Analog pins) -0.5 2.2 V IOUTCONT Output Current (Continuous current) 50 mA IOUTSURGE Output Current (Surge current) 100 mA TA Ambient Operating Temperature Range -40 85 °C TSTOR Storage Temperature -50 150 °C Note: CDM Classification - Class III (JESD22 - C101) HBM Classification - Class 2 (JS-001-2010) Table 19: Recommended Operation Conditions Symbol Parameter Min Typ Max Unit Test Condition VDDA, VDDAO, VDDDO,VDDD Power Supply (DC voltage) 3.135 3.3 3.465 V VDDD_1_8 Power Supply (DC voltage) VDDD_1_8 1.71 1.8 1.89 V TA Ambient Temperature Range -40 85 °C IDDA Analog Supply Current 327.10 377.61 mA IDDD Digital Supply Current (VDDD) 25.53 34.58 mA IDDD_1_8 Digital Supply Current (VDDD_1_8) 84.38 97.53 mA IDDDO Digital Output Supply Current 49.45 72.11 mA All outputs enabled IDDAO Analog Output Supply Current 149.22 178.15 mA All outputs enabled, unloaded Analog Output Supply Current (loaded) 202.42 236.67 mA All outputs enabled,

4 LVPECL outputs

PTOT Total Power Dissipation 1.97 2.49 W All outputs enabled, excluding the loading

8.3 I/O SPECIFICATIONS

8.3.1 AMI INPUT / OUTPUT PORT

8.3.1.1 Structure

Figure 31. 64 kHz + 8 kHz Signal Structure Figure 32. 64 kHz + 8 kHz + 0.4 kHz Signal Structure

8.3.1.2 I/O Level

Figure 33. 64 kHz + 8 kHz / 64 kHz + 8 kHz + 0.4 kHz Figure 34. 64 kHz + 8 kHz / 64 kHz + 8 kHz + 0.4 kHz

2 Vp-p

0 VIM

8.3.1.3 Over-Voltage Protection

according to ITU Recommendation K.41. to achieve the required 1 V pk-pk voltage level for the positive and negative pulses.

8.3.2 CMOS INPUT / OUTPUT PORT

Table 21: CMOS Input Port Electrical Characteristics Parameter Description Min Typ Max Unit Test Condition VIH Input Voltage High 2 V VIL Input Voltage Low 0.8 V IIN Input Current ±10 A Table 22: CMOS Input Port with Internal Pull-Up Resistor Electrical Characteristics Parameter Description Min Typ Max Unit Test Condition VIH Input Voltage High 2 V VIL Input Voltage Low 0.8 V PU Pull-Up Resistor 50 K  IIN Input Current ±150 A Table 23: CMOS Input Port with Internal Pull-Down Resistor Electrical Characteristics Parameter Description Min Typ Max Unit Test Condition VIH Input Voltage High 2 V VIL Input Voltage Low 0.8 V PD Pull-Down Resistor 50 K  IIN Input Current ±150 A Table 24: CMOS Output Port Electrical Characteristics Application Pin Parameter Description Min Typ Max Unit Test Condition Output Clock VOH Output Voltage High 2.4 VDD V IOH = -4 mA VOL Output Voltage Low 0.4 V IOL = 4 mA tR Rise time 2.2 ns CLOAD = 15 pF tF Fall time 2.2 ns CLOAD = 15 pF Other Output VOH Output Voltage High 2.4 V IOH = -2 mA VOL Output Voltage Low 0.4 V IOL= 2 mA tR Rise Time 7 20 ns CLOAD = 50 pF tF Fall Time 7 20 ns CLOAD = 50 pF

8.3.3 LVPECL / LVDS INPUT / OUTPUT PORT

8.3.3.1 PECL Input Port

Figure 36. Recommended PECL Input Port Line Termination

1 PPS

Assuming a differential input voltage of at least 100 mV.
Unused differential input terminated to VDD-1.4 V.

8.3.3.2 LVPECL Output Port

tionality. These outputs are designed to drive 50  transmission lines. Figure 38. 3.3V LVPECL Output Termination

8.3.4 LVDS INPUT / OUTPUT PORT

8.3.4.1 LVDS INPUT PORT

Figure 42. Recommended LVDS Input Port Line Termination

8.3.4.2 LVDS Output Port

8.3.5 OUTPUT CLOCK DUTY CYCLE

NOTE: Output Duty Cycle configured using APLL1 or APLL2.

8.3.5.1 Wiring the Differential Input to Accept Single-Ended

attenuate the signal in half. This can be done in one of two ways. impedance. For most 50 applications, R3 and R4 can be 100 . Figure 44. Recommended Schematic for Wiring a Differential Input to Accept Single-ended Levels

8.4 JITTER PERFORMANCE

Table 30: Gigabit Ethernet Output Clock Jitter Generation (jitter measured on one differential output of APLL1/2 with one differential output enabled) Output Frequency RMS Jitter Typ (ps) RM S Jitter Max (ps) Test Filter Notes

25 MHz

0.72 1.14 2.5 kHz - 5 MHz ITU-T G.8262 limit 0.5 UI p-p (1 UI = 0.8 ns) 0.58 0.78 12 kHz - 5 MHz 0.28 0.34 637 kHz - 5 MHz IEEE 802.3-2008 limit 0.24 UI p-p /

0.0174 UI RMS

(1 UI = 0.8 ns) 125MHz 0.72 1.19 2.5 kHz to 10 MHz ITU-T G.8262 limit 0.5 UI p-p (1 UI = 0.8 ns) 0.59 0.80 12 kHz - 20 MHz 0.20 0.28 637 kHz - 10 MHz IEEE 802.3-2008 limit 0.24 UI p-p / (1 UI = 0.8 ns) 156.25MHz 0.57 0.80 12 kHz - 20 MHz 0.53 0.97 20 kHz - 40 MHz ITU-T G.8262 limit 0.5 UI p-p (1 UI = 100.47 ps) 0.24 0.30 1 MHz - 30 MHz 0.17 0.23 1.875 MHz - 20 MHz IEEE 802.3-2008 limit 0.28 UI p-p /

0.0203 UI RMS

(1 UI = 100.47 ps) 625MHz 0.56 0.95 12 kHz - 20 MHz 0.52 0.71 20 kHz - 80 MHz ITU-T G.8262 limit 0.5 UI p-p (1 UI = 100.47 ps) 0.16 0.22 1 MHz - 30 MHz 0.10 0.148 1.875 MHz - 20 MHz IEEE 802.3-2008 limit 0.28 UI p-p / (1 UI = 100.47 ps) NOTE 1: DPLL locked to input clock

62©2017 Integrated Device Technology, Inc. 82P33810 Datasheet September 4, 2017 Table 31: Gigabit Ethernet Output Clock Jitter Generation (Jitter measured on one CMOS output of APLL1/2 with one CMOS output enabled) Output Frequency RMS Jitter Typ (ps) RM S Jitter Max (ps) Test Filter Notes 0.69 1.11 2.5 kHz - 5 MHz ITU-T G.8262 limit 0.5 UI p-p (1 UI = 0.8 ns) 0.55 0.76 12 kHz - 5 MHz 0.24 0.29 637 kHz - 5 MHz IEEE 802.3-2008 limit 0.24 UI p-p / (1 UI = 0.8 ns) 125MHz 0.76 1.25 2.5 kHz to 10 MHz ITU-T G.8262 limit 0.5 UI p-p (1 UI = 0.8 ns) 0.61 0.85 12 kHz - 20 MHz 0.21 0.28 637 kHz - 10 MHz IEEE 802.3-2008 limit 0.24 UI p-p / (1 UI = 0.8 ns) NOTE 1: DPLL locked to input clock

63©2017 Integrated Device Technology, Inc. 82P33810 Datasheet September 4, 2017 Table 32: SONET/SDH Output Clock Jitter Generation (jitter measured on one differential output of APLL1/2 with one differential output enabled Output Frequency RMS Jitter Typ (ps) RM S Jitter Max (ps) Test Filter Notes

19.44 MHz

0.57 0.80 12 kHz to 1.3MHz GR-253-CORE and ITU-T G.813 Option 2 limit 0.1 UI p-p /

0.01 UI RMS

(STM-16: 1UI = 0.40 ns) 0.65 0.88 12kHz to 5MHz ITU-T G.813 Option 1 limit 0.5 UI p-p (STM-1: 1 UI = 6.43 ns) 0.92 1.48 500 Hz to 1.3 MHz ITU-T G.813 Option 1 limit 0.5 UI p-p (STM-4: 1 UI = 1.61 ns) 0.92 1.46 1 kHz to 5 MHz ITU-T G.813 Option 1 limit 0.1 UI p-p (STM-1: 1 UI = 6.43 ns) 0.34 0.50 65 kHz to 1.3 MHz ITU-T G.813 Option 1 limit 0.1 UI p-p (STM-4: 1 UI = 1.61 ns) 0.40 0.58 250 kHz to 5 MHz ITU-T G.813 Option 1 limit 0.1 UI p-p (STM-4: 1 UI = 1.61 ns)

77.76 MHz

0.61 0.90 12 kHz to 20 MHz GR-253-CORE and ITU-T G.813 Option 2 limit 0.1 UI p-p / (STM-16: 1UI = 0.40 ns) 0.94 1.51 500 Hz to 1.3 MHz ITU-T G.813 Option 1 limit 0.5 UI p-p (STM-1: 1 UI = 6.43 ns) 0.89 1.44 1 kHz to 5 MHz ITU-T G.813 Option 1 limit 0.5 UI p-p (STM-4: 1 UI = 1.61 ns) 0.30 0.38 65 kHz to 1.3 MHz ITU-T G.813 Option 1 limit 0.1 UI p-p (STM-1: 1 UI = 6.43 ns) 0.23 0.31 250 kHz to 5 MHz ITU-T G.813 Option 1 limit 0.1 UI p-p (STM-4: 1 UI = 1.61 ns)

155.52 MHz

0.61 0.85 12 kHz to 20 MHz GR-253-CORE and ITU-T G.813 Option 2 limit 0.1 UI p-p / (STM-16: 1UI = 0.40 ns) 0.97 1.56 500 Hz to 1.3 MHz ITU-T G.813 Option 1 limit 0.5 UI p-p (STM-1: 1 UI = 6.43 ns) 0.92 1.49 1 kHz to 5 MHz ITU-T G.813 Option 1 limit 0.5 UI p-p (STM-4: 1 UI = 1.61 ns) 0.73 1.13 5 kHz to 20 MHz ITU-T G.813 Option 1 limit 0.5 UI p-p (STM-16: 1UI = 0.40 ns) 0.30 0.39 65 kHz to 1.3 MHz ITU-T G.813 Option 1 limit 0.1 UI p-p (STM-1: 1 UI = 6.43 ns) 0.21 0.31 250 kHz to 5 MHz ITU-T G.813 Option 1 limit 0.1 UI p-p (STM-4: 1 UI = 1.61 ns) 0.20 0.26 1 MHz to 20 MHz ITU-T G.813 Option 1 limit 0.1 UI p-p (STM-16: 1UI = 0.40 ns) Table 32: SONET/SDH Output Clock Jitter Generation (jitter measured on one differential output of APLL1/2 with one differential output enabled Output Frequency RMS Jitter Typ (ps) RM S Jitter Max (ps) Test Filter Notes

622.08 MHz

0.63 1.05 12 kHz to 20 MHz GR-253-CORE and ITU-T G.813 Option 2 limit 0.1 UI p-p / (STM-16: 1UI = 0.40 ns) 0.54 0.71 20kHz to 80 MHz GR-253-CORE and ITU-T G.813 Option 2 limit 0.3 UI p-p (STM-64: 1 UI = 0.10 ns) ITU-T G.813 Option 1 limit 0.5 UI p-p (STM-64: 1 UI = 0.10 ns) 0.16 0.23 4 MHz to 80 MHz GR-253-CORE and ITU-T G.813 Option 2 limit 0.1 UI p-p (STM-64: 1 UI = 0.10 ns) ITU-T G.813 Option 1 limit 0.1 UI p-p (STM-64: 1 UI = 0.10 ns) 1.02 1.87 500 Hz to 1.3 MHz ITU-T G.813 Option 1 limit 0.5 UI p-p (STM-1: 1 UI = 6.43 ns) 0.97 1.81 1 kHz to 5 MHz ITU-T G.813 Option 1 limit 0.5 UI p-p (STM-4: 1 UI = 1.61 ns) 0.76 1.42 5 kHz to 20 MHz ITU-T G.813 Option 1 limit 0.5 UI p-p (STM-16: 1UI = 0.40 ns) 0.31 0.41 65 kHz to 1.3 MHz ITU-T G.813 Option 1 limit 0.1 UI p-p (STM-1: 1 UI = 6.43 ns) 0.21 0.32 250 kHz to 5 MHz ITU-T G.813 Option 1 limit 0.1 UI p-p (STM-4: 1 UI = 1.61 ns) 0.15 0.20 1 MHz to 20 MHz ITU-T G.813 Option 1 limit 0.1 UI p-p (STM-16: 1UI = 0.40 ns) NOTE 1: DPLL locked to input clock Table 32: SONET/SDH Output Clock Jitter Generation (jitter measured on one differential output of APLL1/2 with one differential output enabled Output Frequency RMS Jitter Typ (ps) RM S Jitter Max (ps) Test Filter Notes

66©2017 Integrated Device Technology, Inc. 82P33810 Datasheet September 4, 2017 Table 33: SONET/SDH Output Clock Jitter Generation (jitter measured on one CMOS output of APLL1/2 with one CMOS output enabled) Output Frequency RMS Jitter Typ (ps) RM S Jitter Max (ps) Test Filter Notes 0.54 0.81 12 kHz to 1.3MHz GR-253-CORE and ITU-T G.813 Option 2 limit 0.1 UI p-p / (STM-16: 1UI = 0.40 ns) 0.59 0.83 12kHz to 5MHz ITU-T G.813 Option 1 limit 0.5 UI p-p (STM-1: 1 UI = 6.43 ns) 0.91 1.61 500 Hz to 1.3 MHz ITU-T G.813 Option 1 limit 0.5 UI p-p (STM-4: 1 UI = 1.61 ns) 0.88 1.53 1 kHz to 5 MHz ITU-T G.813 Option 1 limit 0.1 UI p-p (STM-1: 1 UI = 6.43 ns) 0.30 0.39 65 kHz to 1.3 MHz ITU-T G.813 Option 1 limit 0.1 UI p-p (STM-4: 1 UI = 1.61 ns) 0.28 0.36 250 kHz to 5 MHz ITU-T G.813 Option 1 limit 0.1 UI p-p (STM-4: 1 UI = 1.61 ns) 0.62 0.97 12 kHz to 20 MHz GR-253-CORE and ITU-T G.813 Option 2 limit 0.1 UI p-p (STM-4: 1 UI = 1.61 ns) 0.95 1.67 500 Hz to 1.3 MHz ITU-T G.813 Option 1 limit 0.5 UI p-p (STM-1: 1 UI = 6.43 ns) 0.91 1.59 1 kHz to 5 MHz ITU-T G.813 Option 1 limit 0.5 UI p-p (STM-4: 1 UI = 1.61 ns) 0.30 0.39 65 kHz to 1.3 MHz ITU-T G.813 Option 1 limit 0.1 UI p-p (STM-1: 1 UI = 6.43 ns) 0.23 0.33 250 kHz to 5 MHz ITU-T G.813 Option 1 limit 0.1 UI p-p (STM-4: 1 UI = 1.61 ns) NOTE 1: DPLL locked to input clock

67©2017 Integrated Device Technology, Inc. 82P33810 Datasheet September 4, 2017 Table 34: DPLL1/DPLL2 Output Clock Jitter Generation (Jitter measured on one CMOS output of DPLL1/DPLL2 with all other outputs disabled) Output Frequency RMS Jitter Typ (ps) RM S Jitter Max (ps) Test Filter Notes 10 MHz 100.11 619.64 100 Hz - 100 kHz N x 1.544 MHz (Note 2) 100.63 543.45 100 Hz - 40 kHz 16.06 39.94 8 kHz - 40 kHz ANSI T1.403 limit 0.07 UI p-p (DS1: 1 UI = 647 ns) N x 2.048 MHz (Note 3) 99.42 449.83 100 Hz - 100 kHz 10.66 26.44 18 kHz - 100 kHz ITU-T G.823 limit 0.2 UI p-p (E1: 1 UI = 488 ns)

34.368 MHz

101.67 202.75 100 Hz - 800 kHz 25.62 39.06 10 kHz - 800 kHz ITU-T G.751 limit 0.05 UI p-p (E3: 1 UI = 29.10 ns)

44.736 MHz

105.16 198.15 100 Hz - 400 kHz 20.77 27.44 30 kHz - 400 kHz NOTE 1:DPLL1/2 locked to input clock NOTE 2: Measured on 12.352 MHz output clock NOTE 3: Measured on 16.384 MHz output clock Table 35: DPLL3 Output Clock Jitter Generation (Jitter measured on one CMOS output of DPLL3 with all other outputs disabled) Output Frequency RMS Jitter Typ (ps) RM S Jitter Max (ps) Test Filter Notes N x 2.048 MHz Note 2 147.325 347.530 100 Hz - 100 kHz 8.02 17.24 18 kHz - 100 kHz ITU-T G.823 limit 0.2 UI p-p (E1: 1 UI = 488 ns) N x 1.544 MHz Note 3 133.88 303.43 100 Hz - 40 kHz 0.80 1.47 8 kHz - 40 kHz ANSI T1.403 limit 0.07 UI p-p (DS1: 1 UI = 647 ns) NOTE 1:DPLL3 locked to input clock NOTE 2: Measured on 12.288 MHz output clock NOTE 3: Measured on 12.352 MHz output clock

8.5 INPUT / OUTPUT CLOCK TIMING

The inputs and outputs are aligned ideally. But due to the circuit delays, there is delay between the inputs and outputs. Figure 45. Input / output clock timing

8.6 OUTPUT / OUTPUT CLOCK TIMING

Figure 46. Output / output clock timing NOTE 2. The measurements in the above table are over operational temperature, varying power supply and repeated power on/off cycle. NOTE 3. Measurements are taken using an ideal REF input and an ideal System clock to account for only internal delays in the device.

ORDERING INFORMATION

“G” after the two-letter package code denotes Pb-Free configuration, RoHS compliant.

REVISION HISTORY

Table 38: Ordering Information Part/Order Number Package Shipping Packaging Temperature 82P33810ABAG 144-pin CABGA green package Tray -40o to +85oC 82P33810ABAG8 144-pin CABGA green package Tape & Reel -40o to +85oC Revision Date Description of Change September 4, 2017 * Updated the de scription of MS/SL in Table 1 * Added MS/SL PIN USAGE MS/SL PIN USAGE * Updated Table 8 * Updated the package outline drawings; however, no mechanical changes. December 22, 2016 Changes on pages 9, 11, 31-32, 37-38, 69 March, 29, 2016 Changes on pages 40, 61 June 24, 2015 Changes on pages 9, 13, 46, 47, 48, 62, 78 May 13, 2015 Changes on page 60, 78 April 21, 2015 Changes on page 69, 71, 73 - 75 February 6, 2015 Changes on pages 45, 69 (Table 38), 72 (Table 40), 73 Table 41 January 28, 15 Change on pages 21, 42 December 19, 2014 Change on page 60 November 20, 2014 Changed part number to 82P33810ABAG and removed the errata Changes on page 9, 12, and 50

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Renesas Technology Corp 82P33810 overview.

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Summary

Synchronization Management Unit for IEEE 1588 and Synchronous Ethernet September 4, 2017

Description

Synchronization Management Unit for IEEE 1588 and Synchronous Ethernet September 4, 2017

Source title 82P33810 Datasheet(PDF) - Renesas Technology Corp

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